Method to imitate double-frequency radio signals

FIELD: radio engineering, communications.

SUBSTANCE: method to imitate radio signals is designed for testing of tracking systems of pulse radar stations (RS). The entire cycle of imitation is divided into two time signals. During the first interval the pulses received from the RS are range-stolen. During the second interval two pulse sequences are generated, which are shifted in time and spaced by frequency. The time shift is arranged as slowly changing, for instance, in accordance with the harmonic law, at the same time harmonics for both frequencies have one and the same frequency, but are phase-shifted. The frequency separation is carried out in two stages: at first the shift is carried out by the value where ω_int - the first intermediate frequency of an RS amplifier, and then both pulse sequences - by the value δ, exceeding the pass band of the specified amplifier. To eliminate stable zeros of a direction-finding characteristic of the RS, the carrier phase in one of sequences is periodically changed relative to the other by 180 degrees, at the same time the phase of the slowly changing modulating function is varied.

EFFECT: increased imitating ability of a double-frequency radio signal.

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The invention relates to electrical engineering and can be used in radar systems.

The known method simulation signal based on the use of passive (angle lens and reflectors) and active means of forming a secondary radio emission (radio retransmitters) (Wohlbach. Radar reflectors. M: Swradio, 1975 [1]). Such funds are intended to indicate the presence of a signal, but not adjusted for quality control tracking systems radar (radar).

The known method simulation of radio signals, based on the generation and radiation of a series of response pulses that overlap the specified interval range followed by the media (Theoretical fundamentals of radar. Edited Vaitulevich, s, M.: Swradio, 1978 [2]). When the variation of the delay between pulses such multiple signal response can simulate moving decoys can hinder the recognition of the true purpose in browse mode radar situation. However, simulating the signals of this type do not bear false angular information and therefore cannot be used for quality control tracking systems goniometric coordinator of the station.

Closest to the proposed technical solution is the simulation based on the formation and emission frequency signal Aeiou, Khiromichi. Monopulse radar. M.: Radio and communication, 1984 [3]). The advantage of this method of simulation is the possibility of introducing false angular information in the simplest single-point radiation of the signal from the Board of the media. If the spacing in frequency between the components of the signal equal to the first intermediate frequency of the radar receiver, under certain conditions, the direction-finding characteristic angular coordinator RLS is distorted, the target tracking is disturbed, the tracking system drifts up to the failure of tracking. We denote these conditions. First, the presence of direct detection in the input elements of the radar receiver secondly, the presence of quadratic current-voltage characteristics of the detectors thirdly, no side signals, for example, the reflected signal fourthly, no heterogenerous any of the components of the frequency signal. When these conditions are met, the direction-finding characteristic (HRP) acquires an even dependence on the angle between the, at the same time disappear stable zeros of HRP. However, to realize these conditions underlying the known method, it is not possible. In fact, as shown by experimental studies, the detection characteristic of microwave diodes contains both even (including square) members, and odd (including linear) members. Prisutstvie is odd, sostavljajushhih in the signal violates even the nature of HRP, leads to the emergence of resistant zeros, which are captured in the tracking system and maintain support. About the same impact and the reflected signal. In the field of small-and medium-range carrier, where the influence of the reflected signal at the input of the radar is especially great, saved in PH stable zeros. In addition, it is possible and heterodyning, as the second harmonic of one of the components of the dual-frequency signal after frequency conversion falls within the bandwidth of the radar receiver. All these phenomena are destroying the useful effect that reduces the simulation ability of this method.

The technical result of the proposed solutions is to improve the simulation capabilities of dual-frequency radio signal that is reflected in the increase in the probability of failure of tracking angular coordinator of the station.

This result is achieved by changing the delay of received impulses in the direction of increasing ("pulling forward ") to the value corresponding to the selected false-range form of the detainees fluctuations by balanced modulation of the first and second components of the two-frequency signal separated by the frequency of these fluctuations on the value ofchange the phase of both components at a constant speed greater than the bandwidth of the first intermediate amplifier frequent what you radar, generate oscillation type a square wave with a frequency greater than the bandwidth tracking meter range radar, changing the phase of one of the formed component relative to another leap from zero to 180 degrees with a frequency formed by meander, simultaneously with the formation of two-frequency component of the signal to modulate the delay on the wrong range, for example, the harmonic law, and the phase difference modulated delay when going from even to odd half cycles of the meander back and constant support.

However remember the frequency received from the radar of radio EGR on a specified number of turns to form the stored packets of signals, detects the received impulses, delay proyektirovaniye pulses, change the delay time in accordance with the desired law, and detained videoanalyse strobert memorized packs of radio signals.

In addition, filter and detects the accepted control signal, separated from proyektirovanive voltage reference signal with a frequencyproduce continuous oscillation , synchronizat obtained oscillation frequency allocated to a reference signal, phase shift, is used in balanced modulation dephased synchronized oscillations as a modulating voltage.

To understand who define the company tasks consider two idealized cases. Let the input of the radar receives only one signal from the target, and the power of this signal is substantially greater than the internal noise of the receiver of the station. In this case, the dependence of the output voltage angular coordinator on the angle between the open feedback (that is, the direction-finding characteristic) is near zero odd character. When you enable tracking system ravesignal direction is strictly relevant to sustainable zero HRP. Let us consider the second case. Unplug the microwave heterodyne, and will radiate with the same purpose in the range of the radar two approximately equal to the pulse signal separated by the first intermediate frequency. As in the differential and total channel monopulse radar input mixers in this case will work in the direct detection of the incoming impulses. The result of the detection of beats in the band of the receiver depends on the power of the input signals and types of volt-ampere characteristics (VAC) of the microwave diode in the mixer. If power is small, and I-V characteristics can be approximated by a quadratic, PH close to even dependencies, and Vice versa, when the signal strength is great and sufficient for linear detection, HRP is dominated by odd components with stable zeros. Experimental data at the dawn radiology the AI, show [4]that the I-V characteristics of the diode can be approximated in the field of positive voltage curve close to the exponential curve, i.e. it contains both odd and even members of the series. It follows that under two-frequency signal PH is in General a complex shape with stable and unstable zeros.

For the approximation of HRP to form described unipolar even function features: firstly, to generate such a signal, of odd degree which would not have been able to get into the bandwidth of the radar receiver on the intermediate frequency. On the other hand, the same signal must provide for free passage through the receiver radar even powers of the specified signal, and secondly, the phase of the generated signal periodically with a certain frequency to change by 180 degrees, thirdly, the delay of the radio pulses to modulate the law slowly varying functions, simulating a valid maneuver purpose, for example, the harmonic law, fourth, to ensure the prevalence of power generated and emitted signal over the power of the reflected signal.

The voltage at the output of the microwave detector, as is known [4], is determined by the envelope signal. The envelope frequency signal depends on the nature of the beating of these frequencies, i.e. on the ratio of the amplitudes of generating oscillations, different is based frequency (ω _CRand mutual phasing of these fluctuations. Assuming the first two parameters unchanged, we will be fast enough to change the phase of the beating from zero to 180 degrees. If you average this process will come to a mutual compensation of its components. A different situation arises when the delay of the pulses is modulated by slowly varying harmonic law, and simultaneously with the jump phase of the beating is a step in the phase of low-frequency harmonics on small value of θ. There is a "splitting" of the original envelope into two parts: the phase of the beating zero and the phase is 180 degrees. Both components have the same frequency of the beating, but opposite signs at variable parts. In addition, the second component, an additional phase shift is equal to θ. As a result, the input of the radar receiver is compensation odd frequencies ω_CR·3ω_CR·5ω_CRand so on, but are stored frequency 2ω_CR·4ω_CR·6 & omega;_CRand so on, which, however, in-band receiver does not fall, as the latter is configured on the frequency ω_CR. In contrast, the square of the envelope (and even her degrees) remain members with frequency ω_CRthat are part of the output of the radar receiver. A stable zeros disappear appears it is a metastable zero slope which drops to minimum,there is a drift tracking system with subsequent failure of tracking. To restore security, you must disable the specified signal processing, and then after the capture of the failure of tracking the conditions of the tests can be repeated.

Dual-frequency signal is formed by two-way balanced modulation pulse radiotelephony. The resulting modulation components of the signal is shifted in frequency relative to the frequency of input fluctuations on the value of. To provide direct detection of double-frequency signal in the receiver of the radar it is necessary to eliminate the danger heterodyne conversion of one component of this signal, which could lead to additional Samotsvety goals. This danger exists because the second harmonic of the differential signal when converting the frequency is within the bandwidth of the radar receiver. For this reason, provided the frequency shift of the two component signal by an amount exceeding the bandwidth of the receiver, but with preservation of frequency separation between the components. This is done by phase modulation of both components with postoyannoi speed δ phase changes.

Minimum value of δ should be greater than the bandwidth of the amplifier radar according to a first intermediate frequency Δω. In fact, at least the first and second harmonics of the difference frequency when the heterodyning clicks the used signal does not fall within the target receiver station. However, using simple calculations can show that there are zones of acceptable values of δ, and these zones are defined by the following inequality

For small values of δ (but exceeding Δω) it is convenient to use a sawtooth phase modulation with frequency of drinking δ (amplitude modulation characteristics 2π) or with frequency δ/2 (at scale 4π) etc. In the case of increased (but valid), the values of δ used dual channel, but SSB balanced modulation.

To neutralize the action of the reflected signal, it is necessary to provide conditions for its output of range gate selector radar and substitution signal generated by higher power. This provides smooth or smoothly-speed (digital version) the delay variation of the generated pulses, for example, according to the parabolic law ("pulling forward") from the minimum value (defined residual time delay relay to one-tenth μs) up to a maximum that depends on the selected false range (for example, 1 km). If the test is only tracking system angular coordinator, anti-tilt range (if present) are disabled, and the acceleration range gate in the process of withdrawal does not exceed the value allowed for the maneuver objectives. In the case of complex tests on the corner and Yes the major along with the withdrawal may include noise cover of the reflected signal, preventing the normal functioning of the protection of the rangefinder.

False range that Pereyaslavets selector and witness measuring range exceeds the interval covered by the gate, but is within the zone of possible maneuver objectives. Thus the delay of the pulses is modulated according to the law of slowly varying functions. When selecting harmonic functions important its phasing. Since the phase modulation function is changing every pollperiod meander on a constant θ, and the frequency of the waveform exceeds the lane tracking system in range, this system appears to be under the influence of two different pulse sequences, the delay difference can be described as the difference of harmonic functions shifted in phase. theory says that the difference between two harmonics of the same frequency with the same amplitude and shifted by a small angle θ, is an oscillation of the same frequency, orthogonal source fluctuations. Such differential pulse sequence after adjusting and smoothing arrives at the inputs of the azimuth and elevation channels radar.

For the formation of delayed impulses, separated by time first, the law of the withdrawal, and then in the vicinity of the selected delay (false range) law is the harmonic function, used recycling taken from the radar impulses. The speed of radio in the ring recirculation or (equivalent) time memorizing the carrier frequency is determined by the width (duration) of videokursov, the guard ring circulation. In turn, the duration of these pulses is directly dependent on the selected interval, false ranges. To get from the saved bundles of radiotelephony narrow delayed by the given law radiopulse, you should create videocasette a sequence of pulses, each separated in time by the same law and the gate remembered radiotolerance in the path of the microwave.

Information about the intermediate frequency of the radar receiver may be formed in advance in the preparation of media. However, it is more practical to send it via radio with the reference signal in a dedicated sub-band of frequencies. In General, the control signal is used to verify the functionality of on-Board equipment, but in this case it can additionally be modulated by a signal frequency. Aboard the carrier control signal is filtered in a given sub-band is detected, and then allocated as a result of the detection of the oscillation frequencysynchronizes the reference voltage, which is suitable the phase is fed to balanced modulation of the generated signal.

Consider the question from a mathematical point of view. Let the radar pulse with a frequency of filling in ω is described by the function

u(t)=V_mcos(ωt-φ); t₀≤t≤t₀+t_u,

where t_uthe pulse duration. The same pulse, the delay which varies according to the law τ₃(t)has the form

u(t)=V_mcos{ω(t-τ₃(t))-φ}

After two-way balanced modulation and shift the frequency by the value of δ will provide a dual frequency signal

Both signal components are separated from each other in frequency by the value of ω_CR⊰⊰ω, resulting in a dual frequency signal can be represented in the form

u₁(t)=E_m(t)cos{(ω+δ)[t-τ₃(t)]-ψ(t)},

where

Δφ=φ₁- Φ₂

For the envelope E_m(t) it is more convenient to use another expression

where

At V_m1≠V_m2the coefficient β<1.

Consider the effect of phase meander modulation on the envelope dokashiteru signal. Assuming the amplitude ratio unchanged (β=const) and the fact that simultaneously with the jump phase of the carrier by 180° shift modulating the delay function on the angle θ, we obtain the expression for the envelope as the sum of two components</>

Introducing the generalized phase

γ(t)=ω_CR[t-τ₃(t)]-Δφ,

find

.

We brought the generated frequency signal to monocosthea mind, but with variable envelope and phase

u₁(t)=E_m1(t)cos[(ω+δ)t+ψ₁(t)],

where ψ₁(t) is a variable phase.

Let us now consider how this signal passes through the input nodes of the radar receiver. At the output of the antennas difference and sum channels RLS have

u_Δ(t)=E_m1(t)F_Δ(ν)cos[(ω+δ)t+ψ₂(t)]=E_m1(t)F_Δ(ν)cosΦ(t)

u_Σ(t)=E_m1(t)F_Σ(ν)cos[(ω+δ)t+ψ₂(t)]=E_m1(t)F_Σ(ν)cosΦ(t)

where F_ΔF_Σ- beam antennas, ν is the angle between, ψ₂(t) differs from the phase ψ₁(t) the phase shift of a wave in space. Next, the resulting oscillations are served at the input of the mixers in the mode of direct detection. Volt-ampere characteristic of microwave diodes will approximate the exponent [4]. This will limit ourselves to three members of the series, allowing you to explore the action as the even and odd components of the output current of the detectors

From the classic radio it is known that when exposed to harmonic oscillations on the nonlinearity of General form reaction occurs as the fundamental frequency, the frequencies of higher harmonics. But the amplitude detector is a special kind of nonlinearity, for in the ideal case responds only on the envelope of the voltage supplied (but not phase)although all of these frequencies. Therefore, the current in the circuit of the amplitude detector is expanded in a Fourier series of the following form

i_Δ(x)=f(x_Δ)=f₀(E_mF_Δ)+f₁(E_mF_Δ)cosΦ(t)+f₂(E_mF_Δ)cos2Φ(t)+...

i_Σ(x)=f(x_Σ)=f₀(E_mF_Σ)+f₁(E_mF_Σ)cosΦ(t)+f₂(E_mF_Σ)cos2Φ(t)+...

The coefficients of the series are calculated using ratios

where cosnΦ=cosn[(ω+δ)t+ψ₂(t)], n=1, 2...

f(x) is the detection function (volt-ampere characteristic).

But high-frequency components (at frequency ω+δ,²(ω+δ)...) does not fall within the bandwidth of the radar receiver and filtered, so we are interested in low-frequency member of a number of f₀.

Believing, k=1, 2, 3, have;;etc. (when computing mean that cosx=0, π/2≤x≤π).

Let's start with the case of a linear detection (k=1), in which the envelope E_mF is linear. But the function E_m(t) consists of the sum of two radicals, which complicates the determination of its spectral composition. Do SL is blowing. Due to the fact that E_m(t) depends on a small parameter θ, decompose the function I(t,θ)=E_m(t,θ)/E_moin a Taylor series in powers of θ. Locking t=t₀and assuming θ⊰⊰t₀find

Given the known correlation for fractional degrees of dokladov (1±x)^m, |x|<1

As you can see, due to the compensation of odd degrees in I(t₀) in addition to the permanent members include members with a double, quadruple, etc. frequencies (i.e. members with frequency 2ω_CR, 4ω_CRetc), which in-band amplifier does not fall.

Computing the derivative I'(t₀), make sure that members with odd degree β are mutually compensated and remain only the terms with even powers of β.

Double, quadruple, etc. the frequency included in the I'(t₀), in-band receiver is also not undergo. It can be shown that a similar situation occurs with derivatives of higher orders. Thus, all components of the function E_m(t,θ) in a linear detection in the receiver path of the radar station on the intermediate frequency does not fall.

We now turn to a square-law envelope detection (k=2). The square of the function I(t,θ) has the form

Neglecting terms that are not in the receive path, the radar will receive: Isup> 2(t,θ)≈2β[cosγ(t)-cosγ(t-θ)].

Therefore, due to the quadratic detection in the receive path of the radar signal as the difference between the functions, shifted in time, which fully described the physics of the processes. Naturally, the contribution to the resulting signal, although greatly reduced, will make components at higher, but even the degree detector characteristics (k=4, 6...). We denote these even the remaining members of the b_Chet.

The voltage at the inputs of phase detectors angular channels RLS record in the form

Assuming γ(t)=ω_nt+γ₀(t);find an approximate expression for the HRP.

wherem=1, 2...

- even remaining a member.

Thus HRP has an even character and does not contain stable zeros.

Figure 1 shows the block diagram of the proposed method, figure 2 is a block circuit diagram of the formation of the gate pulses in figure 3 - block diagram of the reproduction carrier frequency, figure 4 - plot of pulse delay, figure 5 - spectral characteristics of the signals (a) spectrum of the received signal, (b) spectrum of the two-frequency signal in the main and sub-band amplifier,g) valid values, δ d) e) options frequency shifts), figure 6 - plot of harmonic signals with respect meander oscillations, Fig 7 is a plot of the modulating voltages of the blocks 9 and 10.

Receiving antenna 1 is connected through a splitter with 2 unit play of the carrier frequency 3, the first detector 4 and the second detector 5. The output unit 3 via microwave switch 6 is connected to the balanced modulator 7 and the detector 4 to block the formation of the gate pulse 8. The outputs of the balanced modulator 7 through the phase modulators 9 and 10, Cititel 11 and final amplifier 12 is connected to the transmitting antenna 13. The output of the detector 5 through the filter-amplifier 14, the block phase-locked loop 15 and the phase splitter 16 is connected to the modulating input of the balanced modulator 7. The generator frequency shift 17 and the generator type meander 18 through putmodulator 19 is connected with the baseband inputs of the modulators 9 and 10.

The timer 20 via the control unit 21 is connected to the generator deviates functions 22 and generator false range 23, and through them with the pulse shaper delay 24 and output stage 25. Proyektirovaniye pulses from the output of the detector 4 receives the inputs of the blocks 21 and 24, and also to the input of the pulse shaper memory 26.

The first directional coupler 27 through a microwave amplifier 28 is connected to the second directional coupler 29, which first output is om is connected to the microwave switch 30 and the delay line 31, and the second output of the coupler 29 is the output of the block 3.

Received by the antenna 1 pulse signal is fed to splitter 2, resultbase and separating the input signal into three output. Filtering is performed in the band of operating frequencies (first and second outputs) and in-band control of the frequency (the third exit). The radio signal from the first output is supplied to the unit playback, the carrier frequency is 3, which is a device with delayed feedback. Recirculation of the received impulses are produced in the feedback loop with a delay line 31 and the microwave amplifier 28, covering the range of the entire band of operating frequencies. In addition to the directional couplers 27 and 29 in the ring included microwave switch 30, which defines the number of circulation of the pulse or, equivalently, the interval memorization of the carrier frequency. For this purpose, the modulating input of the switch 30 is pulse corresponding to the duration of the shaper 26. The delay line 31 is advisable to choose a is approximately equal to the length of the input impulses, but if the latter is unknown or varies, the width of the circulating pulse is normalized by submitting to the control input of the amplifier 28 output signals (control signal not shown). The stored signal is supplied to the closed in the initial state the microwave switch 6, which opens the delayed video impulse generated at the output of the unit 8. To obtain the sequences of these Gating pulses are used taken from the second output of the splitter 2 signal, proyektirovanii pulse detector 4.

As the delay line in ring a rebreather can be used various types: they all have their advantages and disadvantages, which requires a compromise approach. So, waveguide lines have relatively low linear losses, but bulky in design. Solid lines on the basis of garnet crystals of yttrium small, but have big losses, ultrasonic line due to the double frequency conversion require serious complications scheme when working in a wide range of carrier frequencies. All of these types of lines received wide practical application.

The basis of operation of the processing unit stromimpulse 8 is the development of successive time intervals t₁and t₂, within which is a pulling range (t₁and modulation delay law false range (t₂). Sets the time source is the timer 20 clock pulses. On the set on the timer codes and external team started the timer along with the clock pulses and the pulses of the AMI process synchronization pulses at the beginning and end of the interval t ₁and t₂that (pulses) are fed to the control unit 21. In this block from the received pulses are produced interval voltage for creating control signals first generator 22, and then into the generator 23. The beginning and end of the pulse interval of the voltage coincides with the closest adopted from radar pulses, and the end of the interval t₁coincides with the beginning of the interval t₂. The generators 22 and 23, as well as the imaging unit 24 can be constructed as analog and digital circuits.

In the first case, for the formation of the parabolic law of withdrawal (block 22), you can use an electronic integrator operational amplifiers [5], and to create a low-frequency harmonic functions (block 23) is a synchronized RC oscillator. In block 24 with small overlaps can be applied standby multivibrators with electronic rearrangement of the pulse duration [5]. In such schemes the start is taken from the radar proyektirovanii pulses, and adjusting the pulse duration using the voltage supplied to the transistor control [5].

For the case of digital performance in blocks 22 and 23 is a voltage conversion in the form of leading and harmonic functions in the parallel code. This is usually performed dividing the clock frequency to confuse is to divided pulses schemes linearly increasing voltage, comparison with the voltage specified function, reset the "saw" at the moment of equality and encoding the respective time putinterval [5].

The code in this pointervalue is recorded in the comparator (block 24). With the arrival of the next pulse from the radar (the output of the detector 4) and the input clock signal is triggered input trigger block 24, which (trigger) triggers the counter. Code at the output of the counter is compared in the comparator with the recorded code, and in case of equality of codes, the counter is reset. In subsequent putinterval code changes in accordance with changes of the functions in blocks 22 and 23. Further codes are decrypted and converted into a delayed pulse.

Balanced modulator 7 is running in mode two-way modulation, when the side distant from the carrier by an amount equal. The modulator consists of two symmetrical shoulders, and SHF oscillations act on them in phase, and the modulating voltage with a phase shift of 90°. Modulated oscillations using directional couplers are transmitted on two outputs, with one of the outputs directly, and on the other with a shift of 90°, as a result can separate the side apart from the outputs of the modulator. Balanced modulators of this type are described in the literature and are built in recent years on the basis of application, hybrid ring bridges with di is DAMI in the printed version [6]. Such modulators is provided a suppressed carrier at octave band frequencies for more than 25 dB. Data on intermediate frequency transmitted from the radar to the carrier by the modulation control signal voltage of frequency ω_CR/2. The signal is sent over the radio link in the sub-range of the control frequency and secreted by the filter hub 2 on the second it comes out. After detection and amplification, and oscillation frequency ω_CR/2 is fed to the signal input of the system phase-locked loop 15, which is synchronized tunable local oscillator at this frequency. From separated in phase by 90° are obtained components is formed by modulating the signal from block 16 to block 7.

So, dual-frequency components of the signal taken from the output unit 7 must be shifted in frequency by the same amount δ and subjected to modulation in phase from zero to 180°. Produced both operations in the phase modulators 9 and 10. This is the sawtooth generator frequency δ 17 and the generator meander fluctuations 18. Sawtooth oscillations are amplified and are normalized in putmodulator 19 to a voltage corresponding to the magnitude of the phase 2π, and meander vibrations to a voltage corresponding to the phases 0,π. Sawtooth oscillations are superimposed on the waveform and served next to a modulating input, for example, block 9,while modulating the input unit 10 serves only sawtooth oscillations.

Sources of information

1. Waucoba. Radar reflectors. M: Swradio, 1975.

2. Theoretical bases of radar. Ed Vaitulevich. M: Swradio, 1978.

3. Aeiou, Khiromichi. Monopulse radar. M.: Radio and communication, 1984.

4. Vienuolis. Fluctuation processes in radio receiving devices. M: Swradio, 1951.

5. Uneroded. Pulse technique. M.: Higher school, 1984.

6. Amorality and other Broadband balanced modulators microwave. Electronic engineering, series 1, 9, 1984.

1. The simulation signals for testing tracking systems impulse radar (SAR)based on the reception on a moving target fluctuations of incident radar and signal for controlling on-Board sensors, the radiation in the direction of the same radar two signals separated in frequency by an amount equal to the first intermediate frequency (ω_CRRadar, characterized in that changing the delay of received impulses in the direction of increasing ("pulling forward") to the value corresponding to the selected false-range form of the detainees fluctuations by balanced modulation of the first and second components of the two-frequency signal separated by the frequency of these fluctuations on the value ofchange the phase of both components at a constant speed greater than the band pass is of the first amplifier intermediate frequency radar, generate a voltage type square wave with a frequency greater than the bandwidth tracking meter range radar, changing the phase of one of the formed component relative to another leap from zero to 180° with a frequency formed by meander, simultaneously with the formation of two-frequency component of the signal to modulate the delay on the wrong range, for example, the harmonic law, and the phase difference modulated delay when going from even to odd half cycles of the meander back and constant support.

2. The method according to claim 1, wherein remember the frequency received from the radar of radio EGR on a specified number of turns to form the stored packets of signals, detects the received impulses, delay proyektirovaniye pulses, change the delay time in accordance with the desired law, and detained videoanalyse strobert memorized packs of radio signals.

3. The method according to claim 1, wherein the pre-modulate the control signal in amplitude or phase voltage of frequency equal to half the first intermediate frequency radar.

4. The method according to claim 1, characterized in that the filter and detects the accepted control signal, separated from proyektirovanive voltage reference signal with a frequencyproduce continuous oscillation , sync is nezirut the resulting oscillation of the selected reference signal, shift in phase, used for balanced modulation dephased synchronized oscillations as a modulating voltage.