Method of controlling of an airborne mono impulse radar station with a built-in unit and an arrangement for its realization

FIELD: the proposed inventions refer to radiolocation technique namely to the methods of controlling of an airborne mono impulse rocket radar stations installed on the bearers with a built-in unit.

SUBSTANCE: the essence is in that in the reference point of the bearer of the rocket or of the streamlined antenna cover a sound is installed. It is made in the shape of a half-wave antenna whose arms are linked up to a nonlinear element. At receiving the order «Control» the transmitter of the airborne mono pulse radar station forming super high frequency vibrations on the carrier frequency f_c is connected with the power detector and its power is evaluated, vibrations on the super high frequency f_o which is in n times less than the frequency f_c are created and delayed in time relatively to the super high signals of the transmitter of the frequency f_c and the sound reradiating the signal on the frequency f_c is exposed to them. These signals are received and processed with standard facilities of the airborne mono impulse radar station, the imitated distance, the angle α of the azimuth and the place β are measured and compared with the specified parameters and decision about the efficiency of the airborne mono impulse radar station is accepted if the power of the transmitter is no less than admissible and the differences of the specified and the measured angles α and β do not exceed the admissible meanings.

EFFECT: increases reliability and secretiveness of controlling with a built-in unit.

4 cl, 3 dwg

The present invention relates to radar systems and can be used in the development of devices built-in control airborne monopulse radar stations (MPLS), which is implemented as a coherent and non-coherent signal processing.

Known ([1], p.150-151, RES) method of the built-control radar (radar), consisting in the fact that switch "Operation-control the output of the transmitter is disconnected from the antenna input is connected to series-connected directed coupler and the agreed load, include connected to the output of the mixer system of automatic frequency control) the control device, providing circulation of pulses of intermediate frequency f_CRfor receiving the delayed pulse transform using a local oscillator that generates a frequency f_gand mixer to a frequency in a microwave oscillation frequency f_m=f_g+mf_CRwhere m=1...n, serves these SHF oscillations through valves, directional coupler, a switch Operation Control and protection device of the receiver to the input of the mixer signal and estimate the energy potential of the radar and the accuracy of the measurement range.

The disadvantage of this method of organization of internal control MPLS is that he is unfit for the built-con who pose a coherent MBRLS, since the frequency of the transmitter and lo, decoherent and incoherent MPLS is estimated only energy potential and the ranging channel and not validated measurement error of azimuth angles α and place βyou make the antenna and the structure (waveguide bridges) sum and difference channels MBRLS.

Closest technical solution to eliminate this disadvantage, a method implemented in [2] and consists in the fact that enter the generator internal control signal (VCS) and the control of the defendant, which set out the ground radar at the point the azimuthal coordinate α_ewhich is known with high accuracy, fail to control the defendant the transmitter signal is measured by means of standard radar azimuth angle α_andthe control of the defendant, compare it with the known value of the azimuth angle control of the defendant α_eand calculates the phase error Δ=|α_e-α_and| pass-through channels, trying to eliminate by means of radar or take into account the subsequent processing of information about the measured angles of azimuth α and place β.

This method is based on the fact that, as shown in [3], pp.5-37, the measurement results of the antenna directional diagram (BOTTOM) in the far zone are consistent with the measurements of the BOTTOM when you install auxiliary antenna (AOR is Yes) in the near zone, if:

where S is the area of the probe, scanning probe test antenna;

λ - wavelength radar;

E - remove the probe from the plane of the aperture of the aperture of the investigated antenna.

When the radar operation in the 3-cm range of the radio waves these requirements boil down to the fact that S≤56 mm²and D≥300 mm, i.e. these requirements to the probe and the place of its installation can be performed if the probe is poluvalmovye vibrator (dipole), with the length of the vibratorsmm and a diameter of 2 mm, i.e. the cross-sectional area S=2·7,5·2=30 mm²and installed at a distance of D=300 mm, However, the feeder, which is supplied microwave energy to the probe, can make a significant distortion of the BOTTOM.

Therefore, the preferred method implemented in [4] (prototype), when the probe is made in the form of a dipole, set in the point whose coordinates are known with high accuracy, is exposed to the microwave signals of the control of the generator, which can be used and detained SHF oscillations of the transmitter MBRLS, takes the reflected probe signals measured elevation angles and azimuth dipole, compare them with the known and calculated errors of measurement of the angles of azimuth α and place β.

The disadvantage of this method built-in control MBRLS installed on missiles is, is the fact that in addition to the signals reflected from the dipole antenna MBRLS after installing missiles on the carrier (ship, submarine or aircraft) will receive signals reflected by the structural elements of the media that may lead to measurement errors of the potential angles of azimuth and places. In addition, in some cases, restrictions on the secrecy of inspections that it is not possible to irradiate the probe microwave oscillation frequency MBRLS.

The aim of the invention is to increase the completeness, accuracy and secrecy of the embedded control airborne monopulse radar stations upon maintenance or pre-flight checks MBRLS after installing missiles, which includes MPLS, to the media.

This objective is achieved in that the probe is made in the form of a half-wave vibrator, whose shoulders are connected to the nonlinear element, and set at the clearing point of the carrier rocket or fairing antenna, connect the switch to the "Job Control" transmitter output MPLS generating microwave oscillations of frequency f_cto the power detector, the transmitter MBRLS and appreciate its power, generate microwave oscillations whose frequency f_on times less than the frequency f_ckeep them relatively microwave oscillations transmit the ICA, to reinforce them, filtered and irradiated them probe, take regular means airborne monopulse radar pereizlucheniya nonlinear microwave probe oscillation frequency f_cto measure distance, angles of azimuth location and installation of the probe, calculate the measurement error range of angles of azimuth and places, memorize them and make a decision about the health airborne monopulse radar station, if the transmitting power is not below the target, and the measurement error range of angles of azimuth and places less valid.

The essence of the proposed method built-in control MPLS is that to increase the completeness of control, secrecy and the effects of the structural elements of the carrier rocket, which has MBRLS, the probe is performed in the shape of a half-wave vibrator, whose shoulders are connected to the nonlinear element, set the probe at the clearing point of the Radome or substrate, is irradiated with the probe microwave oscillations, the carrier frequency f_owhich is n times lower than the carrier frequency f_cMBRLS, accept and process microwave signals radiated by the transmitter at frequency f_c.

In this case, the reflection of the structural elements of the carrier occurs at a frequency f_othat is significantly weakened by the receiver and does not affect the work of the MDBs is C.

Comparison of the proposed method built-in test with the prototype shows the presence of additional steps:

- installation at the clearing point of the Radome or media probe in the form of a half-wave vibrator, the shoulders of which is connected to the nonlinear element;

- install auxiliary antenna, radiating the microwave oscillation frequency f_o;

- the formation of microwave oscillations, the carrier frequency f_on times smaller than the carrier frequency f_ctransmitter;

the delay of these fluctuations by using solid state delay lines, their subsequent amplification, filtering, and summarizing to the auxiliary antenna;

- irradiation probe detainees vibrations emitted by the auxiliary antenna;

reception staff antenna pereizluchennykh probe microwave oscillations at a frequency f_c;

- measurement of angles of azimuth and place of installation of the probe and the simulated range;

- calculation of errors of determination of range, azimuth angles and places.

The introduction of such actions to increase the completeness of the control MBRLS from publicly available sources is not known, which allows to make a conclusion on the conformity of the proposed method and device for its implementation the criterion of "Novelty".

Newly blocks required for the implementation of the proposed method, known and described in the technical literature.

In ka is este selector switch "Operation Control" can be used as a mechanical device, described in [1], p.150-151, and device pin-diode [6], p.50-71. Frequency dividers are described in [7], solid state delay line in [8], s. As the power amplifier can be used by domestic quasimonotone integral modules of type H, each of which has a gain of 16 dB [9], pp. 102-103.

As an auxiliary antenna can be used strip antenna.

The probe can be made in the form of a half-wave vibrator, shoulder length l which is chosen in accordance with [5] from the condition

l=(0,2-0,7)λ₀,

where C is the speed of light.

As a non-linear element, to which are connected the shoulders of the half-wave vibrator may be used in any microwave diode, designed for use as a multiplier at frequencies above the frequency f_c.

The essence of the proposed invention is illustrated further by the description and drawings, in which example the technical realization of the proposed method of carrying out the built-in control MBRLS, confirming the possibility of its industrial applicability the following:

- figure 1 - functional diagram of the built-in control MPLS;

- figure 2 is a functional diagram of the device built-in control MBRLS, in which for forming the emitted frequency f_cnot skin which is the multiplication of the reference frequency;

- figure 3 - functional diagram of the built-in control MBRLS, in which the emitted frequency f_cobtained by multiplying the frequency of the oscillator reference signal.

Figure 1 applied the following notation:

1 - antenna (A);

2 - antenna Radome (AO);

3 - probe nonlinear element (SNA);

4 - switch transfer (SPT);

5 receiver (PFP);

6 - transmitter (send);

7 - switch "Operation Control" (GOK);

8 - transmitter-exciter (BB);

9 - antenna control unit (ACU);

10 - solid state delay line (TTLS);

11 - power amplifier (PA);

12 - low pass filter (LPF);

13 is an auxiliary antenna (VA);

14 - power detector (DM).

Communication between these blocks correspond to the one presented in figure 1. Dashed lines marked by wireless.

In figure 2 the following notation:

1 - antenna (A);

2 - antenna Radome (AO);

3 - probe nonlinear element (SNA);

4 - switch transfer (SPT);

5 receiver (PFP);

6 - transmitter (send);

7 - switch "Operation Control" (GOK);

8 - transmitter-exciter (BB);

9 - antenna control unit (ACU);

10 - solid state delay line (TTLS);

11 - power amplifier (PA);

12 - low pass filter (LPF);

13 is an auxiliary antenna (VA);

14 detector m is snasti (DM);

15 - directional coupler (BUT);

16 - switch ();

17 is a frequency divider by n (QH);

18 - band-pass filter (PF).

Communication between these blocks correspond to the one presented in figure 2. Dashed lines marked by wireless.

Figure 3 the following notation:

1 - antenna (A);

2 - antenna Radome (AO);

3 - probe nonlinear element (SNA);

4 - switch transfer (SPT);

5 receiver (PFP);

7 - switch "Operation Control" (GOK);

8 - transmitter-exciter (BB);

9 - antenna control unit (ACU);

10 - solid state delay line (TTLS);

11 - power amplifier (PA);

12 - low pass filter (LPF);

13 is an auxiliary antenna (VA);

14 - power detector (DM);

15 - directional coupler (BUT);

16 - switch;

19 is a frequency multiplier (UCH);

20 - power amplifier channel transmitter (umcp);

21 - synthesizer frequency (MF).

Communication between these blocks correspond to the one presented in figure 3, while the dotted lines depicted by wireless.

Built-in control is performed in the following way (figure 1). BB 8 generates a signal of carrier frequency f_cthe start-up pulses of the transmitter FROM entering transfer 6, the signals of the local oscillator (s) f_gand the reference frequency f_PTSarriving at the PFP 5, and the signals frequently what you

where n is the division ratio of the frequency, n=2, 3, 4.

Oscillations of frequency f_oare formed simultaneously with the pulse OF only when input 2 BB 8 commands "Control". When you receive the command "Control" TEP 7 connects the output of FTEs 6 to DM 14 that generates the voltage U_mproportional to received power and received at the first input of 8 CENTURIES, forming a signal about the health of the transmitter 6, if U_mexceeds a threshold level corresponding to the minimum allowable radiated power P_min.

Signals of frequency f_ofed to the input of TTLS 10, delayed by the time corresponding to, for example, the minimum measured distance MBRLS, strengthen the MIND 11 and filter LPF 12, designed to attenuate harmonics of frequency f_oappearing at the output of the MIND 11, radiate VA 13 and is exposed to SNA 3, which are preferably mounted on the fairing 2 antenna 1, while respecting the relation (2). If the relation (2) is not met, then should the probe be placed in the clearing point of the carrier remote from the plane of the aperture at a distance D≥10λ. Irradiated probe pereizuchit response signal at frequency f_c=nf_othat is received by the antenna 1, is amplified by the receiver 5 and is processed CENTURIES 8.

Thus, by using additional is introduced compulsory units 3, 10, 11, 12 and 13 are formed of microwave signals delayed relative to the signal transmitter 6 at a time determined by the delay time TTLS 10, and coming from a certain direction. These signals are received by the antenna 1 via the SPT 4 arrive at PFP 5, amplified, converted in accordance with the standard algorithms and arrive at the third entrance CENTURIES 8, which determines the range of D_uthe angles of azimuth α_uand place β_uand calculate the errors of their measurement as

ΔD=D_p-D_u;

Δα=α_p-α_u;

Δβ=β_p-β_u;

where D_pthat α_pand β_p- calculated values of range, azimuth angles and positions, respectively.

These errors can be tested or reported during normal working MBRLS.

Rate if applicable to the blocks of the requirements needed to implement this method, the built-in control.

In accordance with the method described in [5], p.7-14 adopted by the antenna 1 signal R_greatat a frequency f_cfor example , when n=2, can be defined as

where R_[Izl], G_[Izl]the power emitted by the auxiliary antenna, and the rate of gain, respectively;

G_a- gain antenna MBRLS at frequency f_c;

λ_about- wavelength signal is La, radiated auxiliary antenna;

where C is the speed of light;

r is the distance between the nonlinear element and the auxiliary antenna;

G_{melody Ave}, G_melody)- gain antenna of the transmitter at frequency f_oand f_c, respectively;

ξ₂(λ_about, R_CR- the coefficient of the nonlinear transformation, depending on the capacity of P_CRacting on the nonlinear element of the probe 3.

In this expression, the first fraction is a power of P_CRcoming to the nonlinear element, and an expression enclosed in square bracket is that it generates power.

In first approximation we can assume that G_{melody Ave}=G_melody)and

where K - coefficient depending on the type of nonlinear element and impinging frequency; according to [5] K=2·10^-5.

Taking into account (4) expression (3) is

After transformation of the expression (5) we get the following formula for calculating the power P_[Izl]emitted from the auxiliary antenna 13

We assume that the probe is classic poluvalmovye vibrator, the shoulders of which is connected to the diode, and having a length shoulder, able to accept oscillation frequency f_{o/sub> and to radiate oscillations of frequency fop.}

Take G_{melody Ave}=G_melody)=5, G_a=300, r=0.3 m, R_great=2·10^-12W λ_about=6 cm, G_[Izl]=10.

Then

Such radiated power on the nonlinear element comes power

If to consider, that the new BB 8 power oscillation frequency

and attenuation TTLS 10 is 50 dB (N_TTLS=10^-5), to obtain the output power P_[Izl]=0.1W gain of the amplifier must be at least

or 10·lg_y≈50 dB.

Obtaining such gain is not difficult. The basic error of measurement of the potential of the N_sweatMRLS are error N_qDM 14, instability N_mgain MIND 11, the instability of the N_Cattenuation TTLS 10 and the instability of the N_tothe K-factor of the probe 3.

Considering that these errors are independent, you can get

If, for example, N_q=N_m=N_C=N_to=3 dB, N_sweat=6 dB, which is close to the error of the estimate of potential known methods and may be reduced, if necessary.

The basis is a great advantage of the proposed method built-in control is without the radiation at the fundamental frequency f_cwhich in some cases is not allowed, determined by the measurement error of the angles of azimuth and places made antenna, the non-identity characteristics shapers signals sum and difference channels, and errors of the ranging channel.

The proposed method can be applied to control MPLS using as a simple signal, and complex signals (vnutriklubnoy linear frequency and phase modulation).

Functional diagram of the device that implements the proposed method built-in control incoherent MBRLS shown in figure 2.

Built-in control is performed as follows. When you receive the command "Control" TEP 7 connects the output of FTEs 6 through 15 to DM 14 and the switch 16 connects the second output BUT 15 to the input QH 17. When you enable send his 6 SHF oscillations of frequency f_withthrough output 1 BUT 15 come on DM 14 forming the voltage U_mproportion to the input power and input 2 8 CENTURIES, creating a signal of the health of the transmitter, if U_m≥ threshold voltage.

Remove from exit 2 BUT 15 SHF oscillations through the switch 16 is received on 17 QH performing the division of the frequency f_cn times. The output signal QH 17 frequencythrough the bandpass filter 18 post the AET on TTLS 10, is delayed by the time corresponding to the minimum measured distance MBRLS, strengthens the MIND 11, are filtered in low-pass filter 12, and is radiated by the auxiliary antenna 13 and irradiates SNA 3 containing a nonlinear element, forming a harmonic frequency f_o.

Harmonic frequency f_oequal to the signal frequency f_c, is received by the antenna 1 and through the SPT 4 arrives at PFP 5, amplified, converted and processed in accordance with the standard algorithms. The processing results received on BB 8, which determines the range of D_IRthe angles of azimuth α_IRand place β_IRand calculates the errors of their measurement as

ΔD=D_p-D_IR;

Δα=α_p-α_IR;

Δβ=β_p-β_IR;

where D_pthat α_pthat β_p- calculated values of the range of elevation angles and azimuth, respectively.

The calculated error can be stored in 8 CENTURIES and taken into account when the standard work on the real purposes when the control loop is given information

D=D_and-ΔD;

α=α_and-Δα;

β=β_and-Δβ,

where D_andthat α_andthat β_andaccordingly, the range of angles of azimuth and designated as measured at regular work for a real purpose.

The advantage of this method built-in control is what I'm tall weight control and secrecy.

However, as shown in [7], currently available frequency dividers having an upper frequency f_in=18 GHz.

Advances in microelectronics allow us to hope that the upper value of the frequency dividers can be increased up to 30-40 GHz that will allow you to use this method to check incoherent MBRLS operating in the mm range.

However, it should be noted that currently used, as a rule, coherent MBRLS, in which microwave signals are generated by multiplying and subsequent amplification of the signals generated by the frequency synthesizers, as described, for example, in [10].

In this case, the built-in control with the use of a probe with a non-linear element can be carried out according to the scheme given in figure 3. The device operates as follows. BB 8 generates the start-up pulses FROM the transmitter and continuous oscillations of the reference frequency f_PTSunder the action of which MF 21 generates the frequency (frequencies) of the local oscillator (lo) f_G1f_T2and during the action OF the pulses of microwave oscillations at a frequency ofthat through the first output BUT 15 arrive at UCH 19. Remove from the output UCH 19 microwave frequency oscillations of f_cincrease umcp 20 and are fed through the GOK 7 to DM 14 forming the voltage U_mproportional input is Amnesty and supplied to the second input CENTURIES 8, outstanding signal the health of the transmitter, if U_m≥ threshold voltage.

Remove from the second output BUT 15 signals of frequency f_ocome on switch 16, the second input is in the "Control" control voltage at which its attenuation is minimal. Remove from the output of the switch 16 signals through TTLS 10 are brought to MIND 11, amplify them, are filtered in low-pass filter 12 is fed to the auxiliary antenna 13, irradiating the probe 3. Pereizlucheniya them signals are received by the antenna 1 and through the SPT 4 arrives at the receiver PFP 5, amplified, converted in accordance with the standard algorithms and arrive at 8 CENTURIES, which determines the range of D_IRthe angles of azimuth α_IRand place β_IRand calculates the errors of their measurement as

ΔD=D_p-D_IR;

Δα=α_p-α_IR;

Δβ=β_p-β_IR

where D_pthat α_pand β_p- calculated values of the range of elevation angles and azimuth, respectively.

These errors can be accounted for during normal working MBRLS, as well as when controlling a non-coherent radar.

The proposed device built-in control of coherent MPLS can be performed on modern domestic element base and its implementation increases full control and not p is iveget to a significant increase in volume and mass.

The practical implementation of the proposed method will not cause special difficulties associated with the placement of the probe.

Literature

1. Davydov PS Technical diagnostics of electronic devices and systems. - M.: Radio and communication, 1988, p.150-151.

2. Monopulse radar. Patent RU (II) No. 2183329 (13) C1 CL G 01 S 13/44, 7/40, N 0103/00 on the application 2000127072/09 from 23.10.2000.

3. Jackson and other Determination of the radiation patterns of the antennas according to the measurement results in the near zone /TIER. - 1973, T No. 12, pp.5 - 37.

4. Device for measuring the phase and amplitude of the electromagnetic field in the near zone of the studied antenna. Copyright certificate №1670629 (USSR), class. G 01 R 29/10 on the application 4639586/00-29(22) from 19.01.89. Inventions of the world. Abstract journal. Issue 85, MKI G 01 P, S No. 21 (1991), S.11.

5. Vershigora NS and Kuznetsov T.V. TO the question of the comparison principle in nonlinear radar / Informal. Electronics and telecommunications, 2002, №3 (21), p.7-14.

6. Weisblatt AV Switching devices microwave semiconductor diode. - M.: Radio and communication, 1987, p.50-71.

7. G_aA_sHBT MMIC/DIVJDE-BY-2DC-13 GH_zWWW.nitlite/com.

8. Gassanov L.G. and other Solid state devices, microwave communications engineering. - M.: Radio and communication, 1988, s.

9. Garmash SV and other passive integrated circuits on gallium arsenide structures in microstrip microwave modules. Abstracts of the 2nd all-Russian is Auce-technical conference on the development of advanced avionics. - Tomsk, April 15-17, 2003, pp. 102-103.

10. Monopulse radar tracking. RF patent №2114444 (13) p.1 CL 6 G 01 S 13/44, 27.06.98 on the application 97112846/09 15.07.97.

1. The way the built-in control airborne monopulse radar missiles mounted on the carrier, which consists in the installation of the probe at a point, angles and azimuth location of which is known, the irradiation of the microwave probe fluctuations, taking pereizluchennykh of signals, measurement of angles and azimuth location of the probe and determining the accuracy of their measurement, characterized in that the probe is made in the form of a half-wave vibrator, the shoulders of which is connected to the nonlinear element and set at the clearing point of the carrier rocket or Radome with a value range of D_p, azimuth angle α_pand elevation β_pswitch "Operation-control the output of the transmitter airborne monopulse radar station, generating microwave oscillations of frequency f_c, connect to the power detector, the transmitter and appreciate its power, generate microwave oscillations whose frequency f_on times smaller than the carrier frequency f_withvibrations generated by the transmitter, hold them relative to the microwave oscillations of the transmitter, irradiate them probe, when imaut pereizlucheniya probe microwave oscillations at the frequency f _cto measure the time delay of the received signal, the range of D_andthe azimuth angle α_andand the angle β_andprobe, calculate the errors of their measurement as ΔD=D_p-D_andthat Δα=α_p-α_andthat Δβ=β_p-β_andand make a decision about the health airborne monopulse radar station, if the transmitting power is not below the target, and the measurement error range of angles of azimuth and places less valid.

2. The device built-in control airborne monopulse radar station containing serially connected switch "Job control" and a directional coupler, the input switch "Job control" is connected to the transmitter output and the second output - to-input transfer airborne monopulse radar station, characterized in that the input power detector probe in the form of a half-wave vibrator, whose shoulders are connected to the nonlinear element, installed at the clearing point of the carrier rocket or fairing antenna switch connected in series, a frequency divider, a band-pass filter, solid state delay line, a power amplifier, a low pass filter and the auxiliary antenna irradiating the probe, the input of the power detector is connected to the first output on ravenage tap, and the output to the second input of the transmitter-exciter airborne monopulse radar, the first input switch connected to the second output of the directional coupler, and the second input switch "Work control, switch and power amplifier command "Control".

3. The device built-in control airborne monopulse radar station that contains a directional coupler and switch "Operation control", whose input is connected to the output of the amplifier channel transmitter, and the first output - to-input transfer airborne monopulse radar, characterized in that the input power detector probe in the form of a half-wave vibrator, whose shoulders are connected to the nonlinear element, installed at the clearing point of the carrier or of the Radome, connected in series circuit breaker, solid state delay line, a power amplifier, a low pass filter and the auxiliary antenna input power detector connected to the second output of the switch "Job control"and the output to the second input of the transmitter - exciter airborne monopulse radar, the input of a directional coupler connected to the output of the frequency synthesizer, the first output to the input of the frequency multiplier, the second output to eromu the input of the switch, but on the second inputs of peracetates "Work control, switch and power amplifier command "Control".