Method of adjusting output parameters of superregenerative transceiver of radiosonde |
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IPC classes for russian patent Method of adjusting output parameters of superregenerative transceiver of radiosonde (RU 2470323):
           
 Device for measuring vertical component of wind velocity for detecting wind shift / 2468387
Device for measuring the vertical component of wind velocity in order to detect wind shift has a wind shift detector, a transmitter, two receivers, two circulators, two antennae, a digital signal processor, an antenna angular position sensor, a cross-correlation function derivative computer, a device for determining the position of the minimum of the cross-correlation function derivative, a power divider, a differentiator, an adjustable delay unit, a multiplier, a low-pass filter and a low frequency amplifier.
 Method of estimating accuracy of doppler radar wind profile / 2460091
Method of estimating accuracy of Doppler radar wind profile (DRWP) includes one radiosonde radar weather station, based on synchronous probing of the atmosphere by the DRWP and a standard meteorological apparatus (MA), where the speed and direction of wind are measured, the DRWP and MA obtain several results which are fed to a computer. The mean-square error of the DRWP in measuring speed and direction of wind is determined based on equal accuracy of measurements with given confidence probability. The disclosed invention is characterised by making the MA in form of two identical radiosonde radar weather stations, the wind speed and direction measurement results of each of which form the first outputs are fed to the second and third inputs of the computer where they are averaged. The difference in results is taken, transformation is performed and the accuracy of the DRWP in measuring speed and direction of wind is determined based on a corresponding mathematical relationship.
Method of determining sea ice draft and system to this end / 2453865
Invention relates to marine hydrometeorology and may be used for determination of sea ice draft. Drifter equipped with transceivers of satellite communication and hydro acoustic navigation systems is used to define coordinates of ice fields. Displacement of ice field relative to reference points is tracked and displayed on monitor. Note here that potentially dangerous ice fields are revealed as well as approach distance and time store to make decision about their localisation. Said decision are made with due allowance of ice field thickness defined by sounding with the help of sonar mounted aboard the airship. Proposed system comprises drifter, producing offshore platform and sonar mounted on rigid-frame airship. Drifter is made up of telescopic cylindrical vessel made from Macrolon. Drifter top section accommodates aforesaid transceiver while it bottom section houses transceiver of hydro acoustic hardware. Said drifter operateds in ''call-reply'' mode and ''pinger'' mode (beacon). For reliable fixing of drifter in holes on ice surface, spacers made up of set of needle passages are made at top section of cylindrical vessel. Producing offshore platform is equipped with transceivers of aforesaid systems, antennas, navigation controller and software. Said sonar mounted aboard the airship serves to define ice field thickness.
 Panoramic radar method of determining parameters of state of ocean surface layer from satellite / 2449312
Knife-edge beam of the antenna is rocked relative the vertical in a direction perpendicular to the direction of motion and each probe pulse is used to illuminate a 14x355 km spot on the water surface (at altitude of 800 km). Reflected pulses are received using time gating on the range based on the Doppler shift sign to select in said 14x355 km spot elementary scattering cells (ESC) measuring, for example, 14x14 km. Using a synthesis procedure along the direction of motion of the satellite, the backscattering section is determined and the water surface slope dispersion in each ESC is reconstructed. Further, by selecting the azimuth angle, the water surface slope dispersion along said direction is reconstructed and, by analysing the azimuth dependency of slope dispersion in each ESC, the direction of wave propagation in each cell is determined. The speed of surface wind V in each ESC is determined using an algorithm obtained using a regression method. In a special case of the method, average values of the rough sea and wavelength of a big wave are also determined.
 Method for remote measurement of wind speed and direction / 2449311
Reflector comprises a modulator-reflector 2, a system 3 of angle reflectors, a stabiliser 4 of plane of rotation of angle reflectors (a flag), a modulator support 5. The device to detect speed and direction of wind installed on a helicopter 6 comprises a transmitter 12, a duplexer 13, a transceiving antenna 14, receiving antennas 15 and 16, amplifiers 17, 22 and 23 of high frequency, a heterodyne 18, a mixer 19, an intermediate frequency amplifier 20, a meter 21 of amplitude modulation depth, multipliers 24, 25, 28, 36 and 38, bandpass filters 26 and 27, narrow band filters 29 and 37, a delay line 30, a phase detector 31, a phase meter 32 and 33, a reference generator 35, kinematically connected to a motor of the helicopter 34, a meter 39 of Doppler frequency and a processor 40.
 Method of monitoring vertical distribution of ionospheric electron concentration / 2445652
Group consisting of not less than two satellites lying in the same orbit plane is formed such that zones of mutual radio-visibility of the satellites are within the ionosphere. Not less than two coherent electromagnetic waves at different frequencies are emitted from at least one satellite. The phase difference between these electromagnetic waves after passing through the ionosphere is recorded on at least one satellite. The full electron content of the ionosphere on the propagation path of the waves is determined from the obtained phase difference value.
 Method of determining absolute ion concentration of earth's ionosphere / 2437117
Method involves transmitting coherent radiation from a low-orbit man-made earth satellite and measuring phase delays of the radiation wavefront after passing through the earth's ionosphere, where coherent narrow-band radiation is simultaneously transmitted from the man-made earth satellite at three frequency bands with central frequencies - 150, 400 and 2844 MHz. Two mutual phase delays Δφ12 and Δφ13 and signals 150-400 MHz and 150-2844 MHz are simultaneously measured and the full electron concentration is calculated from the difference in delay using the following relationship:
 Method of determining velocity field of air mass via high-resolution doppler analysis / 2421754
Disclosed is a method for spectral analysis of a remotely discretised periodic radio signal using a latticed autoregressive Burg filtration algorithm, through which fundamental frequencies of the received signal are determined for each group of distances by determining the optimum set of reflection coefficients µn of the signal. Reflection coefficients are the object of regulation for the purpose of limiting instability of the numerical solution of calculations. The regulated coefficients are used to estimate the current order of the identification model of the lattice filter and to determine fundamental frequencies of the signal by calculating independent variables of complex roots of a polynomial which displays the transfer function of the lattice filter. For each group of distances, it is determined which of the fundamental frequencies is the Doppler frequency of the air mass for that group. The method also includes spatial smoothing of reflection coefficients before determining the current order of the model and looking for the root of the polynomial. The disclosed method can be used for high-resolution spectral analysis when it has to be executed based on a small number of signal samplings.
 Method of determining ionosphere characteristics and device for realising said method / 2421753
Radio signals are received from navigation satellites at two coherent frequencies F1 and F2. Pseudo-ranges DF1 and DF2 to the navigation satellite, measured at frequencies F1 and F2 respectively are determined from the received radio signals. The obtained values are used to calculate the difference between pseudo-range values ΔD12. The full electron concentration Le along the "satellite-ground" point route is determined. Electron concentration of the ionosphere N(z) in the region for measuring the altitude profile is determined. Phase values ψF1 and ψF2 of the received radio signals are measured. The difference between pseudo-ranges ΔD12 is determined taking into account phase values ψF1 and ψF2 of the received radio signals. An iterative procedure for solving the inverse problem is applied, where the said procedure is based on using a method of conjugate gradients and a priori information on the background state of the ionosphere to determine electron concentration of the ionosphere N(z) in the region for measuring the altitude profile. The device for determining electron concentration of the ionosphere has an antenna for receiving radio signals from navigation satellites, the output of which is connected to the input of a double-frequency receiver of satellite navigation systems of the GLONASS and/or GPS type. The device also has a processing and display unit whose input is connected to the output of the double-frequency receiver. The processing and display unit is adapted to determine said parameters.
 Method for complex target location / 2416108
Method for complex target location is based on emitting high-frequency pulses using optical and radio band channels, where said signals are emitted synchronously and have the same duration. The novelty lies in that the known scattering matrix of the target or known scattering matrix of the underlying surface of the target is used to generate probing signals with variable polarisation, contrast of the located space is determined from the reflected signal, polarisation is changed until maximum contrast signals of the target are obtained in both location channels, from which the coordinates and type of the target are determined.
 Method nd device for measuring electron concentration at specific region of ionosphere / 2251713
Method and device can be used for measuring concentration of electrons in specific region of ionosphere plasma which depends on presence and concentration of radioactive impurities in the region of atmosphere to be observed. Device has synchronizer 1, transmitter 2, transmitting aerial, time delay unit, two receiving aerials, right and left circular polarization wave receivers, two switches, heterodyne, mixer, intermediate frequency amplifier, five multipliers, narrow band filter, amplitude limiter, phase meter, computing unit, comparison unit, indicator, phase shifter, scaling switch, subtracter and adder.
 Method for determination of location of lightning discharge and multiple-point system for its realization / 2253133
The multiple-point system for determination of location of a lighting discharge has a data transmission network and sensors, central computing unit, control unit and user computers (according to the number of users) connected to it, superlong-wave independent lightning direction finders - range finders are used as sensors.
 Method for measuring thickness of snow cover / 2262718
Method is based physically on different penetrability level of snow by electromagnetic waves of different frequencies ranges, which is connected to dielectric snow characteristics. Method for measuring thickness of snow covering includes irradiation of snow cover at the same time by electromagnetic waves of centimeter range on bearing frequency f1, on which reflection occurs from limit between snow and soil, and electromagnetic waves of optical range on bearing frequency f2, on which reflection occurs from limit of separation of environments troposphere-snow, and determining of appearing difference of distances, passed by proving signals.
 Mode of sounding of atmosphere or ocean / 2267139
The technical result: simplification of realization of measuring, increasing their precision and also securing possibility of independent definition as the profile of the speed of the sound, so the profile of the index of reflection in atmosphere or in ocean. The essence: in the environment a movement of a sounding object is set up, a modulated acoustic or electromagnetic wave is directed on this object. The wave holds frequencies f1 and f2 and f1≥C/h and f2≤C/H, where C - a medium speed of the wave in the investigated environment, h - required space permission, H - a maximum distance of measuring, reradiated by the object. Corresponding relative Doppler shifts at various locations of the object are defined for frequencies f1 and f2 reradiated by the object. Attitude for these shifts is found. According to this attitude the vertical profile of the speed of the propagation of the wave is computed. Particularly an acoustic wave packet is chosen in quality of sounding object and a vertical profile of the speed of propagation of the electromagnetic wave is computed. The profile of the speed of the sound is defined along the profile of the shift of the frequency f1 with taking into account the profile of the speed of propagation of the electromagnetic wave. Particularly for various moments of time an integral shift of the phase of the wave reradiated by the object on the carrier frequency is found and along this shift a slant distance till sounding object is defined. Particularly along the parameters of received signals an azimuth and an angle of the place of the sounding object are found.
 Storms coordinates accumulator and a variant thereof / 2269792
Kinematic communication equations are solved not for aircraft-lighting flashes, but for aircraft-storm, and because storm coordinates are generated by averaging coordinates of all registered lightning flashes during several minutes, volume of computational operations is decreased manifold.
 Panoramic radar method of determining condition of ocean's layer surface from satellite / 2274877
Method can be used for measuring parameters of sea storm; it can be also used in meteorology and oceanology for distant probing of surface layers of oceans from board of satellite. Microwave range probing pulses are irradiated by Doppler radar. Probing pulses are directed to surface of ocean in nadir; any pulse irradiates spot with sizes of 14x355 km on water surface. When receiving reflected pulses, time and Doppler range selection is used simultaneously inside spot of 14x355 km for elementary dissipating particles with sizes of 14x14 km. Then cross-sections of back dissipation σ0(θi) and σ0(θi+1) are determined for any two sequent "I"-th and "i+1"-th elementary dissipating particles. The cross-sections correct and determine dispersion of inclinations σ2 i(φj). The total dispersion of inclinations σ2 i for "i"-th elementary dissipating particles is determined and direction of propagation φwi of large-scale storm in "i"-th elementary dissipating particle is found. Speed V of surface wind is found by means of algorithm f V=F[σo, σ2 i(φj), σ2 i(φj+90°)] calculated by standard regression method.
 Combined inbuilt control system and a variant thereof / 2277716
Combined inbuilt control system and its variant for storm locators, working in area of very low frequency electromagnetic fields, provides automatic, continuous control with given frequency of electric and magnetic antennas and storm detector channels appropriate for these by creating electric and magnetic fields, distributed in time, to make it possible to perform selection of lightning discharge pulse in two variants of selector circuit construction and to block control circuit automatically for time of lightning discharge pulse processing. Utilization of combined inbuilt control system in equipment makes it possible to increase fullness of storm locator control due to controlling through space of both magnetic and electric antennas, while preventing miss or distortion of lightning discharge processing pulse results when it coincides in time with control pulse.
 Super regenerative transceiver / 2291467
The super regenerative transceiver has a generator of superior impulses, a master oscillator, a source of feeding and an antenna. At that there is introduced in it a diode and in series introduced a line out of a constant resistor, an alternate resister and a condenser. At that the input of the line is connected with the output of the generator of superior impulses, the output - with the input of the launching of the main oscillator, and the common point of the constant and the alternate resistors is connected with null volt of the source of feeding through directly switched diode, the generator of superior impulses and the main oscillator are connected with the plus and the null of the source of feeding, and the output of the main oscillator through antenna is the output of the super regenerative transceiver.
 Method of measuring size of hail's particles / 2292565
Sizes of hail particles are measured by means of two-wave meteorological radar. Radio location probing of atmosphere is carried out within area of precipitation. Radio location reflectivity is determined at wavelengths of 3,2 cm and 10 cm, which equals to η3,2 and η10. Sizes of hail particles is calculated by relation of d3=4,54(η3,2/η10) -0,502, where 4,54 and -0,502 are empiric coefficients. Path of melting of hail particles is determined by radio location method when particles move in atmosphere from zero isotherm level down - H (km). Sizes of hail particles to be found is determined by multiplication of calculated value d3 by correcting multiplier K, found from relation of K=Ha(η3,2/η10)bH, where a=-0,247 and b=0,055.
 Mode of definition of the width of the spectral density of power of radio signals of coherent meteorological radar / 2293351
According to the mode it is necessary to radiate periodically radio impulses into the researched field of atmosphere, to receive radio signals reflected from meteorological particles, to separate coherent and quadrature components of received radio signals reflected from meteorological particles, to form a complex signal uniting coherent and quadrature components of received radio signals reflected from meteorological particles, to calculate the correlation function of the complex signal. The indicated function is calculated in time points the intervals between whom are multiple to the period of repetition of radio signals. The width of the spectral density of power of the radio signals of the coherent meteorological radar reflected from meteorological particles is defined according to the relation:
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FIELD: physics, radio. SUBSTANCE: invention relates to radio engineering and can be used to adjust sensitivity and relative position of the receiving and transmitting frequency of superregenerative transceivers of aerologic radiosondes operating as part of atmospheric radiosounding systems. Disclosed is a method of adjusting output parameters of a superregenerative transceiver of a radiosonde based on optimum selection of the feedback factor of the self-oscillator of the superregenerative transceiver, load resistor, resonance frequency of the oscillatory system, characterised by that when launching the self-oscillator of the superregenerative transceiver, a mode for self-excitation with a hard character of the transient process of establishing self-oscillations is provided, average current and supply voltage of the active device of the self-oscillator of the superregenerative transceiver are stabilised, pulsed current of the control electrode - base of the transistor of the active device of the self-oscillator is controlled, thereby establishing reception frequency relative the carrier frequency of the self-oscillations of the superregenerative transceiver; by adjusting the slope of the exponentially rising leading edge and pulse duration, the required level of sensitivity of the superregenerative transceiver is set. EFFECT: providing separate adjustment of receiving and transmitting frequency and achieving maximum sensitivity of a superregenerative transceiver of an aerologic radiosonde to the request signal of a surface radar station. 8 dwg
The invention relates to electrical engineering and can be used in atmospheric radiosonde (ARP) radiosonde systems in the atmosphere to measure the distance to the radiosonde pulse method, bearing in angular coordinates and telemetry data transmission on a single carrier frequency can also be used to build highly stable and economical super regenerative radio transmitter / receiver devices, radar systems and communications. The national system of radio sounding of the atmosphere (CF) built on angular-distance measuring method of measuring coordinates, speed and direction of movement of the radiosonde in the free atmosphere. Measurement of angular coordinates: azimuth (β), elevation angle (ε), and slant range (RH) is radiopulse method with active response. Particularly effective was the use in the composition of radiosondes super regenerative transponder-responder (SPP). Intense radiation SPP provides reliable transmission of telemetry data and maintenance of the angular coordinates. High sensitivity SPP to radiopulse request signal allows to generate a response signal range in the form of a short pause in the emission of SPP at low power transmitter request of radio radar. Very important in konecne the m account is the fact that the positioning system and the transmission channel telemetry data radiosonde systems are operating at the same carrier frequency (see Viermal and other "System sensing of the atmosphere, Gidrometeoizdat, 1977, s-249). A common problem in modern ARZ is the difficulty of adjusting the output parameters of the super regenerative transponder (SPP) due to their mutual influence of complicating the configuration process in the production of, and does not achieve the optimal proportions of sensitivity and power output, the relative position of the frequency transmission and reception SPP. Also the problem of the production and operation of the RHA is the creation of inexpensive designs of transmitter-receiver pairs, stable radio parameters in conditions of changing pressure, ambient temperature, supply voltage and parameters of the antenna system ARP. There is a method of adjusting the lamp super regenerative transceiver ARP with a separate generator auxiliary oscillations by adjusting the carrier frequency, adjusting the time constant of the inertial chain avtomashine microwave oscillator and communication with the antenna used for receiving a request pulses and send the reply and telemetry signals (see Viermal and other "System sensing the atmosphere is s",; Gidrometeoizdat, 1977, s-259). The disadvantage is the impossibility of its use to configure the semiconductor SPP. There is a method of adjusting SPP radiosonde, which consists in tuning the resonance frequency of the vibrating system at the nominal value of the carrier frequency CAF, the selection of the magnitude of the resistive load of the microwave oscillator by changing the connection with the receiving and transmitting antenna ARP, adjusting the time constant of the inertial chain avtomashine microwave oscillator by changing the values of the output resistance of the generator superimage voltage in the circuit of the base of the transistor microwave oscillator (see the patents of the Russian Federation No. 2172965, No. 2214614). There is a method of adjusting SPP radiosonde, which consists in tuning the resonance frequency of the vibrating system at the nominal value of the carrier frequency CAF, the adjustment of the coefficient of the feedback in the microwave oscillator SPP, the selection of the magnitude of the resistive load of the microwave oscillator by changing the connection with the receiving and transmitting antenna ARP, adjusting the time constant of the inertial chain avtomashine microwave oscillator by changing the values of the output resistance of the generator superimage voltage in the circuit of the base of the transistor microwave cogenerator (see RF patent №2291467 - PROTOTYPE). A disadvantage of the known solution methods, and PROTOTYPE is a significant interdependence of the carrier frequency SPP adjust the sensitivity by changing the values of the output resistance of the generator superimage voltage circuit is included in the base transistor UHF cogenerator. An object of the invention is to improve the accuracy of the tuning frequency transmission and reception, as well as the sensitivity of the SPP due to the exclusion of their mutual influence when configuring ARP in production by: - create a circuit technical and constructive solutions to eliminate the influence of the sensitivity adjustment of the mutual offset of the receive frequency and the carrier frequency CAF when configuring in the conditions of mass production, thereby increasing the sensitivity, the radiation power and stability of the super regenerative mode of the transceiver; - improve technological settings SPP and reduce the cost of production of radiosondes. To solve this problem is proposed a method of adjusting the output parameters of the super regenerative transponder radiosonde, based on the optimal choice of the feedback factor of the super regenerative oscillator transceiver, resistance load, the resonant frequency of the vibrating system at the start of the super regenerative oscillator transceiver can provide a self-excitation mode with the hard nature of the transition process of establishing self-oscillations stabilize the average current and voltage of the active device of the oscillator swerr the generative transceiver, adjust the pulse current of the control electrode is a base of the transistor active device of the oscillator, thereby to set the reception frequency relative to the carrier frequency of self-oscillations super regenerative transceiver, the adjustment of the slope of the exponentially rising leading edge and pulse duration generator superimage voltage (GOS) establish the required level of sensitivity super regenerative transponder. To explain the essence of the present invention, the following structural and electrical diagrams and graphics: figure 1 - Structural diagram of the super regenerative transceiver upper-air radiosonde; figure 2 - Dependence of the attenuation circuit of the microwave oscillator the amplitude of self-oscillations; figure 3 - signal Waveforms illustrating the principle of operation of the SPP with the rigid character of the establishment of self-oscillations acting at different points SPP; 4 is a Graphic illustrating the principle of unstressed run the microwave oscillator SPP; figure 5 - a) is a Graph of the frequency of self-oscillations in the mode setting process of self-oscillations; b) is a graph of the pulse current of the emitter of microwave transistor in the process of establishing self-oscillations; Fig.6 - a) Form supereroi of pulses at the output of the SHG SPP when adjusting the time constant of the filter the low frequencies at the input of the emitter follower; b) form supereroi of pulses at the output of the SHG when the length adjustment; 7 is a Functional diagram of the SPP, including the generator superimage tension, inertia chain avtomashine, the current regulator and SHF AG super regenerative transceiver ARZ; Fig - schematic diagram of the microwave oscillator SPP. Structural scheme of the WBS shown in figure 1, includes: power supply - 1; stabilizer medium power microwave oscillator - 2; voltage regulator power microwave oscillator - 3; generator superimage voltage (SHG) - 4; inertial circuit avtomashine - 5; microwave oscillator - 6; microwave bandpass filter 7; transmit-receive antenna ARZ - 8. Structural scheme of the SPP (figure 1) has the following connections: power supply 1 is connected to the voltage regulator - 3, the first output of the latter is connected with the stabilizer average current of the oscillator is 2, and the second output is connected to a power inlet generator superimage voltage - 4, the output of which is connected to the input of the inertial chain avtomashine - 5; the first output of the current regulator - 2 is connected to the power input of the microwave oscillator - 6, and the second output of the current regulator - 2 is connected to the output of the inertial chain avtomashine - 5 and the input of the microwave oscillator 6 outputinput which connected via microwave band-pass filter 7 with a transmit-receive antennas is th 8; the input modulation is connected to the generator superimage voltage. The principal features of functioning of the WBS can be explained by analyzing its performance during the same period spirituosa frequency Tc(figure 3). Figure 3 shows: U[Izl]- the envelope of the radio pulses emitted SPP duration τand; Uc- voltage spirituosa frequency, characterized by a period Twithand duration τwithδ(t)- the law of variation of the damping ratio of the path of the microwave oscillator; IEE- videospussy DC emitter of microwave transistor. Microwave oscillator (SHF AG) periodically switched on at time t1appearance superimage pulse Ucand off at time t3at the end of the interval damping τd. Operating frequency SHF AG is about 1680 MHz. The frequency of the pulse superimage voltage is 800 kHz (period of Twith=1,25 ISS). Oscillatory system off NGN is characterized by its attenuation δ0. The change in the attenuation circuit for pulse supersale τwithdefines the process of development and establishment of self-oscillations in the microwave oscillator SPP. Super regenerative effect of strengthening is to reduce the delay time τCfront of radio microwave-AG is elicina ∆τ Cwhen the external signal Ucsduring the receiving interval of τCRadjacent to the launch SPP. Increases the duration of the radar pulse and its energy. The output level of the WBS, depending on the level of the request signal in the primary reaction can be estimated by the expression [1]
where A∑- effective amplitude of the noise in the circuit MSR at the time of launch; Acthe amplitude of the external signal. The above expression (1) shows that the effect of the gain ∆τCmainly determined by the magnitude of the starting attenuation δp. The emergence of self-oscillation occurs when starting the damping δp≥0, when the current of the emitter of the active device exceeds a limit value of IEE≥Ig. The development of self-oscillation occurs when δp>0, which is determined by the starting current of the oscillator Ip>Igat the time of launch. So changing the value of Ipleads to the adjustment of the delay time τCand the effect of gain - increment time-delay ∆τC. Measurement of the slant range to the radiosonde, equipped with SPP, is carried out by measuring the time delay between the moment the Ohm feed short challenge of radio and receive the return of radio CAF increased duration to increment the delay time ∆τC. Thus, essentially, the WBS is a transceiver with a time separation of the receiving and transmitting modes during the same period spirituosa frequency Twith. To ensure high sensitivity and amplification in the receiving mode, it is necessary to make the inclusion of a microwave oscillator with a minimum value of inrush negative damping δp. To achieve maximum power output, proportional Andarticlein SPP is required to increase the negative damping in the field of medium and large amplitudes for a given type of active device of the oscillator (see figure 2). To implement these conflicting requirements, it was necessary to implement the circuit WBS hard mode setting oscillations [1]. This result can be obtained by analysis of a simplified nonlinear oscillator equation
Qualitative analysis of equation (2) allows us to determine the behavior of the function δ(t,A) depending on the amplitude A (figure 2) and in the time domain (figure 3). Research the different options for the implementation of the function δ(t,A) show that, unlike featured in well-known literature soft-mode establishing oscillations in the class is the practical sverigekartan (δ(A)=δ P1) [2], SPP, you must implement the transition process with rigid character of the establishment of oscillations [1]. In this case, the start of SPP can occur with minimum negative value of the slope δ(A)=δP3that provides a minimum bandwidth reception and high sensitivity. The establishment of steady state occurs at the area of maximum values of the amplitudes Andarticletherefore, at high output power. It must be emphasized that the changing pad attenuation δpvirtually no effect on the aarticle. This allows, ultimately, separately and effectively adjust parameters of receiving and transmitting modes SPP by adjusting the starting current SHF AG at the time of inclusion. It should be emphasized that to ensure the transition from the rigid character of the establishment of oscillations, it is necessary chain base of transistor microwave oscillator to control the voltage pulses produced by the generator superimage voltage (GOS) with low output impedance. Almost impulses GOS are formed using an emitter follower, which provides low differential output impedance of the GOS (see RF patent №93546). The coefficient of regeneration (feedback factor) in the microwave oscillator must be optimal. Max neg is negative damping δ(t)=δ maxin the area of the average values of amplitudes provides a quick switch from receiving to transmitting mode SPP. This contributes to the formation of a virtually rectangular impulses and symmetric spectrum radiation SPP characteristic of the sequence of radio classical pulse oscillator. It must be emphasized that in transistor microwave oscillator SPP inrush current Ipduring the receiving interval exceeds a limit value of Igalmost only tens to hundreds of mA. Therefore, to reduce the effect of shock excitation circuit SHF AG and ensure high sensitivity of the shape of the current pulse emitter for receiving interval should be gradually increasing from zero to the starting value of Ip=5-10 mA (see figure 3). Next, the constant component of the current of the emitter IEE(and the collector current Ico=IEEchanges synchronously with the amplitude of self-oscillations due to the hard nature of the transition process to the maximum values for the given active device until the establishment of the stationary mode Ico=180-250 mA. It should be emphasized that the steady state amplitude aarticleand Iaamahdo not depend on the inrush current Ip. It should be noted that the average value of the DC collector current IDAC during the period of supersale is determined by the ratio τCand τwith. Since the value of τCadjustable starting current Ipit appears that adjusting the average current ISRcauses a corresponding change in the starting current of the microwave oscillator. For example, under the influence of destabilizing factors in the increase in the average current ISRincreasing the starting current Ipthat leads to a reduction of the time delay τCthe increase in the duration of radio τandand reduced sensitivity. When reducing the average current ISRthe process goes in the opposite direction. Thus, the stabilization of the current ISRallows to stabilize τCthe sensitivity and bandwidth in the receiving mode, and the duration and the power output of radio SPP τand. Accordingly, the duration supereroi pulses τwithallows you to optimize the ratio of sensitivity and radiated average power SPP [1]. Thus, the stabilizer of the average current ISR- 2 UHF oscillator - 6 is an important WBS node. Introduction to the structure of the SPP voltage 3 power supply - 1 associated with the need to ensure the stability of the carrier frequency of the microwave oscillator SPP in the range f0=1680±5 MHz. As noted by the ü higher generator superimage voltage - 4 produces videospussy with a frequency of Fc=800 kHz, the control directly the operation of the microwave oscillator (figure 3). Practically these pulses are generated by using an emitter follower, which is included at the output of the GOS (see RF patent №93546), providing a low differential output impedance. The GOS parameters are essential for optimizing SPP. Inertia chain avtomashine - 5 are necessary for increasing the stability of the microwave oscillator 6 and secure mode "response pause in the measurement range in the composition of the radiosonde system (see RF patent №2214614). Response pause is formed by the reaction inertia chain avtomashine - 5 receiving additional charge for the increment of time delay ∆τCthat leads to the locking of microwave oscillator at the time of generation of the next radar pulse. Figure 7 shows the simplified functional diagram WBS containing GOS, the emitter follower which is performed on the transistor VT1. SHF AG implemented at the transistor VT2. Inertia chain avtomashine SHF AG formed by resistor R2 and capacitor C4. Adjust R2 allows you to change the time constant of the inertial chain avtomashine and ensures the formation of a response From The P to the inquiring signal RLS, as suggested in the patents of the Russian Federation No. 2172965, No. 2214614. However, when adjusting R2 is due to the change of the operation mode SHF AG offset of the carrier frequency, which does not allow to simultaneously adjust the sensitivity, to combine the reception frequency and the carrier frequency SPP. On Fig for information shows a schematic diagram of the microwave oscillator - 6 (MW AG) SPP. Specifications and features settings SHF AG discussed in detail in the patent of Russian Federation №104326, therefore, are not discussed here. Next, you need to explain the principle of the unstressed run the microwave oscillator SPP, providing maximum sensitivity. Figure 4 shows the fluctuations U∑in the circuit of the microwave oscillator in the startup process. On the time interval from 0 to t1the active device SHF AG (microwave transistor) is turned off. In the circuit there are thermal fluctuation fluctuations. At time t1generator superimage voltage turns on the start-up current oscillator IEthat grows exponentially. On this time interval the current IEin the circuit is shock excited oscillations Ubeats. Because decrement the interval attenuation loop until t2remains positive, the shock oscillations are exponentially damped until the fluctuation noise Ufat this online is rule determined by the total effect of thermal fluctuations and fluctuations shot of the current active device. At time t2the current reaches the boundary values of IE=Ig. At this point, the average value of the attenuation circuit dcpis equal to zero. However, the effective value of attenuation is determined by the effective value of the fluctuation component of the decay deffthat fundamentally cannot be zero. Therefore, the bandwidth of the circuit WBS at this point is minimal, but the final value. If the time interval ∆t=t2-t1enough to shock oscillations had time to subside to the level of the fluctuations Ufthe development of self-oscillations UAKsince t2on incremental plot comes from the level of the fluctuations Uf. The current active device further increases to the level of the starting value of IE=Ip. It is important to emphasize that in transistor microwave oscillator WBS output average power of less than 0.5 W boundary current has a value of the order of IE=5-8 mA, a Ipinrush current Ipduring the receiving interval exceeds a limit value of Igalmost all tens of μa. This run mode SPP is unstressed and essentially provides the maximum sensitivity of the CAF to the request signal. Since the phase and amplitude fluctuations that determine the initial launch conditions, are random processes, the spec is R radiation of radio SPP in this case will be solid. If the time interval ∆t=t2-t1insufficient for the attenuation of shock oscillations, the development of self-oscillations UAKSPP will determine the shock oscillations Ubeats. Therefore, the phase of radio SPP will synchronize the shock waves and the sensitivity of the CAF to the external signal will drop dramatically. The emission spectrum of radio SPP in this case is discrete, and bar. This run mode is typical for classical pulse oscillator. It must be emphasized that there is a constant component of the current of the emitter IEE(and the collector current Ico=IEEchanges synchronously with the amplitude of self-oscillations due to the hard nature of the transition process to the maximum value, until the establishment of the stationary regime (see figure 3, 4). It should be emphasized that the steady state amplitude aarticleand Iaamahpractically do not depend on the inrush current Ip. Required law changes the shape of the pulse current of the microwave oscillator at the time of launch is provided by pulses superimage voltage generated by the emitter follower GOS (see figa, b). To explain the features of the adjustment of the frequency of radiation relative to the receive frequency figure 5 (a) dependencies of the frequency of the microwave oscillator in the installation process is to set the amplitude of self-oscillations And for different modes of operation SPP. Reception frequency fCRcorresponds to the frequency of self-oscillations in the time of the launch of the CAF with the amplitude A=0. Figure 3 this mode corresponds to the time t2. Carrier emission frequency f[Izl]SPP corresponds to the frequency established self-oscillation when a=aarticle. When the condition fCR=f[Izl] 2reception frequency and the transmission frequency CAF match. Under the conditions of fCR≤f[Izl] 2and f[Izl] 3≤fCRthe carrier frequency is above or below the frequency of the reception SPP. Essentially reception frequency fCRis determined by the resonant frequency of oscillatory system SHF AG at the time of launch SPP. Next, the process of establishing the frequency of self-oscillations is determined by the dependence of the integral of the reactive parameters of the active device on the amplitude of the operating currents and voltages in the circuit SHF AG. As noted earlier, the SPP DC microwave transistor IEEchanges synchronously with the amplitude of high-frequency oscillations in figure 5 (b). Therefore, the adjustment of its stationary values of IEA Stallows you to effectively control the frequency of the steady-state self-oscillations relative to the receive frequency fCR. The most easy to control the pulse current IEA Stby adjusting the pulse current of the control electrode of the active device (the base current of the microwave transistor) changes the output resistance gene the operator superimage voltage. 7 adjusting the output resistance of the generator superimage voltage output emitter follower VT1) is performed by the resistor R2. The increase in the resistance R2 leads to the decrease of the pulse current IEA st1and corresponding increase of the carrier frequency of radio CAF in position fCR<f1. Reducing the resistance R2 allows you to combine and receive frequencies of radiation fCR=f2when IEA ST2or to set the frequency of the radiation is below the receive frequency fCR>f3when IEA St3. Reception frequency fCRis determined by the setting of the resonance frequency of the vibrating system SHF AG at the time of launch SPP. Thus, by adjusting the amplitude of videokursov current active device (microwave transistor) by changing the output resistance of the generator superimage voltage R2 is able to control the mutual position of the frequencies of transmission and reception of SPP with the required accuracy. The intensity of the radiation SPP practically does not change. However, to maintain the optimum values of the time constant circuit avtomashine - 5, required for the formation response signal range - reply pause, requires appropriate selection of capacitor C4. As shown above, to achieve maximum sensitivity, you need both is that unstressed run the microwave oscillator SPP. Practically this is achieved by adjusting the time constant τ=R1C1 - lowpass filter formed by resistor R1 and capacitor C1 at the input of the emitter follower VT1 GOS (Fig.7). The increase in the resistance of the resistor R1 decreases the rate of rise of voltage at the input of the microwave oscillator (see figure 4 and 6) and reducing the level of shock oscillations. However, this reduces the effective duration supereroi pulses and decreases the gain SPP proportional to the average delay time τCsee equation (2). To restore the required gain level WBS is required to increase the duration supereroi pulses. Reducing the resistance of the resistor R1 causes a reverse change settings SPP. When the optimal value of the time constant τ=R1C1 maximum sensitivity and amplification of the SPP, including, in the "response delay". Another option for adjusting the sensitivity and gain SPP fundamentally can be implemented by varying the duration supereroi pulses, as shown in Fig.6 (b). It should be emphasized that the frequency of the radiation SPP when adjusting the sensitivity of the receiving mode is not changed. The actual work of the PSC in the composition of the electronic system are described in detail in the aforementioned patents of the Russian Federation and work is x the same author and, therefore, in the description of this application is not repeated. The proposed method settings SPP allows guaranteed to ensure the production of CAF radiosondes on modern microwave transistors with sensitivity at the level of minus 95÷100 dB/W at an average power of 250÷350 mW and an efficiency of not less than 35%. This transceiver ARP provides accurate measurement of slant range ground radar to 250-300 km with an accuracy of ±15 m, with a low level query power ground radar. Thus, the peak power of the radar transmitter is 200 watts, average - 0.2 watts. Transmission of telemetry signals ARP is carried out by frequency or phase modulation supereroi pulses, i.e. on the same carrier frequency is the measure of all ARP coordinates: elevation, azimuth, slant range and is transmitting telemetry signals meteorological variables. Ultimately, the use of CAF in the composition of the RHA can significantly reduce the cost of obtaining aerological information on the network of Roshydromet Russian Federation. Literature 1. Ivanov VA, Fridzon MB, Issac S. p. "weather-balloon data, Technical and metrological aspects of the development and application of radiosonde measurement tools", edited Vaifanua. Yekaterinburg. UB RAS. 2004. 596 S. ISBN 5-7691-1513-0. 2. Sverigekartan. McKellen, Gaytravel, Uguccione, Bastrukov; re the action McKellen. - M.: Radio and communication, 1983. - 248 S., Il. The method of adjusting the output parameters of the super regenerative transponder radiosonde, based on the optimal choice of the feedback factor of the super regenerative oscillator transceiver, resistance load, the resonant frequency of oscillatory system, characterized in that at the start of the super regenerative oscillator transceiver can provide a self-excitation mode with the hard nature of the transition process of establishing self-oscillations stabilize the average current and voltage of the active device of the oscillator super regenerative transceiver, adjust the pulse current of the control electrode is a base of the transistor active device of the oscillator, thereby to set the reception frequency relative to the carrier frequency of self-oscillations super regenerative transceiver, the adjustment of the slope of the exponentially rising leading edge and duration superimage pulse set the desired sensitivity level super regenerative transponder.
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