Method for conversion circuit control and device for realisation of this method. RU patent 2510835.
 Multilevel frequency converter with differential voltage levels and bypass semiconductor keys / 2510769Invention pertains to electrical engineering and can be used in high voltage regulated electrical drives. Multilevel frequency converter with differential voltage levels and bypass semiconductor keys contains input multi-winding transformer, control system and several levels of power cells in each phase. Output voltage of cells for each level is different: output voltage of the first level cells is equal to half of the rated output voltage of frequency converter and each next level is twice less than voltage of the previous level. In parallel to output of each power cell there's bypass semiconductor key, one semiconductor key of power cell is connected to the first control output of the control system by commutator switch in case of the cell failure, while its other control input is connected to the second control output of the control system by commutator switch in operating modes to change output voltage of the frequency converter. |
 Twelve-phase step-up autotransformer phase changer / 2510568Device includes a three-phase autotransformer, having three windings 1, 2, 3 of a primary coil and six windings 4, 5, 6, 7, 8, 9 of secondary coils, six interconnected windings 4, 5, 6, 7, 8, 9 of a primary coil, having taps 10, 11, 12, 13, 14, 15, 16, 17, 18, 19, 20, 21 from windings, the winding 1 of the primary coil of the first phase is connected by its end to a node B, where windings 6 and 8 of the secondary coils of the second phase and third phase are connected; the winding 2 of the primary coil of the second phase is connected by its end to a node D, where the windings 9 and 5 of secondary coils of the third phase and the first phase are connected; the winding 3 of the primary coil of the third phase is connected by its end to a node F, where windings 4 and 7 of secondary coils of the first phase and the second phase are connected; the beginning of the winding 4 of the secondary coil is connected to the beginning of the winding 8 of the secondary coil to form a node A; the end of the winding 8 of the secondary coil is connected to the end of the winding 6 of the secondary coil to form a node B; the beginning of the winding 6 of the secondary coil is connected to the beginning of the winding 5 of the secondary coil to form a node C; the end of the winding 5 of the secondary coil is connected to the end of the winding 9 of the secondary coil to form a node D; the beginning of the winding 9 of the secondary coil is connected to the beginning of the winding 7 of the secondary coil to form a node E; the end of the winding 7 of the secondary coil is connected to the end of the winding 4 of the secondary coil to form a node F and close the loop of windings of the secondary coils forming a "hexagon" A, B, C, D, E, F; each winding of the secondary coil of the autotransformer is a side of the "hexagon" A, B, C, D, E, F, which converts a symmetrical three-phase voltage system to a symmetrical six-phase voltage system. |
 Converter of dc voltage into three-phase quasi-sinusoidal one / 2509404Converter of DC voltage into three-phase quasi-sinusoidal one comprises four serially connected power conversion units: a step-up converter (1) with a control unit (2), a three-phase inverter unit (3) with a control unit (4), a unit of transfilters (5) and a unit of outlet filters (6). |
 Composite capacity and its application / 2508574Each of capacitor units contains many base capacitors installed on special module printed-circuit board (PCB). All the base capacitors of capacitor units are identical, thus simplifying both manufacturing and maintenance of capacity component. Formation of composite capacity on base capacitors of the same type simplifies significantly their manufacturing and maintenance. Space flexibility achieved due to application of lots of electrically interconnected capacitor units is preferable in such power devices where capacity available to capacity component inside the device may be limited in at least one direction. Geometrically flexible arrangement provided by separate capacitor units allows their arrangement at random angle to each other thus occupying available space in power devices increasing their composite capacity. |
 Control method for usage of redundancy in case of fault of multi-phase ac rectifier with distributed energy accumulators / 2507671In accordance with the invention, a subsystem (10) of a branch (T1, …, T6) of valves corresponding to a faulty branch (T1, …, T6) of valves, of a faulty phase module (100) is controlled so that its terminal voltage (UX21) is equal to zero, and therefore accordingly one subsystem (10) corresponding to this branch (T1, …, T6) of valves of the branch (T1, …, T6) of valves of each faulty phase module (100) is controlled so that their terminal voltages (UX21) are equal to zero. Thus a control method is produced to use redundancy in case of a fault of a multi-phase AC rectifier with distributed energy accumulators (9), at the same time the generated output voltages (UL10, UL20 and UL30) no longer contain a DC voltage component. |
 High-voltage frequency-controlled electric drive / 2505918In the high-voltage frequency-controlled electric drive, an uncontrolled high frequency converter is connected through a multiple-winding single-phase high-frequency transformer to a controlled high frequency converter having a cellular type, wherein inputs of rectifier-inverter cells are connected to corresponding secondary windings of the single-phase high-frequency multiple-winding transformer, the primary winding of which is connected to the output of the uncontrolled high frequency converter, and the input of the latter is connected through a reactor to the mains supply. |
 Five-phase phase changer / 2503121Invention may be used to create rectifiers for controlled electric DC and AC drives for machines to increase their efficiency, and also on transformation substations for power supply to electrified railway roads, in electric metallurgical and chemical industry to reduce the value of pulsations of rectified voltage and to reduce content of higher harmonic components in an AC curve in a three-phase grid. The proposed five-phase phase changer comprises a three-phase transformer, having three coils of the primary winding, which are connected as a star network, and are connected to the three-phase grid with a zero wire "0", six joined main coils of the secondary windings, one additional coil of secondary winding and taps from turns of the main coils of the secondary windings, which jointly with the output clamp of the additional coil of the secondary winding create a symmetrical five-phase system of voltages. Each main coil of the secondary winding of the transformer is a side of a "hexagon" A, B, C, D, E, F, transforming a symmetrical three-phase system of voltages into a symmetrical six-phase system of voltages, at the same time the additional coil of the secondary winding with its beginning is connected to the unit of the "hexagon" circuit, which is not connected with the main coils of the secondary winding of the phase, on the rod of which there is the additional coil of the secondary winding. |
 Control method of parallel connected modules of uninterrupted power source / 2502181Control method involves use of similar modules switched in control chains either to a drive or driven module modes; besides, in the drive module there used is additional feedback as to current of capacitors of output filters of modules. In case of failure of any of the modules, it is disconnected from load and the primary power network, and an operating mode of each module, if required, is changed by means of switches. In order to change over the driven module to the drive module operation, a signal is supplied to its input, which is obtained by switching an input chain from the setting signal of current to sine-shaped voltage signal, from which the connected signal of the main feedback as to voltage and total current signal of capacitors of output filters of modules is deducted. At the same time, a current signal of the drive module is connected to a common control bus of output current of the drive module. When an additional module is being introduced to an uninterrupted power source, first, it is set to a drive module mode, and then it is switched over to a driven module mode. |
 Unit to control power inverter of dc conversion into ac of circuit of resonant power converter, in particular, dc converter into dc for use in circuits of high voltage generator of up-to-date device of computer tomography or x-ray system / 2499349Circuit of power conversion of resonance type comprises a phase-to-phase transformer (406), serially connected to at least one serially connected resonant circuit (403a and 403a' or 403b and 403b') at the outlet of two cascades (402a+b) of the power inverter of DC conversion into AC, supplying to the high-voltage transformer (404) with multiple primary windings. The phase-to-phase transformer (406) serves to eliminate mismatch (ΔI) of resonant output currents (I1, I2) of cascades (402a+b) of the power inverter of DC conversion into AC. The method of control guarantees that the phase-to-phase transformer (406) is not saturated, provides for operation under zero current and provides for minimised losses of power at the inlet. |
 Intelligent voltage converter / 2499348Device comprises the main and the reserve AC circuit of 3-50 Hz, 380 V, the first, second and third switchboard, the first, second and third filter, the first and second rectifier, the first and second current sensor, an inverter, a transformer, a group of stabilised DC voltage consumers, a power supply unit, a unit of power switch drivers, a temperature sensor, a voltage sensor, a microcontroller, a control and indication panel, a unit of fans and an external system of remote control and monitoring, the device includes a limiter of start-up current, and the microcontroller is made as capable of monitoring the voltage value of the first and second AC circuit 3-50 Hz, 380 V, monitoring of the current value at the inverter inlet, monitoring of actuation in the unit of protection and the unit of power switch drivers by high current in open thyristors of the inverter, monitoring of the value of voltage and current of consumption by the group of stabilised DC voltage consumers, and with the possibility for control of the first, second and third switchboard, control of the unit of power switch drivers. |
 Mode(variants) and an arrangement(variants) of electric supply of predominantly portable electron aids / 2269862The aids include at least one active element with three or more electrodes particularly a transistor and using this active element(elements) carry out amplification, conversion or generation (formation) of working electric signals of alternating or direct voltage including broadband signals. The mode and the arrangement for electric supply of predominantly portable electron aids is carried out by way of using at least one a three-electrode active element, amplification, conversion or generation of an electric signal of alternating or direct voltage based on supplying voltage on the clamps of the electron aid, impulse voltage whose on-off time ratio is within the limits of 1,1-20,0 is used as supply voltage. In the second variant of the mode and of the arrangement the impulse voltage has the following parameters: the frequency of impulses is at least one level higher than the maximum frequency of the spectrum of the electric signal of alternating voltage or at least one level less than the minimal frequency of the spectrum of this electric signal, and the duration of the impulse fronts is at least one level less than the magnitude inverse to the maximum frequency of the spectrum of the electric signal of alternative voltage. |
 Device for measuring three-phased voltage / 2314630Device contains three-phased bridge rectifier, made on diodes (1-6). Output contacts of rectifier, being output contacts of indicator, are meant for connecting load circuit (7). Resistors (8-10) are introduced into input circuits of alternating current, connected to corresponding phases of voltage supply being measured. Resistance value of each resistor (8-10) equals to (0,5÷0,7) of value of active resistance of constant current load chain (7). |
 Phase-shifting device / 2320071Device contains control signal source (input of phase-shifting device), adder, amplitude modulator, integrator, 2 relay elements, logical element "XOR", three logical elements "2AND", subtracting "n"-bit binary counter, input for connecting a supply of supporting voltage, generator of stable frequency impulses, adding "n"-bit binary counter, digital comparator, logical element "kAND", where n>k, mono-stable multi-vibrator, logical element "2OR", input for connecting the source of control impulses for power thyristors. Device belongs to the class of integrating systems with two digital scanning functions. One scan is independent and is generated due to generator of stable frequency impulses. The second scan is dependent, which is generated from control signal, and transformed due to impulse signal from output of voltage transformer to impulse frequency. Command for managing power thyristors is generated at the time moments when numeric values of independent and dependent scanning functions are equal or exceeded. |
 Device for adjusting output current of impulse stabilizing transformer / 2321148The device contains two-cycle impulse transformer with two high frequency controllable switches (1,2), an input LC-filter (3) and output transformer (9), connected to secondary winding (8) of which are: rectifier (7); network rectifier (10), connected through switch (11) to input of LC-filter (3); output LC-filter (4), is connected by input to output of rectifier (7) and by output to load circuit (5); control unit (15) is connected by output to contacts of primary windings of dividing transformers (17,18), contacts of secondary windings of which are connected to control circuits of switch (1,2); adding amplifier (16) is connected by first input through current sensor (6) to output of LC-filter (4) and by output to input of control unit (15); pulse-width modulation comparator (12) is connected by output to control input of switch (11) and by first input through generator of linearly changing voltage (13) is connected to output of clock impulse generator (14); integration adder (21) is connected by first input to current setting supporting voltage supply (19), by second input to output of current sensor (6) and by output to second input of adding amplifier (16); and amplifier with piecewise-linear transfer characteristic (20) is connected by input to output of adding amplifier (16) and by output to second input of the pulse width modulation comparator. |
 Semi-bridge thyristor inverter / 2321942In accordance to the invention, a transformer is coupled into alternating current diagonal of semi-bridge thyristor inverter. Secondary winding of transformer through diode bridge is connected to constant current load. In parallel to main semi-bridge thyristor inverter, an additional semi-bridge thyristor inverter is included into constant current diagonal which has capacitors with approximately ten times less capacity compared to the main one. An additional transformer winding is incorporated into alternating current diagonal of additional inverter with number of coils less than that of its primary winding. The inverter is controlled from typical pulse-width regulation circuit in broad range of loads. |
 Method of control of tetrasquare converter with computation of switching phases and microprocessor device to implement method / 2327276Invention relates to electrical engineering and may be used to control the electric train AC. The invention increases the accuracy in control of the converter and eliminates alarm operating conditions. The method of control of tetrasquare converter with computation of switching phases includes generating the data on the dependency of the gate switching intervals on the depth of modulation and inputting this data into the memory of the converter control system for the range of tolerable operating frequencies in compliance with the number of the PWM-intervals. The control system is used to preset the current voltage value at the converter output, the current circuit value and the value of phase difference between the circuit voltage and current. The circuit current value id regulated by varying the voltage modulation at the converter input. The intervals of the controlled gates switching are calculated and the voltage modulation value is varied by setting the control signal for cutting in- cutting off the gates. The method features the correction of the gates cutting in interval values allowing for certified data on controlled gates, operating conditions and the converter load nature. Here, in every half-cycle of the supply voltage, the maximum modulation frequency is limited by the gate switching duration. The microprocessor device to control the said converter incorporates a timer, a processor, an operating memory, a permanent memory, ANC, drivers' unit, current sender, synchroniser and the input current amplitude generator, timer inputs-outputs, those of the processor, permanent memory, operating memory. The drivers' unit inputs are coupled by the data-address bus. It also includes the converter operation parameters generator, voltage sender, gate switching phase computation unit, the unit of limiting switching intervals, the time interval I/O unit, the unit of communication with the converter load. |
 Method of output voltage control in multi-cell frequency converter / 2331151Invention refers to electric engineering and may be used in inductive heating systems with semi-conducting frequency converters when control system are designed. Method is intended for controlling output voltage of converter containing several inverters and multi-elements matching transformer with primary windings being connected to proper inverters and secondary windings being connected serially forming voltage summation circuit. Output voltage of one inverter is controlled by means of DC voltage converter connected to inverter input within the range defined by low and high thresholds. Other non-controlled inverters connected in parallel or fed from rectifiers are actuated into one of two states: "boosting voltage" or "short circuit". Output voltages of non-controlled inverters are set to be proportional to weight coefficient of bit pattern (1, 2, 4, 8, 16, ...). Different combinations of non-controlled inverters states form several levels of output voltage further creating several sub-ranges (zones) of output voltage controlling. Control is conducted by controlled inverter within those sub-ranges. Therefore, if output voltage of controlled inverter achieves proper range of controlling, states of non-controlled inverters are changed so that sum of non-controlled inverters weight coefficients being in "voltage boosting" mode could change by one. It results in control range shifting in controlled inverter by the voltage value assigned for lowest weight coefficient. |
 Direct current to alternating current converter / 2333591Invention pertains to electrical engineering, and specifically to invertors for autonomous electrical power supply for different electrical equipment, requiring use of sinusoidal alternating current. The direct current converter has a generator of sinusoidal voltage, a driver-amplifier and a power electronic converter. The sinusoidal voltage generator with frequency f is in the form of a miniature motor-generator, the electric motor of which rotates with a stable velocity proportional to frequency f and the motor-generator controls the electronic breaker-splitter. The electric motor of the motor-generator works on direct or alternating current and can smoothly change speed of rotation. |
 High voltage electric drive of alternating current (versions) / 2334349Composition of the electric drive of an alternating current includes the frequency converter, the invention can be used for the launching and control of the work of asynchronous or synchronous electric drives with the working voltage 6...10 kV and power of up to tens of mW. The high-voltage electric drive of the alternating current with the three-phase electric motor contains a source of an adjustable direct current, three-phase bridge thyristor chopper, switching devices connected to the outputs of alternating current of the inverter consistently with the phases of the three-phase winding of the electric motor, sensors of current and voltage and the control devices of the inverter and switching devices. Each switching device contains a capacitor with two outputs and the bidirectional symmetric operated semi-conductor key connected in parallel to it completely. Starting of the switching device in the electric drive is carried out in the manner as it specified in the materials of application for each of the three variants. In the electric drive for each of the variants protection of semi-conductor keys is provided at extraordinary and emergency situations. |
 Method of providing power supply of electrodynamic flying vehicles / 2335060Invention relates to remote transfer and conversion of super-high-frequency energy into DC electrical power. The proposed method consists in fitting an aluminium foil enclosure on over the entire surface of the vehicle airframe skin. The super-high-frequency converter is made in a material representing a mix of two chemical solid-state components with grain size not over 30 to 50 microns, taken in equal proportion but different atomic numbers, and forming, when combined, a dipole solid-state matrix. Note that the said bi-component mix is applied uniformly onto the said skin enclosure, the like poles of the dipole matrix being combined and connected to appropriate terminals of the vehicle flight control components. |
FIELD: electricity.
SUBSTANCE: invention is attributed to the field of electric engineering and can be used for conversion circuit control. According to the control method the conversion circuit contains partial conversion systems (1), (2) of inductance (L1, L2); each partial conversion system (1, 2) contains at least one two-pole commutation cell (3) and it contains two in-series controlled bidirectional power semiconductor switches with controlled one-directional passage of current and capacitive storage. Power semiconductor switches of commutation cells (3) in the first and second partial conversion system (1) are controlled by control signals (S1) and (S2) respectively. In order to calculate capacitive storage for power of the conversion circuit notwithstanding current required at output of the conversion circuit, i.e. from its frequency, control signal (S1) is shaped of voltage fluctuation signal (VL) at inductances (L1, L2) and commutation function (α1). Additional control signal (S2) is shaped of voltage fluctuation signal (VL) at inductances (L1, L2) and commutation function (α2). Commutation functions (α1, α2) are shaped by signal (VA) of voltage fluctuations (Vu) at the output (A) and selected reference signal (Vref).
EFFECT: maintaining voltage ripple at low level.
The technical field
The invention relates to the field of power electronics. Specifically refers to the manner of management of the Converter circuit and device for realization of the method in accordance with restrictive parts of the independent claims.
The level of technology
Conversion schemes are used today in many applications. In WO 2007/023064 A1 described Converter circuit, the voltage which is particularly easy recalculated. It contains the first and second partial conversion system that consistently connected among themselves by means of two series of inductors. The connection point both series inductance forms the output, such as electrical load. Each partial conversion system includes at least one two-pole switching cell, and in the case of multiple switching cells in a partial conversion system they consistently connected among themselves. Each two-pole switching cell contains two series of managed bidirectional power semiconductor switch managed unidirectional flow of current and capacitive energy storage is in parallel serial parallel connection of power semiconductor switches.
To control conversion scheme WO 2007/023064 A1 provided depicted in figure 1 are known device that contains first a management scheme for the formation of a control signal to control the power semiconductor switches switching cells first partial conversion system and the second a management scheme for the formation of additional control signal to control the power semiconductor switches switching cells second partial conversion system.
Usually Converter scheme for WO 2007/023064 A1 managed so that the output produced net AC voltage and clean alternating current. The calculation of the capacitive energy storage commutation of cells is carried out in such a way that ripple voltage on capacitive drive remains within a specified range of fluctuation for this maximum current output, and this current has a given frequency. If desirable less frequency than the one that was laid in the basis of calculation, the ripple voltage increases. If the output is supposed to produce direct current or alternating current with a DC component, the ripple voltage increases almost indefinitely. In this case, the capacitive energy storage devices must either be supplied from the outside, or must be selected infinitely large to when working with a constant current or constant component output that is not fully discharged or has not been charged arbitrarily.
The control mode of the Converter circuit of the WO 2007/023064 A1, which would allow to calculate the capacitive energy storage devices regardless of the desired output current, i.e. irrespective of its frequency, is currently unknown.
Disclosure of the invention
The objective of the invention is a method of management of the Converter circuit, which would provide a calculation of its capacitive energy storage, regardless of the desired output current of the Converter circuit, i.e. on its frequency. In addition, the object of the invention is a device, which is particularly simple way may be to implement the proposed method.
These tasks are solved according to the signs of claims 1 and 10 of the formula, respectively. In dependent clauses are given preferred embodiments of the invention.
Converting schema contains the first and second partial conversion system that consistently connected among themselves by means of two series of inductors. The connection point both series inductance forms exit. Each partial conversion system includes at least one two-pole switching cell, and each two-pole switching cell contains two series of managed bidirectional power semiconductor switch managed unidirectional the direction of current flow and included in parallel serial parallel connection of power semiconductor switches capacitive energy storage. Mainly the number of switching cells first partial conversion system corresponds to the number of switching cells second partial conversion system. In part of the way power semiconductor switches switching cells first partial conversion system controlled via the control signal and power semiconductor switches switching cells second partial conversion system - by means of additional control signal. According to the invention, the control signal form of the signal voltage fluctuations on the inductances and switching functions for power semiconductor switches switching cells first partial conversion system, and additional control signal from signal voltage fluctuations on the inductances and switching functions for power semiconductor switches switching cells second partial conversion system, and switching functions form via the signal voltage fluctuations at the output and select the reference signal, particularly at the same time. Through the application of oscillations, i.e. at the expense of signal fluctuations voltage inductances to provide a control and additional control signals and at the expense of signal voltage fluctuations at the exit for the formation of the switching functions, preferably to achieve what the ripple voltage on capacitive energy storage devices if desired current the output of the Converter circuit can significantly diminish, resulting in the calculation of the capacitive energy storage, which is necessary to carry out only in the reduced ripple voltage, does not depend on the desired output current.
The proposed device for the control of converting schema contains designed to provide a control signal first drive circuit, connected with power semiconductor switches switching cells first partial conversion system. In addition, the device includes designed to provide an additional control signal a second drive circuit, connected with power semiconductor switches switching cells second partial conversion system. According to the invention, to the first of a management scheme for the formation of a control signal signal voltage fluctuations on the inductances and a switching function for power semiconductor switches switching cells first partial conversion system. The second of a management scheme for the formation of additional control signal signal voltage fluctuations on the inductances and a switching function for power semiconductor switches switching cells second partial conversion system. In addition, there is the first computer unit for the formation of the switching function of the signal voltage fluctuations at the output and select the reference input. The device for realization of the method of management of the Converter circuit is implemented, thus, very simple and cost-effective because of scheme costs can be maintained very low and also the design requires only a small number of elements. Using this device, the proposed method is thus particularly easy.
These and other challenges, advantages and features of the invention become apparent from the following detailed description of the preferred options of its implementation in combination with the drawings.
Brief description drawings
The drawings:
figure 1 is a variant of the device for realization of the method in accordance with the level of equipment;
figure 2 - a variant of the device for realization of the offered method;
figure 3 - time response of the output current of the Converter circuit;
figure 4 - temporary characteristics output voltage Converter circuits;
figure 5 - time response of the currents through the first and second partial conversion system.
Used on figures from the reference position and the value of the combined list. In principle, on the figures of the same elements marked with the same reference positions. Describes the options are examples of object of the invention and do not have a restrictive effect.
The implementation of the invention
In figure 1, as already mentioned, depicts a variant of the device for realization of the method in accordance with art. Figure 2 shows a variant of the device for realization of the proposed method. Converting the diagram in figure 2 contains the first 1 and 2 second partial conversion system that consistently connected among themselves by means of two series of inductors L1, L2. The connection point of both series of inductors L1, L2 forms exit. Each partial conversion system 1 and 2 includes at least one two-pole switching cell 3. In the case of multiple switching cell 3 partial conversion system 1, 2 they consistently connected among themselves (figure 2). Each two-pole switching cell 3 contains two series of managed bidirectional power semiconductor switch managed one-way direction of current flow and the capacitive energy storage is in parallel serial parallel connection of power semiconductor switches. Controlled power semiconductor switch is made, in particular, in the form of lock-up thyristor (ATT) or thyristor with integrated management (IGCT) respectively of counter-parallel diode. You can also perform a controlled power semiconductor switch, for example, in the form of a power MOSFET transistor with advanced counter-parallel diode or in the form of a bipolar transistor (IGBT) with advanced counter-parallel diode. Preferably the number of switching cells 3 first partial conversion system 1 corresponds to the number of switching cells 3 second partial conversion system 2.
In part of the way power semiconductor switches switching cell 3 first partial conversion system 1 is managed by the control signal S1 and power semiconductor switches switching cell 3 second partial conversion system 2 - via additional control signal S2. Both signals for each switching cell 3 mainly time-shifted so that each switching cell 3 you can control preferably with a shift in time. According to the invention, the control signal S1 signal is formed from L V voltage fluctuations at the inductors L1, L2 and switching functions α 1 for power semiconductor switches switching cell 3 first partial conversion system 1, in particular from the sum of the two values, and the additional control signal S2 - out signal L V voltage fluctuations at the inductors L1, L2 and switching functions α 2 for power semiconductor switches switching cell 3 second partial conversion system 2, in particular from the sum of the two values, and switching functions α 1 , α 2 are formed by a signal in V A voltage fluctuations u V at the output and select reference signal V ref , particularly at the same time. Mainly as a reference signal V ref select the reference signal voltage u V output And, which is formed by adjusting the actual value of current i u output And to the given value.
The result is applied fluctuations, i.e. using signal L V voltage fluctuations at the inductors L1, L2 to provide a control S1 and additional control S2 signals and ringing V A voltage fluctuations u V output And for the formation of the switching functions α 1 , α 2 , you can achieve a substantial reduction ripple voltage on capacitive energy accumulators if desired current i u output And conversion schemes, which means that the calculation of capacitive energy accumulators is required only in respect reduced ripple voltage, and therefore, without depending on the desired output current i u .
According to the invention, switching function α 1 for power semiconductor switches switching cell 3 first partial conversion system 1 form of signal V A voltage fluctuations u V at the output and select the reference signal V ref following the formula:
α 1 = 1 2 ( 1 - V r e f - V A ) (1)Switching function α 2 for power semiconductor switches switching cell 3 second partial conversion system 2 form of the signal V A voltage fluctuations V u output and select the reference signal V ref according to the following formula:
α 1 = 1 2 ( 1 + V r e f + V A ) (2)According to the invention, the signal L V voltage fluctuations at the inductors L1, L2 is formed from the signal V i current oscillation partial conversion systems 1, 2, as explained by the following formula:
V L = V i x ( j ω ( L 1 + L 2 ) ) (3)Peak value M h signal voltage fluctuations is formed from the actual values i u of the current output and the reference signal V ref , preferably one can use formula (5.1) and (5.2), and to determine the amplitude values of M h signal fluctuations stress formula (5.1) must be solved only in respect of the amplitude value M h signal fluctuations.
Mainly signal V i fluctuations current partial power conversion systems 1, 2, signal V L voltage fluctuations at the inductors L1, L2 and signal V A voltage fluctuations u V output And have the same modulation. In addition, the signal V i fluctuations current partial power conversion systems 1, 2, signal V L voltage fluctuations at the inductors L1, L2 and signal V A voltage fluctuations u V output And preferably have the same phase shift Phi, and the same phase shift Phi optional.
Using the proposed method is preferable, you can work out at the output current is i u with fixed and variable components with the frequency W, which is based on the above apply fluctuations, and only applied fluctuations affect the ripple voltage on capacitive energy accumulators switching cell 3, making the ripple voltage can be maintained at a low level. Associated with this calculation capacitive energy accumulators may be preferred only in respect of such low ripple voltage, i.e. without depending on the desired output current i u . Current i u output And is calculated as follows:
i u ( t ) = I 0 + i ∧ u x cos ( ω t + ' ) (7)where I 0 - mentioned constant component, a
i u ∧- the mentioned amplitude of the variable component. For clarification figure 3 shows the time response of current i u output And conversion scheme. Furthermore, figure 4 shows the time response of the voltage u V output And conversion scheme. Figure 5 shows the time response of current i 1 through the first partial Converter system 1 and current i 2 through the second partial conversion system 2, and in both currents i 1 , i 2 also includes fixed and variable components with the frequency W, caused by the above-mentioned applications fluctuations. Completeness ' sake, it should be said that the capacitive currents in the energy accumulators not contain any DC component and no variable component with the frequency W, or two-frequency W mentioned above applied fluctuations.
In a multiphase system, for example in a three phase system with three conversion schemes, applied fluctuations, if they are selected with the same phase shifts, are common-mode voltage multi-phase load is connected to the phase conclusions A. Additional current oscillations do not occur. This method is used, for example, if overmodulation. In contrast to sverkajuschii here frequency and phase angle common-mode voltage arbitrary. Output current i 0 , which is then multiphase, is a constant-current, i.e. he has no variable component.
If the current i on u output And should have the desired variable component
i ∧ u x cos ( ω u t + ' u )with the frequency W u and desired phase shift Phi u, then the formula (5.1) is amended as follows:
1 2 i ∧ u x cos ( ω u t + Phi u ) x M h 2 + A h x M h x cos ( Δ Phi ) - ( 1 + V r e f ) x ( 1 - V r e f ) x i ∧ u x cos ( ω u t + + Phi u ) ≅ 0 (8)and for the determination of amplitude values And h signal current fluctuations can also resort to the formula (5.2), and peak value And h signal current oscillation and amplitude the value of M h signal voltage fluctuations, as already mentioned, can be defined by formulas (8) and (5.2). Then at the output And the desired way, there is a following current i u :
i u ( t ) = i ∧ u x cos ( ω u t + ' u ) + i ∧ u x cos ( ω t + ' ) (9) where i ∧ uestimated peak value of current.
The device figure 2 contains designed to provide a control signal S1 first drive circuit 4, connected with power semiconductor switches switching cell 3 first partial conversion system 1. Additionally, there are intended to provide an additional control signal S2 second control scheme 5, connected with power semiconductor switches switching cell 3 second partial conversion system 2. According to the invention, to the first management diagram 4 to provide a control signal S1 is served sum received from the signal L V voltage fluctuations at the inductors L1, L2 and switching functions α 1 for power semiconductor switches switching cell 3 first partial conversion system 1. The second control diagram 5 to provide an additional control signal S2 is served sum received from the signal L V voltage fluctuations at the inductors L1, L2 and switching functions α 2 for power semiconductor switches switching cell 3 second partial conversion system 2. For provide a control S1 and additional control S2 signals is used, for example, the corresponding table of correspondence (look-up table) in the first 4 and 5 second control circuits, in which for the switching function α 1 rigidly fixed appropriate control signals S1, but for switching function α 2 - appropriate control signals S2, or, for example, the appropriate modulator based on the method of pulse-width modulation. Additionally, there are first computer unit 6 for the formation of the switching functions α 1 , α 2 by calculating with formulas (1) and (2) of the signal V A voltage fluctuations u V at the output and select the reference signal V ref .
Figure 2 provides a second computer unit 10 for the signal conditioning instrument L V voltage fluctuations at the inductors L1, L2 signal V i fluctuations current partial power conversion systems 1, 2 with the second computer unit 10 generates signal L V voltage fluctuations at the inductors L1, L2 by calculation by formula (3).
Also included is a third computer unit 7 for signal V i fluctuations current partial power conversion systems 1, 2 of amplitude values And h signal current oscillation, which generates a signal V i fluctuations current partial power conversion systems 1, 2 calculation based on the formula (4).
In addition, a fourth computer unit 9 for the formation of amplitude values And h signal current oscillation of actual values i u current output and the reference signal V ref , and the fourth computing unit 9 forms a peak value And h signal current oscillation calculation based on the formula (5.1 and (5.2) or (8) and (5.2).
Fifth computing unit 8 is used for signal V A voltage fluctuations u V output And amplitude values of M h voltage fluctuations, and the fifth computing unit 8 generates signal V A voltage fluctuations u V output And by calculation by formula (6).
Fourth computing unit 9 also provides for the formation of amplitude values of M h voltage fluctuations from the actual values i u of the current output and the reference signal V ref , and the fourth computing unit 9 forms a peak value M h voltage fluctuations calculation based on the formula (5.1 and (5.2) or (8) and (5.2).
In General, were able to show that depicts, in particular, figure 2 proposed device can be implemented very simply and cost-effective because of circuit costs are very small and also the design requires only a small number of elements. Using this device, the proposed method is thus particularly easy.
The list of reference position
1 - the first partial conversion system
2 - the second partial conversion system
3 switching cell
4 - first management scheme
5 - second control scheme
6 - the first computing unit
7 - the third computer unit
8 - fifth computing unit
9 - the fourth computing unit
10 - second computer unit.
4. The method according to claim 3, in which the amplitude value (h ) of current oscillations form of actual values (i, u ) output current (a) and the reference signal (V ref ).
5. The way one of claims 1 to 4, in which the signal (V A ) voltage (V, u ) at the output (A) form of amplitude values (M h ) voltage fluctuations.
6. The method according to claim 5, which peak value (M h ) voltage fluctuations form of actual values (i, u ) output current (a) and the reference signal (V ref ).
7. The method of claim 2, in which the signal (V i ) current oscillation partial power conversion systems (1, 2), signal (V, L ) voltage fluctuations on the inductances (L1, L2) and signal (V A ) voltage (V, u ) at the output (A) have the same frequency.
8. The method of claim 2 or 7, in which the signal (V i ) current oscillation partial power conversion systems (1, 2), signal (V, L ) voltage fluctuations on the inductances (L1, L2) and signal (V A ) voltage (V, u ) at the output (A) have the same phase shift.
9. The method according to claim 1, wherein the quality of the reference signal (V ref ) selects the signal of the reference voltage (u V ) at the output ().
10. The device for realization of the method of management of the Converter circuit, containing the first and second partial conversion system (1), with partial conversion system (2) are connected among themselves by means of two series inductance (L1, L2), and the connection point series inductance (L1, L2) forms the output (A), each partial conversion system (1, 2) contains at least one two-pole switching cell (3), and each two-pole switching cell (3) contains two series of managed bidirectional power semiconductor switch managed a one-way direction of current flow and included in parallel a consistent scheme of power semiconductor switches capacitive energy storage device that contains the first drive circuit (4), made with the possibility of formation of the control signal (S1) and connected with power semiconductor switches switching cells (3) the first partial conversion system (1), second driver circuit (5), made with the possibility of formation of additional control signal (S2) and connected with power semiconductor switches switching cells (3) second partial conversion system (2), to first management scheme (4) to provide a control signal (S1) signal (V, L ) voltage fluctuations on the inductances (L1, L2) and a switching function (alpha 1 ) for power semiconductor switches switching cells (3) first partial conversion system (1), to the second management scheme (5) to provide an additional control signal (S2) signal (V, L ) voltage fluctuations on the inductances (L1, L2) and a switching function (alpha 2 ) for power semiconductor switches switching cells (3) second partial conversion system (2)with the specified device contains the first computing unit (6) for the formation of the switching functions (alpha 1 , α 2 ) of the signal (V A ) voltage (V, u ) at the output (a) and select the reference signal (V ref ).
11. The device according to claim 10, characterized by the fact that contains the second computer unit (10) for signal conditioning (V, L ) voltage fluctuations on the inductances (L1, L2) of the signal (V i ) current oscillation partial power conversion systems (1, 2).
12. The device according to claim 11, characterized by the fact that contains the third computer unit (7) for signal conditioning (V i ) current oscillation partial power conversion systems (1, 2) of the amplitude value (A to h ) of current oscillations.
13. The device indicated in paragraph 12, which is characterized by the fact that contains the fourth computing unit (9) for the formation of amplitude values (h ) of current oscillations of actual values (i, u ) output current (a) and the reference signal (V ref ).
14. The device indicated in paragraph 13, which is characterized by the fact that contains the fifth computing unit (8) to the signal conditioning instrument (V A ) voltage (V, u ) at the output (A) of the amplitude value (M h ) voltage fluctuations.
15. The device 14, characterized by the fact that the fourth computing unit (9) made with the possibility of formation of amplitude values (M h ) voltage fluctuations from the actual values (i, u ) output current (a) and the reference signal (V ref ).