Method of demodulating phase-modulated and frequency-modulated signals and apparatus for realising said method

FIELD: radio engineering, communication.

SUBSTANCE: method of demodulating phase-modulated and frequency-modulated signals is characterised by that the nonlinear element used is a three-pole nonlinear element; the four-terminal element is complex and consists of reactive and resistive elements; the three-pole nonlinear element is connected between a source of a phase-modulated or frequency-modulated signal and the input of the four-terminal element on a scheme with a common one of three electrodes; a high-frequency load is connected in a transverse circuit between the output of the four-terminal element and a lowpass filter.

EFFECT: wider field of physical realisability of change in the real and imaginary components of resistance of the signal source and the load, within which the required values of the modulus and phase of transfer constants are provided simultaneously.

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The group of inventions relates to the field of radio communication and radar systems and can be used for phase-shift keyed demodulation, fazokodirovannymi, frequency-shift keyed and frequency-modulated signals.

There is a method of demodulation fazokodirovannymi signals (FMS), consisting in the fact that two of the nonlinear element at the same time served in antiphase frequency of the FMS and the high-frequency phase reference wave with a frequency equal to the carrier frequency of the FMS. The result is a comparison of the variable in the time phase of the FMS and the continuous phase of the reference oscillation, which is converting the FMS in amplitude-modulated and fazokodirovannymi signal (afss). The amplitude varies according to the law of change of phase. This signal then undergoes the same transformation as in the amplitude demodulator [Baskakov SR Radio circuits and signals. M.: Vysshaya SHKOLA, 1988, str-292]. This means that the non-linear elements range afss breaks down (decomposes) on low-frequency and high-frequency components. Next, using the lowpass filter is allocated low-frequency component, the amplitude of which varies according to the law changing the phase of the input FMS. Then, with the separation capacity included in the longitudinal chain (sequentially)eliminates constant is leaving, incurred by non-linear elements as a result of interaction with afss. After this low-frequency oscillations, containing useful information are allocated to the low-frequency load.

This method and apparatus can be used for demodulation of frequency-modulated signals (CMS), in which the phase is changed by law, the integral of frequency. For this low-frequency oscillations, containing useful information, you need to apply for a differentiating circuit.

A disadvantage of such a method and device for its implementation is that to highlight the low-frequency signal, the amplitude of which varies in accordance with the law changing the phase of the RF Federal migration service, you must have the generator of the reference oscillation. Another disadvantage is the lack of correction of the amplitude modulation factor afss that when passing through the resonance circuit leads to the decrease of this characteristic, that is, to well-known phenomenon of partial demodulation afss or decreased immunity. The main disadvantage is the small size of the quasi-linear plot of the phase demodulation characteristics due to the use of only reactive elements and lack of choice of their parameters according to the criterion of converting the FMS in afss in the specified frequency band or on a given number of frequencies. Mode is attotney demodulation the main disadvantage is the small size of the quasi-linear plot of the frequency demodulation characteristics due to the use of only reactive elements and lack of choice of their parameters on criterion transformation CMS in amplitude-modulated and CMS (ECMS) in a given frequency band or on a given number of frequencies.

The closest in technical essence and the achieved result (prototype) is a method of demodulating fazokodirovannymi and frequency-modulated signals, consisting in the fact that for demodulation of the FMS and CMS use frequency detector, consisting of a cascade-connected amplitude limiter, Converter CMS ACMS in the form of a parallel oscillatory circuit and a conventional amplitude demodulator. Next, the process of separating the low-frequency component is the same as described above. The peculiarity of the use of this frequency detector for demodulation of the FMS is that if the frequency of the carrier signal FMS is located on the right slope of the amplitude-frequency characteristics (AFC) circuit, the low frequency component serves on the differentiating circuit. If the frequency of the carrier signal FMS is located on the left slope of the frequency response of the circuit, the low frequency component serves on the integrating circuit. As a result, the output devices have a low frequency oscillation, the amplitude of which changes according to the law changing the phase of the input high-frequency photomodeling fluctuations.

The peculiarity of the use of this frequency detector for demodu is acii CMS is if the frequency of the carrier signal CMS feature on the left slope of the frequency response of the circuit. The amplitude of ACMS changed according to the law of change of frequency [Baskakov SR Radio circuits and signals. M.: Vysshaya SHKOLA, 1988, str-292]. If necessary, between the source of modulated signals and the nonlinear element or between the nonlinear element and the load include reactive or resistive two-port network for the coordination and additional selection signal and interference. As a result, the output devices have a low frequency oscillation, the amplitude of which changes according to the law changes the frequency of the input high-frequency customemoticons fluctuations.

The disadvantage of this method and device for its implementation is that after converting the FMS in afss the amplitude modulation factor afss is not controlled and, as a rule, is insignificant, which impairs immunity [Baskakov SR Radio circuits and signals. M.: Vysshaya SHKOLA, 1988, str-292. Gonorovski Istraditionally circuits and signals. M.: Radio and communication, 1986, str-252]. The main disadvantage is the small size of the quasi-linear plot demodulation characteristics due to the use of only reactive elements and lack of choice of their parameters according to the criterion of converting the FMS in afss in the specified frequency band or C is the number of frequencies. In the mode of frequency demodulation the main disadvantage is the small size of the quasi-linear plot of the frequency demodulation characteristics due to the use of only reactive elements and lack of choice of their parameters on the basis of the conversion CMS in amplitude-modulated and CMS (ECMS) in a given frequency band or on a given number of frequencies.

In addition, the classical theory of radio engineering circuits assumes that the nonlinear element is purely resistive and instantaneous, and therefore he does not react to changes in the frequency and phase of the input signal, and responds only to the change of the amplitude. Meanwhile, everyday experience shows that nonlinear elements have an internal capacitance and inductance, which have a significant influence on the formation of the dependence of their conductivity (or resistance matrix elements of the conductance or resistance) from frequency and phase. Especially significant this is evident with increasing frequency, which currently aimed mainly at designers of new systems and radio communications.

Another important drawback of all these methods and devices is that all of the elements of two (MD) made jet that is associated with the desire of developers to pay an additional paragraph shall lose by using comprehensive two-terminal device based on the reactive and resistive elements. When used in the matching devices only reactive or only resistive elements is not always possible to ensure agreement on the criterion of ensuring the required values of the modules and phases of the coefficients of transmission in two States managed nonlinear element is defined by two frequencies of the input FMS or input CMS, in order to form a given slope of the frequency response, because they have certain physical realizability (the editing area of the real and imaginary components of the impedance of the signal source and load), within which implemented these matching conditions (A.A. Golovkov Kompleksirovanii electronic device. M.: Radio and communication, 1996. - 128 S.).

The technical result of the invention is the expansion of the field of physical realizability as areas of change of the real and imaginary components of the impedance of the signal source and the load, within which simultaneously provides the required values of modules and phases of the coefficients of transmission in two States defined by two frequencies of the input FMS or CMS, in order to form a given slope of the frequency response for converting the FMS in afss or CMS in ACMS by optimizing schema and parameter values of the integrated quadrupole simultaneous is velichanii bandwidth, in which this conversion is possible, which increases the noise immunity of the receiver. The ability to change options include a nonlinear element with respect to the matching integrated quadrupole further enhance the field of physical realizability.

1. This result is achieved in that in the known method demodulation fazokodirovannymi and frequency-modulated signals, consisting in the fact that fazokodirovannymi or frequency-modulated signal fed to the demodulator, is made of a quadrupole, a nonlinear element, a lowpass filter, the separation capacity and low load, fazokodirovannymi signal is converted into an amplitude-fazokodirovannymi signal, the frequency-modulated signal is converted into an amplitude-frequency-modulated signal, converting photomodeling signal amplitude fazokodirovannymi signal and the frequency-modulated signal to amplitude-frequency-modulated signal is carried out by feeding these signals on the left slope of the frequency response demodulator, using non-linear element destroy the range of the amplitude-photomodeling signal and the amplitude-frequency-modulated signal into high frequency and low frequency components, the low frequency component serves on the integrating circuit filter lower cha is the one using a lowpass filter emit low-frequency information signal, the amplitude of which changes according to the law of change of phase photomodeling input signal or the law changes the frequency of the frequency-modulated signal, with the separation capacity eliminate the DC component, optionally as a nonlinear element using a three-pole non-linear element, the quadrupole perform complex from reactive and resistive elements, three-pole non-linear element includes between source photomodeling or frequency-modulated signal and the sign of the quadrupole for the common one of the three electrodes, between a quadrupole and a lowpass filter include in the transverse chain introduced high-frequency load set based module transmission the functions of the high-frequency part of the demodulator frequency in order to form a given slope of the amplitude-frequency characteristics provide by choosing according to item z₂₂matrix of resistances of the integrated quadrupole frequency using the following mathematical expression:

where; z₂₁, z₁₁- set the s dependence of the corresponding matrix elements of the complex impedance of the quadrupole frequency in the specified frequency band; m₂₁that & Phi;₂₁- set according to the magnitude and phase of the transfer function from the frequency in the specified frequency band;and,,,- set dependence of the complex elements of the matrix of resistances tripolar nonlinear element from the frequency in the specified frequency band; z₀, z_n- set dependence of the complex impedance of the source photomodeling or frequency-modulated signal and the high-frequency load frequency in the specified frequency band.

2. This result is achieved in that in the known device demodulation fazokodirovannymi and frequency-modulated signals, consisting of a source photomodeling and the frequency-modulated signal, a quadrupole, a nonlinear element, a lowpass filter, the separation capacity and low load, an additional quadrupole performed integrated in the form of the l-shaped connecting two integrated two-terminal device, as a nonlinear element used tripolar nonlinear element, the nonlinear element is included between the source photomodeling or frequency-modulated signal and the sign of the quadrupole for the common one of the said electrodes, between the exit of the quadrupole and the lowpass filter in the transverse chain included introduced high frequency load, the first dvukhpolosnykh G-shaped connection formed of series-connected first resistor dvukhpolosnykh with resistance R₁the first capacitor with capacitance C₁, jet dvukhpolosnykh with predetermined resistance X₀₁X₀₂on the two specified frequencies and connected in parallel between a second resistive dvukhpolosnykh with resistance R₂and the second capacitor with capacitance C₂and the values of the parameters of the first dvukhpolosnykh G-shaped connection determined in accordance with the following mathematical expressions:

;

;

;'

where A=(x₁-X₀₁)²[(r₁-r₂)²+(x₁-X₀₁)²]; B=-2(x₁-X₀₁)(x₂-X₀₂)[(r₁-r₂)²+2(x₁-X₀₁)²]; D=-2(x₁-X₀₁)(x₂-X₀₂)[(r₁-r₂)²+2(x₂-X₀₂)²]; E=(x₂-X₀₂)[(r₁-r₂)²+(x₂-X₀₂)²];r₁, r₂x₁x 2optimal values of the real and imaginary components of the resistance of the first comprehensive dvukhpolosnykh G-shaped connection at two frequencies;- the optimal value of the impedance of the first comprehensive dvukhpolosnykh G-shaped connection at two frequencies;;; Z_2n- set the values of the complex impedance of the second integrated dvukhpolosnykh G-shaped connection at two frequencies; m_21nthat & Phi;_21n- set values of modules and the phase transfer function of the high-frequency part of the demodulator at two frequencies;,,,- set values of a complex matrix elements of tripolar impedance of the nonlinear element at two frequencies; z_0n, z_nn- set values of the complex impedance of the source photomodeling and the frequency-modulated signal and the high-frequency load on two frequencies ω_1,2=2πƒ_1,2; n=1, 2 - rooms two given frequencies ƒ_1,2.

1 shows a diagram of the demodulation device fazokodirovannymi and the frequency-modulated signal is in the (prototype), realising a prototype method.

Figure 2 shows the structural diagram of the device according to claim 2, implements the proposed method according to claim 1.

Figure 3 shows a scheme of the integrated quadrupole proposed device according to claim 2.

Figure 4 shows a diagram of the first comprehensive dvukhpolosnykh, part of the integrated quadrupole proposed device according to claim 2

The device prototype (figure 1) contains the source 1 fazokodirovannymi and frequency-modulated signals, the two-port network 2, the nonlinear element 3, the low pass filter 4 on the elements of R, C, the separation capacity of 5 to item C_pand low-frequency load 6 on the elements of R_nC_n.

The principle of the demodulation device fazokodirovannymi and frequency-modulated signals (prototype) is as follows.

Fazokodirovannymi or frequency-modulated signal from source 1 is fed to the demodulator (figure 1). The principle of the device that implements this method is that by using a reactive two-port network 2, which represents a parallel resonant circuit and connected between the source of the FMS or CMS and a nonlinear element, convert FMS in afss or CMS in ACMS, using non-linear element 3 destroy range of afss or ACMS on high-frequency and low-frequency sostavlyajushie is. The latter are distinguished by using a lowpass filter (integrating circuit) 4 and fed to the low-frequency load 6. The separation capacity of 5 removes the DC component. As a result, the output devices have a low frequency oscillation, the amplitude of which changes according to the law of change of the envelope of high-frequency afss (ACMS), i.e. the law of variation of the phase of the input FMS (frequency input CMS), changing the law of variation of the amplitude of the primary signal. The disadvantages of the method and device for its implementation described above.

High-frequency to low-pass filter) the structural scheme of the generalized proposed device according to claim 2 (figure 2) consists of a cascade-connected source of the FMS and CMS 1, nonlinear three-electrode element 3 (included on the circuit with a common one of the three electrodes), an integrated two-port network 2, and a high-frequency load 7. The low-frequency portion of the structural schema contains the lowpass filter 4, a separating tank 5 and the low frequency load 6. Integrated quadrupole (HT) 2 made in the form of the l-shaped connecting two integrated two-terminal device with impedance Z₁-8, Z₂-9 (figure 3). Frequency dependence of element z₂₂matrix of resistances HT 2 selected from the conditions of formation of quasi-linear slope of the frequency response of the high-frequency part of the demodulator with the ass is nymi values of the module of the transfer function at two predetermined frequencies of the desired frequency band. The implementation of these dependencies is performed by the selection circuit HT in G-shaped link, the optimal frequency dependence of the first comprehensive dvukhpolosnykh-8 of this link and the implementation of this frequency dependence of the selection circuits of the first integrated dvukhpolosnykh of the series-connected first resistor dvukhpolosnykh with resistance R₁10C, a first capacitor with capacitance C₁-11, arbitrary reactive dvukhpolosnykh with resistance X₀-12 and connected in parallel between a second resistive dvukhpolosnykh with resistance R₂-13 and the second capacitor with capacitance C₂-14 (figure 4) and the choice of parameter values R₁, R₂C₁C₂from the condition of ensuring conversion of the FMS in afss and CMS in ACMS by forming a quasi-linear slope of the frequency response of the high-frequency part of the demodulator in the specified frequency band by using certain mathematical expressions.

The principle of operation of this device is that when applying the FMS or CMS from source 1 with an impedance of z₀in the special choice of parameter values R₁, R₂C₁C₂elements of the first comprehensive dvukhpolosnykh G-shaped link is formed, the left slope of the frequency response of the demodulator is set to the specified modules of the transfer function on t is x given frequency of the desired frequency band. It provides a specified amplitude modulation factor afss and ACMS more bandwidth, which increases the noise immunity of the receiver. At the same time the range of afss or ACMS destroyed using nonlinear element 3 connected between the source of the FMS or CMS and quadrupole. In the low-frequency oscillation, the amplitude of which changes according to the law changing the phase of the input FMS or frequency input CMS excels at low load 6, that is the phase or frequency demodulation. While the source impedance of the FMS or CMS and load can be freely selected.

Let us prove the possibility of realization of the specified properties. Let the known dependence of the complex impedance of the load z_nsource of high-frequency signal (FMS and CMS) z₀and the elements of the matrix of resistances tripolar nonlinear element,,,the frequency at a given amplitude of the DC voltage. For simplicity, write the arguments ω=2πƒ (circular frequency) and U I (voltage or current constant amplitude of the power source) are omitted.

Thus, the known matrix of resistances of the transistor:

and the corresponding classical transfer matrix:

where-the determinant of the matrix (1). An asterisk ( * ) entered in the interests of the differences of the elements of the matrix of resistances tripolar element from the corresponding elements of the matrices resistance integrated quadrupole or HT:

and the corresponding classical transfer matrix:

where- the determinant of the matrix (3) subject to conditions of reciprocity quadrupole z₁₂=-z₂₁.

Multiply the matrix (2) and (4). Taking into account the normalization conditions (Feldstein A.L., AVIC LR Synthesis of two-and cosmipolitan on the microwave. M: Communications, 1971. P.34-36) get the total normalized classical transfer matrix of the high-frequency part of the demodulator:

Using known relationships between elements of classical transfer matrix and the elements of the scattering matrix (ibid) subject to (5), we obtain the expression for the transmission coefficient of the high-frequency part of the demodulator:

Physically realizable transfer function associated with the ratio of the front and as follows: .

Suppose you want to define the schema of the integrated quadrupole and values of the complex impedance of the two-terminal component for which it is possible to ensure the specified dependencies module m₂₁and phase φ₂₁the transfer function of the high-frequency part of the demodulator frequency:

After substituting (6) into (7) we obtain a complex equation, the solution of which has the form of the relationship between the elements of the desired matrix of resistances HT, optimal according to the criterion of ensuring the formation of a given quasi-linear slope of the frequency response of the high-frequency part of the demodulator (7) over the entire frequency range:

where;

The resulting relationship (8) between the elements of the transfer matrix of the integrated quadrupole means that the phase demodulators must contain at least one independent dvukhpolosnykh with a complex impedance whose value must satisfy the equation formed on the basis of this relationship. To find the optimal values of parameters of an integrated two-port network, you must choose any scheme of M≥1 dvukhpolosnykh with comprehensive weather resistance is observed find the matrix of resistors whose elements are expressed through the parameters of the scheme of integrated quadrupole, and substitute them into (8). The resulting equation must be solved relative to the resistance of the selected integrated dvukhpolosnykh. The parameter values of the remaining M-1 complex two-terminal device can be set randomly or selected from any other physical considerations. In accordance with the described algorithm obtained the optimal criterion (7) the dependence of the resistance of the first comprehensive dvukhpolosnykh G-shaped connection of two complex two-terminal (figure 3) frequency:

where;; n=1, 2... - non frequency interpolation. Resistance Z_2ncan be chosen arbitrarily or based on any other physical considerations. The index n must be entered in other symbols of physical quantities, explicitly dependent on the frequency.

If frequency response (9) the first comprehensive dvukhpolosnykh G-shaped connection would be provided are specified based on the m₂₁phases φ₂₁transmission ratios of frequency throughout the frequency range. However, the implementation of (9) is continuous, even a very narrow band of frequencies, n is possible.

To implement the optimal approximation (9) on a finite number of frequencies by interpolation it is necessary to form dvukhpolosnykh with an impedance of z_1nof not less than 2N (N is the number of frequency interpolation) of elements of type R, L, C, find the expression for its resistance to equate their optimum values of the resistances of dvukhpolosnykh at a given frequency, defined by the formulas (9)and solve the resulting system of 2N equations for 2N selected parameters R, L, C Values of the remaining elements can be selected randomly or based on any other physical reasons, for example, of the conditions of physical realizability. Let the first dvukhpolosnykh HT with an impedance of z_1nformed of series-connected first resistor dvukhpolosnykh with resistance R₁the first capacitor with capacitance C₁arbitrary reactive dvukhpolosnykh with predetermined resistance X₀₁X₀₂at two frequencies and connected in parallel between a second resistive dvukhpolosnykh with resistance R₂and the second capacitor with capacitance C₂(figure 4). Impedance of the first dvukhpolosnykh HT:

Divide into (10) between a real and imaginary part and for N=2 will make the system of the four equations:

Solution:

;

;'

where A=(x₁-X₀₁)²[(r₁-r₂)²+(x₁-X₀₁)²]; B=-2(x₁-X₀₁)(x₂-X₀₂)[(r₁-r₂)²+2(x₁-X₀₁)²]; D=-2(x₁-X₀₁)(x₂-X₀₂)[(r₁-r₂)²+2(x₂-X₀₂)²]; E=(x₂-X₀₂)[(r₁-r₂)²+2(x₂-X₀₂)²];r₁, r₂x₁x₂optimal values of the real and imaginary components of the resistance of the fourth complex dvukhpolosnykh integrated quadrupole at two frequencies, defined by the formulas (9).

Implementation of optimal approximations of the frequency characteristics of HT (8) using the l-shaped connecting two integrated two-terminal device and the frequency characteristics of the first comprehensive dvukhpolosnykh (9) of this compound using (10), (12) provides increased bandwidth, within which certain deviations provides adjusted based on the m₂₁and phase φ₂₁the transfer function of the high-frequency part is modulator frequency (7). This allows at reasonable choice provisions set frequencies ω₁, ω₂relative to each other to expand the frequency band within which is provided a specified slope of the frequency response in a given frequency band in order to transform the FMS in afss and CMS in ACMS. An additional variation of the values of the elements forming the arbitrary reactive dvukhpolosnykh with resistance X_oneven more increases quasi-linear plot of the slope of the frequency response of the high-frequency part of the demodulator. The frequency characteristics of the impedance of the signal source and the load can be set to any.

The proposed technical solutions are new, because public information is unknown, the method and apparatus demodulation fazokodirovannymi signals, ensuring the transformation of the FMS in afss and CMS in ACMS on a given quasi-linear slope of the frequency response of the high-frequency part of the demodulator in a predetermined frequency band through the use of three non-linear element, the special choice of the frequency dependence of the element z₂₂matrix of resistances integrated two-port network is implemented by the execution of the quadrupole in the form of the l-shaped connecting two integrated two-terminal device, by forming the first integrated dvukhpolosnykh G-shaped connection of the serially connected first resist the ate of dvukhpolosnykh with resistance R ₁the first capacitor with capacitance C₁arbitrary reactive dvukhpolosnykh and connected in parallel between a second resistive dvukhpolosnykh with resistance R₂and the second capacitor with capacitance C₂and the choice of these parameters on the relevant mathematical expressions in the interests of further amplitude demodulation and allocation of the low-frequency component, the amplitude of which varies according to the law changing the phase of the input FMS or frequency input CMS.

The proposed technical solutions involve an inventive step, because of the published scientific data and known technical solution is not obvious that the claimed sequence of operations (execution of a quadrupole complex in view of the above schemes, the inclusion of three nonlinear element between the source of the FMS or CMS and quadrupole for the common one of the three electrodes, the high-frequency connection of the load to the output of the quadrupole, the implementation of optimal frequency dependence of element z₂₂matrix of resistances of the integrated quadrupole perform this quadrupole in the form of the l-shaped connecting two integrated two-terminal device, by forming the first integrated dvukhpolosnykh G-shaped connection from consistently with the United first resistive dvukhpolosnykh with resistance R ₁the first capacitor with capacitance C₁arbitrary reactive dvukhpolosnykh and connected in parallel between a second resistive dvukhpolosnykh with resistance R₂and the second capacitor with capacitance C₂and the choice of these parameters on the relevant mathematical expressions) provide specified according to the magnitude and phase of the transfer function of the high-frequency part of the demodulator frequency in the specified frequency band, within which is provided a specified slope of the frequency response in order to transform the FMS in afss and CMS in ACMS.

The proposed technical solutions are practically applicable, so as to implement them can be used commercially available industry transistors (p-n-p or n-p-n), the inductance and capacitance, formed in the claimed design demodulation. Frequency characteristics of the HT and the first comprehensive dvukhpolosnykh G-shaped connection, the resistance values of resistive elements, and tanks can be determined using the mathematical expressions are given in the claims.

Technical and economic efficiency of the proposed method and device is simultaneously providing the required dependencies of the module and phase of the transfer function of the high-frequency part of the demodulator frequency, which contributes to f is mirovanju given quasi-linear plot of the slope of the frequency response in order to transform the FMS in afss and CMS in ACMS more bandwidth with increased areas of physical realizability as areas of change valid and imaginary components of the impedance of the source of the FMS or CMS and load to further amplitude demodulation and allocation of the low-frequency component, the amplitude of which varies according to the law changing the phase of the input FMS or frequency input CMS, i.e. to provide demodulation of the FMS and CMS.

1. The way demodulation fazokodirovannymi and frequency-modulated signals, consisting in the fact that fazokodirovannymi or frequency-modulated signal fed to the demodulator, is made of a quadrupole, a nonlinear element, a lowpass filter, the separation capacity and low load, fazokodirovannymi signal is converted into an amplitude-fazokodirovannymi signal, the frequency-modulated signal is converted into an amplitude-frequency-modulated signal, converting photomodeling signal amplitude fazokodirovannymi signal and the frequency-modulated signal to amplitude-frequency-modulated signal is carried out by feeding these signals on the left slope of the frequency response of the demodulator, using non-linear element destroys range amplitude-photomodeling signal and the amplitude-frequency-modulated signal into high frequency and low frequency components, the low frequency component serves on the integrating circuit is a lowpass filter, using fil the RA of the lower frequencies emit low-frequency information signal, the amplitude of which changes according to the law of change of phase photomodeling input signal or the law changes the frequency of the frequency-modulated signal, with the separation capacity eliminate the DC component, characterized in that as the nonlinear element using a three-pole non-linear element, the quadrupole perform complex from reactive and resistive elements, three-pole non-linear element includes between source photomodeling or frequency-modulated signal and the sign of the quadrupole for the common one of the three electrodes, between a quadrupole and a lowpass filter include in the transverse chain introduced high frequency load, defined according to the module of the transfer function of the high-frequency part of the demodulator frequency in the interests of formation of a given slope of the amplitude-frequency characteristics provide by choosing according to item z₂₂matrix of resistances of the integrated quadrupole frequency using the following mathematical expressions:

wherez₂₁; z₁₁- set according to the respective elements of the matrix resistors integrated the th quadrupole frequency in the specified frequency band;
m₂₁that & Phi;₂₁- set according to the magnitude and phase of the transfer function from the frequency in the specified frequency band;
,,,- set dependence of the complex elements of the matrix of resistances tripolar nonlinear element from the frequency in the specified frequency band;
z₀, z_n- set dependence of the complex impedance of the source photomodeling or frequency-modulated signal and the high-frequency load frequency in the specified frequency band.

2. The demodulation device fazokodirovannymi and frequency-modulated signals, consisting of a source photomodeling and the frequency-modulated signal, a quadrupole, a nonlinear element, a lowpass filter, the separation capacity and low load, characterized in that the quadrupole is made complex in the form of the l-shaped connecting two integrated two-terminal device, as a nonlinear element used tripolar nonlinear element, the nonlinear element is included between the source photomodeling or frequency-modulated signal and the sign of the quadrupole for the common one of the three electrodes, between the output look no further than the polutnik and lowpass filter in the transverse chain included introduced high frequency load, first dvukhpolosnykh G-shaped connection formed of series-connected first resistor dvukhpolosnykh with resistance R₁the first capacitor with capacitance C₁, jet dvukhpolosnykh with predetermined resistance X₀X₀₂on the two specified frequencies and connected in parallel between a second resistive dvukhpolosnykh with resistance R₂and the second capacitor with capacitance C₂and the values of the parameters of the first dvukhpolosnykh G-shaped connection determined in accordance with the following mathematical expressions:

where A=(x₁-X₀₁)²[(r₁-r₂)²+(x₁-X₀₁)²]; B=-2(x₁-X₀₁)(x₂-X₀₂)[(r₁-r₂)²+2(x₁-X₀₁)²];
D=-2(x₁-X₀₁)(x₂-X₀₂)[(r₁-r₂)²+2(x₂-X₀₂)²]; E=(x₂-X₀₂)[(r₁-r₂)²+2(x₂-X₀₂)²];

r₁, r₂x₁x₂optimal values of the real and imaginary components of the resistance of the first comprehensive dvukhpolosnykh Mr. obras the th connections on two frequencies;
- the optimal value of the impedance of the first comprehensive dvukhpolosnykh G-shaped connection at two frequencies;
Z_2n- set the values of the complex impedance of the second integrated dvukhpolosnykh G-shaped connection at two frequencies;
m_21nthat & Phi;_21n- set values of modules and the phase transfer function of the high-frequency part of the demodulator at two frequencies;
,,,- set values of a complex matrix elements of tripolar impedance of the nonlinear element at two frequencies;
z_0n, z_nn- set values of the complex impedance of the source photomodeling and the frequency-modulated signal and the high-frequency load at two frequencies;
ω_1,2=2πf_1,2; n=1, 2 - rooms two given frequencies f_1,2.