Device to transmit and receive signal and method to transmit and receive signal. RU patent 2491744.

FIELD: radio engineering, communication.

SUBSTANCE: broadcasting signal is transmitted, which contains data for a service and preamble data, at the same time preamble data bits are represented into preamble data symbols, and data bits into data symbols, at least one data slice is developed on the basis of data symbols, a signal frame is created on the basis of preamble data symbols and the data slice, a signal frame is modulated with the help of a multiplexing method with orthogonal frequency division (OFDM), and the modulated signal frame is sent, besides, data symbols of the preamble are divided into at least one unit of the level 1 (L1), besides, the pass band of the unit L1 corresponds to the number of active subcarriers assigned for one channel, and units L1 are repeated in a frequency area along the pass band.

EFFECT: improved efficiency of data transfer and optimised general reliability of a system.

14 cl, 66 dwg

The technical field to which the invention

The present invention relates to a method for transmission and reception of a signal and a device to transmit and receive, and more particularly to a method of signal transmission and receiving, and a device for transmitting and receiving signals improve the efficiency of the data transmission.

The level of technology

When the technology was developed digital broadcast, users got a moving image with high definition (HD). With the continuous development of the compression algorithm and hardware high performance in the future users will be provided the best environment. The system of digital television (DTV) can receive a digital signal broadcast, and provide a variety of additional services to users, as well as video and audio signal.

Digital broadcast video (DVB)-C2 is the third specification to join the family of DVB transmission systems of the third generation. Developed in 1994, modern DVB-C are used in more than 50 millions of cable tuners worldwide. Along with the other systems of the third generation of DVB, DVB-C2 uses a combination of low density parity (LDPC) codes and BCH. This powerful proactive error correction (FEC) provides improved relations carrier-to-noise ratio of about DVB-C is approximately 5dB. Schemes interleave bit optimize overall system reliability FEC. These shots are advanced using the header, called channels physical layer (PLP). One or more of these PLP in a slice of the data. Each slice is used two-dimensional striping (in time and frequency domains), enabling the receiver to exclude the impact of damage packages and frequency of electoral interference, such as one point of entry frequency.

Disclosure of the invention

Technical problem

With the development of these technologies digital broadcast increasing demands for services, such as video and audio signal, and gradually increase the amount of data desired users or the number of channels broadcast.

Technical solution

Thus, the present invention is directed to the method for transmission and reception of a signal and a device for transmission and reception of the signal, which essentially eliminate one or more of the problems caused by deficiencies and limitations of the relevant prior art.

The present invention is to create a method of transmitting a signal receiver broadcast with data services and data of the preamble, the method contains: displays the data bits of the preamble data characters in the preamble, as bits of data in the data characters, at least one slice of the data on the basis of data symbols, creating frame signal on the basis of data symbols of the preamble and slice data frame modulation signal using the method of multiplexing with orthogonal frequency division (OFDM) and transfer of the modulated frame signal, and the characters of data preamble share on at least one power level 1 (L1), and bandwidth block L1 corresponds to the number of active carriers assigned to one channel.

Another aspect of the present invention provides a way of reception of a signal broadcast in a way that contains: demodulation of the received signals using the method of multiplexing with orthogonal frequency division (OFDM), detection frame signal of demodulated signals and frame signal contains the characters of the preamble and the characters of data, inverse mapping in bits for the characters of the preamble and the bits of data symbols and decode bits for the characters of the preamble with schema shortened and decoding of LDPC (low density parity), and the characters of the preamble share on at least one power level 1 (L1), and bandwidth block L1 corresponds to the number of active carriers, assigned to one channel.

Another aspect of the present invention provides transmitter for transmitting the signal receiver broadcast with data services and data of the preamble , and the transmitter contains: the device display, made with the possibility of displaying data bits preamble data characters in the preamble, as bits of data in the data characters device slicing data, made with the possibility of creating at least one slice of the data on the basis of data characters device create a frame, made with the possibility of constructing a frame signal the basis of the character data of the preamble and the slice of the data, modulator, made with the possibility of modulation of the frame signal using the method of multiplexing with orthogonal frequency division (OFDM), and transmission device, made with the possibility of transmission of the modulated frame signal, and the transmitter is designed with the possibility of signal processing, data characters preamble share on at least one power level 1 (L1), and bandwidth block L1 corresponds to the number of active carriers assigned to one channel.

Another aspect of the present invention provides a receiver for reception of a signal broadcast and receiver contains: demodulator, made with the possibility of demodulation of received signals by using the method of multiplexing orthogonal frequency division (OFDM), the unit of analysis of the frame, made with the possibility of obtaining frame signal of demodulated signals and frame signal contains the characters of the preamble and the characters of data, the device of the inverse mapping, made with the possibility of the reverse display the received signal frame the bits for the characters of the preamble and the bits for character data, and the decoder, made with the possibility of decoding bits for characters in the preamble using the shortened and decoding of LDPC (low density parity), and the receiver is made with the possibility of signal processing, and the characters of the preamble share on at least one power level 1 (L1), and bandwidth block L1 corresponds to the number of active carriers assigned to one channel.

Brief description of drawings

Accompanying drawings, which are included to provide additional insight into the invention, and are part of this application and make a part of it, illustrate the option (options) for carrying out the invention and together with the description and serve to explain the principles of the invention.

The drawings:

Figure 1 - example of a 64-quadrature amplitude modulation (QAM), used in the European DVB-t

Figure 2 - way binary code reflected gray (BRGC).

Figure 3 - the output is close to the Gaussian by modifying the 64-QAM used in DVB-t

Figure 4 - distance between the reflected couple in BRGC.

Figure 5 - characteristics of the QAM, where the mirrored pair exists for each axis I and axis Q.

6 is a way to modify QAM using a mirrored pair BRGC.

Fig.7 - example modified 64/256/1024/4096-QAM.

Fig.8-9 - examples of modified 64-QAM using a mirrored pair BRGC.

Figure 10-11 - examples of modified 256-QAM using a mirrored pair BRGC.

Fig.12-fig.13 - examples modified 1024-QAM using a mirrored pair BRGC(0~511).

Figure 14-fig.15 - examples modified 1024-QAM using a mirrored pair BRGC(512~1023).

Fig.16-fig.17 - examples modified 4096-QAM using a mirrored pair BRGC(0~511).

Fig.18-fig.19 - examples modified 4096-QAM using a mirrored pair BRGC(512~1023).

Fig.20-fig.21 - examples modified 4096-QAM using a mirrored pair BRGC(1024~1535).

Fig.22-fig.23 - examples modified 4096-QAM using a mirrored pair BRGC(1536~2047).

Fig.24-fig.25 - examples modified 4096-QAM using a mirrored pair BRGC(2048~2559).

Fig.26-fig.27 - examples modified 4096-QAM using a mirrored pair BRGC(2560~3071).

Fig.28-fig.29 - examples modified 4096-QAM using a mirrored pair BRGC(3072~3583).

Fig.30-fig.31 - examples modified 4096-QAM using a mirrored pair BRGC(3584~4095).

Fig.32 - display example bits modified QAM, where 256-QAM modified using BRGC.

Fig.33 - conversion example MQAM in uneven population.

Fig.34 - example for a system with digital transmission.

Fig.35 - an example of the input processor.

Fig.36 - information that may be included in the base frequency band (BB).

Fig.37 - example BICM.

Fig.38 - example of a shortened/ encoder.

Fig.39 - example of application of the various complexes.

Fig.40 is another example of the cases, when take into account the compatibility between traditional systems.

Fig.41 - frame structure, which contains a preamble for alarm L1 and symbol for the data in the PLP.

Fig.42 - sample device creation of the frame.

Fig.43 - the example of inserting the pilot signal (404)depicted on figure 4.

Fig.44-structure SP.

Fig.45 new structure SP or template pilot signal (PP)5.

Fig.46 - the design 5.

Fig.47 - dependence between the data and the preamble.

Fig.48 - other dependency between the data and the preamble.

Fig.49 - profile example delay cable channel.

Fig.50 - dispersed structure, pilot signal, which uses z=56 and z=112.

Fig.51 - example of a modulator based on OFDM.

Fig.52 - an example of the structure of the preamble

Fig.53 - example of decoding the preamble.

Fig.54 - the process of designing a more optimized preamble.

Fig.55 is another example of the structure of the preamble.

Fig.56 is another example of decoding the preamble.

Fig.57 - an example of the structure of the preamble

Fig.58 - example of decoding L1.

Fig.59 - example analog processor.

Fig.60 - an example of the digital receiver.

Fig.61 - example analog processor used in the receiver.

Fig.62 - example demodulator.

Fig.63 - sample analysis device frame.

Fig.64 - example demodulator BICM.

Fig.65 - example decoding of LDPC using trim/thinning

Fig.66 - a sample output of the processor.

Realization of the invention

Now will be made detailed reference to the preferred embodiments of the present invention, examples of which are illustrated in the accompanying drawings. Where possible, the same reference numbers will be used on all drawings for the designations identical or similar parts.

In the following description of the concept of “service” indicates that any content of a broadcast, which may be transferred or accepted by the device of transmission/reception.

Quadrature amplitude modulation (QAM) using binary code reflected gray (BRGC) is used as the modulation in the environment broadcast, which use traditional modulation encoded bits (BICM). Figure 1 shows an example of 64-QAM is used in the European DVB-t

BRGC can be created using the method shown in figure 2. n bits BRGC can be created by appending a code of (n-1) bits BRGC (i.e. reflected code) to the rear of the (n-1) bits, using add a 0 (zero) to the front side of the original (n-1) bits BRGC and by adding 1 (units) to the front side of the reflected code. Code BRGC created using this method, has a distance between adjacent codes equal to (1). In addition, when used BRGC to QAM, distance between a point and four points, which are most closely related to the point equal to (1), and the distance , between the point and the other four points, which are the second most closely related to the point, is (2). Characteristics such distances between a particular point aggregate and other related points may be called the rule display warming in QAM.

To make the system reliable relative to additive white Gaussian noise (AWGN), the signals are transmitted from a transmitter can be done close to the Gaussian distribution. To be able to do this, the location of points in the set can be modified. Figure 3 depicts the output is close to the Gaussian, by modifying the 64-QAM used in DVB-T. Such a set can be called an uneven QAM (NU-QAM).

To create uneven QAM, can be used Gaussian cumulative distribution function (CDF). In case of 64, 256 or 1024-QAM, i.e. 2^N AM QAM can be divided into two independent N-PAM. By splitting the Gaussian CDF N sections of equal probability and using the assumptions to point signal in each section represented the partition can be created in the aggregate, has a Gaussian distribution. In other words, coordinate xj newly defined uneven N-PAM can be defined as follows:

Equation 1

Figure 3 is an example of a conversion 64QAM DVB-T in NU-64QAM using the aforementioned methods. Figure 3 represents the result of modification of the coordinates of each axis I and axis Q using the aforementioned methods and display the previous points collectively in the newly defined coordinates. In the case of 32, 128 or 512 QAM, i.e. cruciate QAM, which is 2^N QAM, by modifying accordingly Pj, can be found a new coordinate.

One variant of the implementation of the present invention can modify QAM using BRGC using characteristics BRGC. As shown in figure 4, distance between the reflected couple in BRGC equal to one, since it differs only one bit that is added to the front of each code. Figure 5 depicts the characteristics of the QAM, which reflected a pair exists for each axis I and axis Q. This figure reflected a pair exists on each side of a solid line of dots.

By using mirrored pairs, existing in QAM, average power aggregate QAM can be reduced, at the same time, supporting the rule display warming in QAM. In other words, in a population in which the average power is normalized to 1, in the aggregate, may be increased minimum Euclidean distance. When this modified QAM apply to systems of broadcasting or communication can either system, more reliable relatively noise, using the same energy as a traditional system, or a system with the same level of performance that the traditional system, but that uses less energy.

Figure 6 depicts a way to modify QAM using a mirrored pair BRGC. Fig.6 depicts the aggregate, and fig.6b depicts a block diagram of the sequence of steps for modifying QAM using a mirrored pair BRGC. First, there must be found a focal point that has the highest power, points to the population. Suitable points are points where can move the target point, and they are the closest neighbouring points in the mirrored pair to the target point. Then among the appropriate points must be found empty point (i.e. the point, which was not yet taken other points), has the lowest power, and compare the power of the target point and capacity of proper point. If the power of the proper point less, the target point is moved to the appropriate point. This process is repeated until the average power points in the aggregate not reach a minimum, at the same time, supporting the rule display warming.

Fig.32 shows an example display bits modified QAM, where 256-QAM modify using BRGC. Fig.32 and fig.32b represent the largest display of significant bits (MSB). The point marked as being filled circles represent display units, and the points marked as empty circles are zeros. In the same way, every bit display, as shown in figures (a) to (h), on fig.32, until not make the least significant bits (LSB). As shown in the fig.32, modified QAM can give possibility to solve bit using only axis I or Q, as the traditional QAM, except the bit that follows the MSB (fig.32 and fig.32d). Using these characteristics can be created with a simple receiver using a partially modified receiver for QAM. Effective receiver can be done by checking the values for both I and Q only in determining the bit after the MSB and by calculating only I or Q for the remaining bits. This method can be used to approximate a LLR, the exact LLR or tough decision.

By using a modified QAM or MQAM that uses features of the above-mentioned BRGC could be an uneven set or NU-MQAM. In the above equation, which used the Gaussian CDF, Pj which can be modified to fit MQAM. Just as QAM, MQAM can be considered on two FRAMES with axis I and axis Q. However, unlike QAM, in which the number of points corresponding to the value of each axis of FRAMES is the same MQAM number of points varies. If the number of points, which corresponds to the j-th value of the FRAMES, determined as in nj MQAM, where there are all the points together, then Pj can be defined as follows:

Equation 2

Through the use of a particular Pj MQAM can be converted into non-uniform set. Pj can be defined as, for example, 256-MQAM.

Fig.33 is an example of transformation MQAM in uneven population. NU-MQAM, created using these methods, it can support receivers MQAM with modified coordinates of each of the FRAMES. Thus, can be made effective receiver. In addition, can be implemented, a more robust relative to the noise than the previous NU-QAM. For a more effective system to broadcast a possible hybridization MQAM and NU-MQAM. In other words, the system is more robust relative to the noise can be implemented using MQAM for the environment that is used code with error correction with high speed code, and otherwise by the use of NU-MQAM. For this case transmitter can allow the receiver had information on the speed of your code with error correction used currently, and modulation type used in the current moment, so that the receiver can analyze in accordance with the modulation used in the current moment.

Fig.34 shows an example of a digital transmission. The input data may contain some number of threads MPEG-TS or threads GSE (total encapsulation flow). Module 101 input processor may add transmission parameters in the input stream and to plan for the module 102 BICM. Module 102 BICM can add redundancy and error correction data transmission channel. Device 103 create a frame can create keyframes using the add alarm physical level and pilot signals. Modulator 104 can perform modulation relative to input characters in effective ways. Analog processor 105 can perform various processes for the conversion of input digital signals to analog output signals.

Fig.35 depicts an example of the input processor. Input stream MPEG-TS, or GSE can be converted by using the input processor in the total number n of threads that will be processed independently. Each of these threads may be either full frame TS, which includes many components of services, or the minimum frame TS, which includes a component services (such as video or audio). In addition, each of these threads may be a flow of GSE, which transmits, or the set of services, or a favor.

Module 202-1 input interface may appoint a certain number of input bits are equal to the maximum capacity of the data field of the frame main frequency bands (BB). Filling can be inserted to complete the capacity of the code block LDPC/BCH. Module 203-1 synchronization input stream may provide a mechanism to re-generate in the receiver heartbeats transport stream (or bagged a generalized flow), in order to ensure cross-cutting constant bit rate and delay.

To allow the re-unification of the transport stream without requiring additional memory in the receiver input transport streams detained by compensators 204-1~n delay, given the options interleave PLP data in the group, and the associated common PLP. Modules 205-1~n removal of an empty package can increase the transmission efficiency by removing inserted an empty package for the case of services VBR (variable bit rate). Modules 206-1~n encoder control cyclical excessive code (CRC) can add parity, CRC, to increase the reliability of the frame transmission CENTURIES. Modules 207-1~n insert a header CENTURIES can add the header frame CENTURIES in the initial part of the frame CENTURIES. Information that may be included in the header of the CENTURIES, is depicted on fig.36.

Module 208 of the device of Association/ slicing can perform cutting frame CENTURIES of each PLP, Association of personnel CENTURIES from a variety of PLP and planning each frame CENTURIES in the frame transmission. Therefore, the module 208 of the device of Association/device slicing can display information alarm L1, which relates to the appointment of the PLP in the frame. Finally, the module 209 device encryption CENTURIES can randomize the input bit streams to minimize the correlation between bits in the bit streams. Modules in the shadow of the fig.35 modules are used when the transmission system uses a single PLP other modules on fig.35, modules are used when the transfer device uses a lot of PLP.

Fig.37 depicts an example of a module BICM. Fig.37 depicts the route data, and fig.37b depicts the route L1 module BICM. Module 301 external encoder module and 303 of the internal encoder can add redundancy to the input bit streams for error correction. Module 302 external and module 304 internal can bits to warn error package. Module 302 external can be skipped if BICM is designed specifically for DVB-S2. Module 305 demultiplexer bit can manage the reliability of each bit derived from the module 304 internal . Module 306 device display characters can display the input bit streams in streams of characters. In this moment you can use any of the traditional QAM, MQAM, which uses the BRGC to improve performance, NU-QAM, which uses non-uniform modulation, or NU-MQAM that uses applied BRGC uneven modulation to improve performance. To design a system that is more robust relative to the noise can be considered a combination of modulations using MQAM and/or NU-MQAM, depending on the speed of your code or code with error correction and capacity of the population. At this point in time module 306 display device characters can use the appropriate set in accordance with the speed of the code and the capacity of a population. Fig.39 shows an example of such combinations.

Case 1 shows an example of the use of NU-MQAM at low speed of the code for the implementation of the simplified system. Case 2 shows an example of the use of optimized conjunction with each speed of your code. The transmitter can send information about the speed of code with error correction and capacity of the population in the receiver, so that the receiver can use a matching set. Fig.40 represents another example of cases in which take into account the compatibility between traditional systems. In addition to the examples, other combinations possible to optimize the system.

Module 307 insert header ModCod, depicted on the fig.37, can take the information feedback adaptive coding and modulation (ACM)/AC coding and modulation (VCM) and add information about a parameter used when encoding and modulation, block FEC as a header. Title modulation type/speed of your code (ModCod) may include the following information:

type the FEC (1 bit) - long or short LDPC,

the speed of the code (3 bits),

modulation (3-bit) up to 64K QAM,

ID PLP (8 bits).

Module 308 characters can perform alternation in the character field to get more results alternations. Similar processes made about the route of the data, can be made about the route of the alarm L1, but possibly with different parameters (301-1~308-1). At this point module (303-1) a shortened/ code can be used for internal code.

Fig.41 shows the structure of the frame that contains a preamble for alarm L1 and symbol for the data in the PLP. You can see that the preamble and data symbols generate cyclically using the same frame as the unit. Characters contain data type 0 PLP passed using the fixed modulation/coding, and type 1 PLP passed using the variable modulation/coding. For type 0 PLP information such as modulation, FEC type and speed of the code FEC, passed in the preamble (see box 401 header frame fig.42) For type 1 PLP relevant information may be transmitted in the header block FEC character data (see box 307 header ModCod fig.37). By splitting the types of PLP amount of overhead ModCod may be reduced by 3 about 4 percent of the full speed transmission for type 0 PLP passed with fixed bit rate. Receiver for fixed modulation/coding PLP type 0 PLP device r401 delete a frame header, shown in fig.63 can derive information on the modulation and speed of your code FEC and provide the extracted information in the module decoding BICM. For variable modulation/coding PLP type 1 PLP modules r307 and r307-1 extract ModCod depicted on fig.64 can extract and provide the parameters necessary for decoding BICM.

Fig.42 shows an example of creation device frame. Module 401 insert frame header can form the frame of the input character streams and can add frame header front of each transmitted frame. Frame header may include the following information:

the number of channels (4 bits),

guard interval (2 bits),

PARP (2 bits),

template pilot signal (2 bits),

digital identification system (16 bits),

frame ID (16 bits),

frame length (16-bit) characters multiplexing with orthogonal frequency division (OFDM) to the frame

length (16-bit) number of frames ,

the number of PLP (8 bits),

for each PLP

identification of PLP (8 bits),

the connection ID of the channel (4 bits),

the beginning of the PLP (9 bits),

type PLP (2 bits)PLP or other,

the type of payload PLP (5 bits),

type of MS (1 bit)-fixed/variable modulation and coding,

if the type of MS= fixed modulation and coding,

type the FEC (1 bit)-long or short LDPC,

the speed of the code (3 bits),

modulation (3 bits)-up to 64K QAM,

end if;

the number of channels the mark (2-bit

for each mark,

beginning mark (9 bits),

the width of the mark (9 bits)

end;

width PLP (9 bits)-the maximum number of blocks FEC PLP

type interleave time PLP (2 bits)

end;

CRC-32 (32-bit).

Assume that binding framework channel for information L1 transmitted in the header of the frame and the data that correspond to each slice of the data defined as the PLP. Therefore, information such as the ID of the PLP, the linkage identifier of the channel and the starting address of the PLP is required for each channel used in the binding. One way of implementing this invention provides transfer field ModCod in the header frame FEC, if the type of the PLP supports variable modulation/coding and transmission fields ModCod in the header of the frame, if the type of the PLP supports fixed modulation/coding to reduce the amount of overhead alarm. In addition, if there is a band of frequencies mark for each of the PLP, the transfer of the initial address of the mark and its width becomes necessary decoding relevant bearing in the receiver.

Fig.43 shows an example of a template 5 pilot signal applied in an environment linking the channel. As shown, if the position SP coincide with the positions of the pilot signal preamble, may appear irregular structure, pilot signal.

Fig.43 depicts an example of a module 404 insert a pilot signal, as illustrated on the fig.42. As shown in Fig.43, if you use the same frequency band (for example, 8 MHz), the available bandwidth is equal to 7.61 MHz, but if you connect set of frequency bands, protective strips of frequencies can be removed, thus, the efficiency of the frequency may increase greatly. Fig.43b is an example of a module 504 insert the preamble, as depicted in fig.51 passed in the front of frame and even binding channel, the preamble has repetition rate equal to 7.61 MHz, which is the bandwidth block L1. This is a structure that takes into account the bandwidth of a tuner that performs an initial scan channel.

In detail, if the distance between z scattered pilot signals (SP) in the symbol of OFDM is 48 and if the distance y SP corresponding to a particular carrier SP, along the x-axis is equal to 4, the actual distance x after interpolation time is 12. This is the case when the share of the guard interval (GI) is equal to 1/64. If the share GI equal to 1/128, can be used x=24, y=4, z=96. If you use linking the channel position SP can be made to coincide with the positions of the pilot signal of the preamble by generating a non-consecutive points in the structure of the scattered pilot signal.

At this point in time position pilot signal preamble may coincide with each and positions SP character data. When using the linking of the channel cross-section data, and pass their service can be specified independently from the granulation bandwidth of 8 MHz. However, to reduce the overhead for addressing slice of the data can be selected transmission, starting from the position of the SP and ending in the position of the SP.

When the receiver accept such SP, if necessary, the module r501 channel estimation, depicted on the fig.62 can resample the time to get the pilot signals depicted lines as points on Fig.43, and resample the frequency. At this point of time for non-consecutive points intervals of them designated as 32 on Fig.43, can be carried out either interpolation left and right or interpolation only on one side, then interpolation on the other side using already interpolated positions pilot signal, interval equal to 12 as checkpoint. At this time of the cutting width data can vary to 7.61 MHz, thus, the receiver can minimize power consumption by running the channel estimation and decoding only necessary carriers.

Fig.44 represents another example 5 applied in an environment linking the channel or the structure of SP to maintain the actual distance x as 12, to avoid irregular structure SP depicted on the Fig.43, use when linking the channel. Fig.44 is a structure of SP for character data, and fig.44b is a structure of SP for the character of the preamble.

As shown, if the distance SP maintain a constant in the case of binding channel won't be a problem in the interpolation frequency, but the position of the pilot signal between the data and the preamble may not coincide. In other words, this structure does not require additional channel estimation for irregular structure SP, however the positions SP used in the binding of the channel and the position of the pilot signal preamble become different for each channel.

Fig.45 depicts the new structure of the SP or 5 to provide a solution to the two above-mentioned problems, in an environment linking the channel. Specifically, the distance pilot signal x=16 can solve these problems. To preserve the density of pilot signal or maintain the same amount of overhead 5 can have x=16, y=3, z=48 for GI=1/64, and 7 can have x=16, y=6, z=96 for the GI=1/128. Can still be supported functionality interpolation only the frequency. Position pilot signal is depicted in fig.45 for comparison with the structure of 5.

Fig.46 shows an example of a new template SP or patterns 5 in an environment linking the channel. As shown in the fig.46 use either single channel or channel linking can be achieved actual distance pilot signal x=16. In addition, because of the position of the SP can be made to coincide with the positions of the pilot signal preamble, can be deterioration of channel estimation caused by the irregularity SP, or divergent positions SP. In other words, there is no irregular position of the SP for the interpolator frequency, and ensured correlation between the positions of the preamble and the SP.

Therefore, the proposed new template SP can be advantageous in that one template SP can be used both for one and for the associated channel, no irregular structure, pilot signal may not be called, so you can have a good channel estimation, the positions of both the preamble and pilot signal SP can be supported by matching density pilot signal can be sustained by the same as for 5 and 7, respectively, and can also be saved functionality interpolation only the frequency.

In addition, the structure of the preamble can meet the requirements such as: the position of the pilot signal preamble should cover all possible positions SP for initial receipt of the channel, the maximum number of bearing should be 3409 (to 7.61 MHz) for the initial scan, exactly the same templates pilot signal and sequence of encryption should be used for the detection of C2 and does not require any specific for the detection of the preamble, as P1, in T2.

In terms of structure frame, granulation position slice of the data can be modified in 16 sub-carriers, and not 12, thus, there may be a smaller amount of overhead addressing position, and no problems regarding the state of the data slice. You can expect the zero state of the interval of time, and so on

Now on the requirements related to the structure of the preamble and the pilot signal, there is consistency in these positions pilot signals of the preamble and the SP should be the same regardless of linking the channel, the number of carriers in the block L1 should be shared at a distance pilot signal to avoid irregular structure on the edge of bandwidth, blocks L1 should be repeated in the frequency domain, and blocks L1 should always be in arbitrary position of the window tuner. Additional requirements would be that the positions of the pilot signal and templates should be repeated with a period of 8 MHz, valid offset carrier frequency shall be appraised without knowledge binding channel, and decoding L1 (rearrange) cannot be offset by frequency offset.

Fig.47 depicts the dependence between the data and the preamble, when the use patterns of the preamble, as shown in the fig.51 and fig.53. Block L1 can be repeated with a period of 6 MHz. To decode L1 must be found pattern as the frequency offset and the offset of the preamble. Decoding L1 impossible in arbitrary position of the tuner without information about linking the channel, and the receiver cannot distinguish between an offset value of the preamble and the frequency offset.

Thus, the receiver, specifically for the device r401 remove the frame header is illustrated on the fig.63 to perform the decoding of the signal L1, requires that was obtained structure linking the channel. Since the offset of the preamble, expected in two vertically shaded areas on fig.47 is known, the module r505 synchronization time/frequency fig.62 can evaluate offset carrier frequency. Based on the assessment of the route alarm L1 (r308-1 CRC r301-1) on fig.64 can decode L1.

Fig.48 depicts the dependence between the data and the preamble, when the use patterns of the preamble, as shown in the fig.55. Block L1 can be repeated with a period of 8 MHz. To decode L1 is required to find the offset, frequency, and channel linking may not be required. Frequency offset can be easily assessed by using a known sequence of pseudorandom binary sequence (PRBS). As shown in the fig.48, symbols of the preamble and aligned data, thus, additional search synchronization can be redundant. Therefore, for the receiver, specifically for the device r401 remove the frame header is illustrated on the fig.63, perhaps that should be obtained only the maximum correlation sequence without encryption pilot signal, to perform the decoding of the signal L1. Module r505 synchronization time/frequency fig.62 can evaluate offset carrier frequency of the position of the maximum.

Fig.49 shows an example of delay profile of the cable channel.

In terms of design, pilot signal existing GI already with the reserve protects the propagation delay of the cable channel. In the worst case, the option may be to re-designing the model of a channel. To repeat the pattern exactly every 8 MHz, distance pilot signal should be divider 3584 bearing (z=32 56). The density of the pilot signal z=32, may increase the amount of overhead pilot signal, thus, can be selected z=56. A little less coverage of the delay may be unimportant in the duct. For example, it can be 8μs for PP5 and 4μs for PP7 compared with 9,3μs (PP5) and 4,7μs (PP7). Significant delays can be covered by both templates pilot signal, even in the worst case. For the position of the pilot signal of the preamble are needed not more than all the positions of the SP in the symbol of the data.

If the route delay -40 dB can be ignored, the actual propagation delay can be 2,5μs, 1/64 GI=7μs or 1/128 GI=3,5μs. This shows that the distance parameter pilot signal z=56 can be good enough value. In addition, z=56 can be a useful value for the structuring of the template pilot signal, which gives the opportunity structure of the preamble, shown in fig.48.

Fig.50 shows the structure of the scattered pilot signal, which uses z=56 and z=112, designed 404 module insertion pilot signal on fig.42. Proposed 5 (x=14, y=4, z=56) and 7 (x=28, y=4, z=112). Extreme bearing could be inserted for closing edge.

As shown in the fig.50, the pilot signals are aligned on 8 MHz from each edge bands, each position pilot signal and the structure of the pilot signal may be repeated every 8 MHz. Thus, this structure can support structure of the preamble, as shown in fig.48. In addition, may be used in the General structure of a pilot signal between the characters of the preamble and data. Therefore, the module r501 channel estimation on fig.62 you can evaluate a channel using interpolation regarding the character of the preamble and data, as may be designated by irregular template pilot signal, regardless of the position of the window you choose with the help of locations slice of the data. At this point in time use only interpolation frequency may be sufficient to compensate for distortion channel of propagation delay. If, in addition, perform the interpolation of time, can be made more accurate estimate of the channel.

Hence, in the new proposed template pilot signal position and template pilot signal may be repeated on the basis of the period of 8 MHz. One template pilot signal can be used for characters as the preamble, and the data. Decoding L1 can always be possible without the knowledge of linking the channel. In addition, the proposed template pilot signal may not affect the coincidence with KZT2, because it can be used the same strategy, pilot signal template scattered pilot signal, T2 already uses 8 different templates pilot signal and considerable difficulty receiver may not be increased by means of the modified template pilot signal. For a sequence of encryption pilot signal period PRBS can be 2047 (m-sequence), generation PRBS can be reinstalled every 8 MHz, the period which is equal to 3584, the repetition rate of the pilot signal, equal to 56, can also be supplied together 2047, and you can not expect any problems PARP.

Fig.51 depicts an example of a modulator based on OFDM. Input streams of characters can be converted to the time domain by using the module 501 IFFT. If necessary, the ratio of maximum to average power (PARP) can be reduced in a module 502 reduce the PARP. For ways PARP can be used extension to the active population (ACE) or redundancy tone of the parcel. Module 503 insert GI can copy the last part of the effective OFDM symbol to fill the guard interval, in the form of cyclic prefix.

Module 504 insert the preamble can insert the preamble front of each transmitted frame so that the receiver can detect a digital signal frame and get the collection of displacement time/frequency. At this time of the signal preamble may perform signaling, the physical layer, such as the size of the FFT (3 bits) and the size of the guard interval (3 bits). Module 504 insert preamble may be skipped if the modulator is designed specifically for DVB-C2.

Fig.52 depicts an example of the structure of the preamble to link channel generated module 504 insert the preamble to fig.51. One complete unit

L1 should be “always ” in any arbitrary position setup window to 7.61 MHz and should not have a designated loss alarm L1, regardless of the position of the window. As shown, blocks L1 can be repeated in the frequency domain with a period of 6 MHz. Character data may be associated with the channel for each of 8 MHz. If for decoding L1 tuner receiver uses, such as tuner r603 presented at fig.61 that uses bandwidth to 7.61 MHz, the device r401 remove the header of the frame on the fig.63 should reorder adopted shifted cyclically block L1 (fig.53) in its original form. This reordering is possible, because the L1 repeat for each block of 6 MHz. Fig.53 can be in fig.53b.

Fig.54 depicts the process of designating more optimized preamble. The structure of the preamble fig.52 only uses 6 MHz of the entire bandwidth to 7.61 MHz tuner for decoding L1. From the point of view of efficiency of spectrum bandwidth to 7.61 MHz tuner is not completely used. Consequently, there may be additional optimisation of the efficiency of spectrum.

Fig.55 represents another example of the structure of the preamble or patterns of characters of the preamble to the full effectiveness of the spectrum generated in a module 401 insert frame header on fig.42. Just as data character blocks L1 can be repeated in the frequency domain with a period of 8 MHz. One complete unit L1 still is “always ” in any arbitrary position setup window to 7.61 MHz. After the configuration data to 7.61 MHz can be considered as virtually evenly spaced code. Having exactly the same bandwidth for characters as the preamble, and the data and exactly the same structure, pilot signal for the characters as a preamble, and data, you can maximize the effectiveness of the spectrum. Other symptoms such as cyclically shifted feature and not sending the unit L1 in case of absence of data slice, can remain unchanged. In other words, bandwidth characters preamble may be identical bandwidth character data or, as depicted in the fig.57, bandwidth characters preamble may be bandwidth tuner (in this example, it is equal to 7.61 MHz). Bandwidth tuner can be defined as bandwidth, which corresponds to the number of all active carriers when using one channel. That is, bandwidth symbol preamble may correspond to the number of all active carriers (in this example, it is equal to 7.61 MHz).

The number of active carriers on the channel can be different, depending on the method of counting, as would any person skilled in the art. That is, the fig.46 passed 3409 active carriers on one channel, in accordance with the bandwidth to 7.61 MHz. However, if not counting any edge of the channel, we can say that the number of carriers on one channel is 4308.

Fig.56 depicts virtually evenly spaced code. Data to 7.61 MHz from the block L1 8 MHz can be considered as thinned encoded. When the tuner r603, depicted on the fig.61, uses bandwidth to 7.61 MHz to decode L1, the r401 delete a frame header, shown in fig.63 must rearrange adopted shifted cyclically block L1 in the original form, as shown in the fig.56. At this point, perform the decoding L1 using the entire bandwidth of the tuner. If a block is L1 resequenced, range reordered block L1 can have an empty area of the spectrum, as shown in the upper right side of the fig.56 because the original block size L1 equal to the bandwidth of 8 MHz.

If an empty area is filled with zeros, either after the abolition of alternations in character area using your device r403 cancellation alternation frequency fig.63 or by using the device r308-cancel 1 interleave characters on fig.46 or after the abolition of alternations in the field of bits via the device r306-1 reverse display, multiplexer r305-1 bit and internal device r304-cancel 1 interleave on fig.64, the unit may have the appearance that seems as evenly spaced as shown in the lower right side of the fig.56.

This block L1 can be decoded in the module r303-1 /a shortened decoding on fig.64. Using this structure, the preamble may be used bandwidth tuner, thus, can be increased spectrum efficiency and win encoding. In addition, the same bandwidth and structure, pilot signal may be used for the characters of the preamble and data.

In addition, if the bandwidth of the preamble or the bandwidth of the symbols of the preamble installed as bandwidth tuner, as shown in the fig.58 (it is equal to 7.61 MHz in the example), a full block L1 can be obtained after reordering, even without thinning. In other words, for the frame that has the characters of the preamble, in which the characters of the preamble have at least one power level 1 (L1), we can say that the block is L1 has 3408 active carriers, and 3408 active carriers correspond to 7.61 MHz radio frequency (RF) band of frequencies of 8 MHz.

Thus, can be maximized the efficiency of spectrum and the decoding performance L1. In other words, the receiver decoding can be done in the module r303-1 /a shortened decoding on fig.64 only after the abolition of alternations in the character of the region.

Therefore, the proposed new structure of the preamble can be advantageous in that it is fully compatible with earlier used in the preamble, except that bandwidth is another, blocks L1 repeat with a period of 8 MHz, block L1 can be always , regardless of the position of the window tuner, full band tuner can be used to decode L1, maximum efficiency of spectrum can guarantee a greater gain coding, incomplete block L1 can be considered as evenly spaced encoded simple and the same structure pilot-the signal can be used for both the preamble and to the data and the same bandwidth can be used for both the preamble and to the data.

Fig.59 shows an example of analog processor. Module 601 DAC can convert entered the digital signal into an analog signal. After the transfer bandwidth convert with increase of frequency (602), and can be sent analog filtered (603) signal.

Fig.60 depicts an example of the digital receiver. The received signal is converted into a digital signal in the module r105 processing of the analog signal. Demodulator r104 can convert the signal in the frequency domain data. Device r103 analysis of the frame can delete the pilot signals and headers and gives a selection of information about the service, which must be decoded. Demodulator r102 BICM can correct errors in the transmission channel. Output processor r101 can recover originally passed thread services and alarm information.

Fig.61 shows an example of analog processor used in the receiver. Module r603 tuner/AGC can select the desired bandwidth of the signal. Module r602 conversion can recover baseband. Module r601 ADC can convert an analog signal into a digital signal.

Fig.63 shows an example of analysis device frame. Module r404 removal pilot signal can delete a character, pilot signal. Module r403 cancellation alternation frequency can perform cancellation alternations in the frequency domain. Device r402 Association OFDM symbol can recover data frame of streams of characters to be passed in the OFDM symbols. Module r401 remove the header of the frame can extract alarm physical layer of the header of each transmitted frame and remove the header. The retrieved information can be used as parameters for the following treatments in the receiver.

Fig.64 shows an example of the demodulator BICM. Fig.64 depicts the route data, and fig.64b depicts the route alarm L1. Device r308 cancellation interleave characters can perform cancellation alternations in the character of the region. Device r307 extraction ModCod can retrieve the parameters ModCod from the front of each frame CENTURIES and do the options available for the following processes of adaptive/variable demodulation and decoding. Device r306 reverse display characters may display back input streams of characters in a bit streams of the coefficient of the logarithm of the probability (LLR). Output bit streams LLR can be calculated with the use of the aggregate used in the device 306 display characters transmitter as a reference point. At this point in time, when using the above MQAM or NU-MQUAM, by calculating any axis I or axis Q calculating bit, nearest MSB and by calculating any axis I or axis Q when calculating other bits may be exercised effective device of the inverse mapping of characters. This method can be applied, for example, to approximate the LLR, for the exact LLR or hard decisions.

When using the optimized set, in accordance with the aggregate capacity and speed of the code, with the correction of errors in the device 306 display characters transmitter device r306 reverse display characters receiver can receive the totality of using information on the speed of your code and capacity aggregate transmitted from a transmitter. Multiplexer r305 bit of a receiver can perform the inverse function demultiplexer 305 bit transmitter. Internal structure of the r304 cancellation interleave and the external device r302 cancellation interleave receiver can perform the inverse functions of the internal 304 and external 302 transmitter, accordingly, to receive the bit stream in its original sequence. External device r302 cancellation alternations can be skipped if demodulator BICM is specifically for DVB-C2.

The internal decoder r303 and external decoder r301 receiver can perform the appropriate decoding processes in the internal encoder 303 and external encoder 301 transmitter, respectively, in order to correct errors in the transmission channel. Similar processes made about the route of the data, can be made about the route of the alarm L1, but with different parameters (r308-1 CRC r301-1). At this point in time, as explained in the part of the preamble, the module r301-1 shortened/ code can be used to decode the signal L1.

Fig.65 shows an example of decoding LDCP using trim/thinning. The demultiplexer r301a may separately withdraw the information part and a part of parity systematic code of the input bit-streams. For information part-zeroing (r302a) can be performed in accordance with the number of input bit streams LDPC decoder, for part of the examination by the parity of the input bit streams for (r303a) LDPC decoder can be generated using undo thinning covered part. Decoding (r304a) LDPC can be done in the generated bit streams, zeros in the information part can be removed and withdrawn (r305a).

Fig.66 shows an example of the output of the processor. Device r209 decryption CENTURIES can restore encrypted (209) bit streams in the transmitter. Separator r208 can recover frames CENTURIES, which correspond to the multitude of PLP that and passed from the transmitter in accordance with the route of the PLP. For each route PLP device r207-1 CRC n can delete the header, which is referred to in the front part of the frame CENTURIES. Decoder r206-1 CRC n can perform the decoding of the CRC and to build robust frames CENTURIES available for selection. Modules r205-1 CRC n inserting empty packages can restore the packages that have been removed for more high transfer efficiency, in their original location. Modules r204-1 CRC n delay recovery can recover the delay between each route PLP.

The transmission of information ModCod in the header of each frame CENTURIES, which is necessary to ACM/VCM, and transfer the rest of the alarm physical layer in the header of the frame, can be minimized amount of overhead alarm.

Can be implemented modified QAM for more energy-efficient transfer or a more reliable in terms of noise digital broadcasting system. The system may include the transmitter and receiver for each of the disclosed example and their combination.

Can be carried out improved uneven QAM for more energy-efficient transfer or a more reliable in terms of noise digital broadcasting system. Also explains how to use speed code with error correction NU-MQAM and MQAM. The system may include the transmitter and receiver for each of the disclosed example and their combination.

The proposed method of signaling L1 can reduce the amount of overhead on 3 about 4 percent by minimizing overhead alarm during linking the channel.

Persons skilled in the art would understand that in the present invention may be made various modifications and changes, which go beyond the invention.

1. A method of transmission in the receiver signal broadcast that contains data for the services and the data of the preamble, the method contains the stages at which display the data bits of the preamble data characters in the preamble, and the bits in the data characters, create at least one slice of the data on the basis of data symbols, create frame signal on the basis of data symbols of the preamble and the slice of the data, modulate frame signal by using method multiplexing with orthogonal frequency division (OFDM) and modulated transmit frame signal, and the characters of data preamble divided into at least one power level 1 (L1), and bandwidth block L1 corresponds to the number of active carriers assigned to one channel, and blocks L1 repeated in the frequency bandwidth.

2. The method according to claim 1, wherein bandwidth block L1 equal to 7.61 MHz.

3. The method according to claim 1, wherein a block L1 has the alarm information L1 for a slice of the data.

4. The method according to claim 1, additionally contains a stage at which encode using LDPC data preamble using the shortened and LDPC.

5. A way of reception of a signal broadcast in a way that contains the stages at which incoming signals with the help of a method multiplexing with orthogonal frequency division (OFDM), can detect a frame signal of demodulated signals and frame signal contains the characters of the preamble and the characters of data, display back into bits for the characters of the preamble and the bits for character data and decode bits for characters the preamble using the shortened and decoding of LDPC (low density parity), and the characters of the preamble divided into at least one power level 1 (L1), and bandwidth block L1 corresponds to the number of active carriers assigned to one channel, and blocks L1 repeated bandwidth.

6. The method according to claim 5, which bandwidth block L1 equal to 7.61 MHz.

7. The method according to claim 5, which block L1 has the alarm information L1 for a slice of the data.

8. Transmitter for transmitting the signal receiver broadcast, containing data for services and data of the preamble, the transmitter has a display device, made with the possibility of displaying data bits preamble data characters in the preamble, as bits of data in the data characters device slicing data, made with the possibility of creating at least one slice data on the basis of data characters device create a frame, made with the possibility of constructing a frame signal on the basis of data symbols of the preamble and the slice of the data, modulator, made with the possibility of modulation of the frame signal using the method of multiplexing orthogonal frequency division (OFDM), and transmission device, made with the possibility of transmission of the modulated frame signal, and the transmitter is designed with the possibility of signal processing, data characters preamble divided into at least one power level 1 (L1), and bandwidth block L1 corresponds to the number of active carriers assigned to one channel, and blocks L1 repeated bandwidth.

9. The transmitter item 8, in which the bandwidth block L1 equal to 7.61 MHz.

10. The transmitter item 8, in which the unit L1 has the alarm information L1 for a slice of the data.

11. The transmitter 8, additionally contains the encoder LDPC, made with the possibility of coding data preamble using the shortened and LDPC.

12. Receiver for reception of a signal broadcast and receiver contains a demodulator, made with the possibility of demodulation of received signals by using the method of multiplexing with orthogonal frequency division (OFDM), the unit of analysis of the frame, made with the possibility of obtaining frame signal of demodulated signals and frame signal contains the characters of the preamble and the characters of data, the device of the inverse mapping, made with the possibility of the reverse display the received frame signal bits for the characters of the preamble and the bits for character data and decoder, made with the possibility of decoding bits for characters in the preamble using the shortened and decoding of LDPC (low density parity), and the receiver is made with the possibility of signal processing, and the characters of the preamble divided into at least one block to the level 1 (L1), and bandwidth block L1 corresponds to the number of active carriers assigned to one channel, and blocks L1 repeated bandwidth.

13. The receiver on the 12 in which bandwidth block L1 equal to 7.61 MHz.

14. The receiver on the 12 in which the unit L1 has the alarm information L1 for a slice of the data.