Method and apparatus for scalp electric potential measurement

FIELD: medicine.

SUBSTANCE: group of inventions refers to medicine and medical equipment, particularly to methods and apparatuses for scalp electric potential measurement. The apparatus comprises a number of sensors obtaining the initial measurement of a scalp electric potential through a hair-covering and an air contact area; a number of preamplifiers connected to one of the appropriate mentioned sensors. The contact area produces a high and variable coupling impedance of the source and the scalp. Each preamplifier contains a broadband high-impedance input and an active bias circuit generating input impedance more than 10 petaOhm over the range from 0.01 Hz to 400 Hz; a high-gain low-noise operating amplifier with the input impedance of 10 teraOhm; and a shielded feedback and bias circuit. The preamplifier is configured to have the input impedance substantially higher than the impedance produced by the source-sensor contact area. One version of the implementation of the method for scalp electric potential measurement, the preamplifier obtains the initial measurement of the scalp electric potential and forms a pre-intensified measurement of the scalp electric potential. The measurement is taken through the hair-covering and air. In the other version of the implementation of the method, an input signal of the initial scalp electric potential is obtained from the number of sensors to generate an appropriate number of channels. It is followed by the signal pre-amplification by the preamplifier with the high input impedance to form the pre-intensified measurement of the scalp electric potential. Then, a measurement mode is configured in a group containing a channel mode relative to a reference channel, a channel mode relative to a middle channel and a differential interchannel mode. Then, the pre-intensified measurement of the scalp electric potential is biased with maintaining the mentioned high input impedance; a channel gain is adjusted to differential obtaining of the channel signal. An additional stage providing the processed channel signal is suppressing radiofrequency interferences of the channel signal with maintaining adjustment of the gain and the phase; a common-mode of the channel signal is suppressed, and the band-pass channel filtration is provided. The processed channel signal is digitised to present a digital signal of the measurement of the scalp electric potential, characterising the mentioned input signal measured according to the mentioned chosen measurement mode.

EFFECT: use of the group of inventions allows more effective measurements of the scalp electric potential due to the preamplifiers, and allows reducing the need of exfoliating of the necrotic epithelial cells or application of abrasive or conducting gels.

27 cl, 11 dwg

 

The technical FIELD TO WHICH the INVENTION RELATES.

The present invention relates, in General, to medical devices, particularly to medical devices for electroencephalogram (EEG). However, it should be understood that the invention is not limited to this particular application.

Embodiments of developed, mainly in the form of a method and device for measuring the electrical potential on the scalp and will be described below with reference to this application.

The prior art INVENTIONS

Any analysis of the known prior art in the description in any case not be considered as an assumption that the mentioned prior art is widely known or forms part of the usual well-known facts in this field.

EEG (electroencephalography) signals are usually recorded in the clinical setting for the diagnosis of epilepsy and other conditions that occur in these brain waves. EEG signals are usually measured using sensors installed on the helmet, fastened on the head with a belt that extends from the helmet and fastened under the chin.

Installation of the mentioned sensors usually requires separation of the scalp and remove dead tissue from the scalp by applying a conductive abrasive gel. The sensors connect what about the helmet, usually, using clamp or screw so that when the helmet is put on, he has applied positive pressure to the sensor in the direction of the scalp. This way the sensors usually allows for continuous measurement of EEG for about one hour, until again required to prepare the scalp.

An alternative solution, for example, offered by the company Advanced Brain Monitoring Inc, provides wireless touch headset that can be worn for approximately eight hours of continuous use. However, for this device provided a connection between the sensors and scalp for eight hours, the sensor emits a conductive cream through the hair during use. Current technology typically offers ways to improve and maintain a stable conductive connection between the sensor and the scalp to resolve this problem.

In the art there is a need for method and device for measuring the electrical potential on the scalp, which is less demanding conductivity of the scalp.

The INVENTION

The aim of the invention is to provide an improved method or device for measuring the electrical potential on the scalp, which can effect the VNO be used with relatively little training or no training scalp.

In accordance with the first aspect of the invention proposes a device for measuring electrical potentials on the scalp, containing:

multiple sensors made with the original measuring the electrical potential on the scalp through the hair and air contact area; however, the contact area creates a high AC impedance source connection with the scalp; and

many preamplifiers associated with a corresponding one of the sensors; and each preamp made with the possibility of having an input impedance substantially higher than the impedance generated by the contact area of the sensor-source and preamp takes the original measured electric potential on the scalp and generates a pre-amplified measuring the electrical potential on the scalp for the formation of the pre-amplified measuring the electrical potential on the scalp.

The impedance of the contact area-sensor source is, preferably, any contact with the environment, skin and subjacent tissues.

Input impedance is preferably active and increased by applying feedback.

The preamplifier preferably contains a broadband high-impedance input and the active bias circuit, vypolnenno is with the possibility of creating an input impedance of more than 10 PECOM (POM) in the range from 0.01 Hz to 400 Hz. In particular, the preamplifier contains a low noise operational amplifier with high gain at field-effect transistors with input signal with amplitude equal to the supply voltage, input impedance 10 teraohm (Volume) and shielded by the feedback circuit and offset to create the input impedance.

In a preferred embodiment, the device further comprises:

amplifier with common mode noise filter associated with the preamplifier, while the common mode noise filter is configured to suppress essential components in-phase signal and noise contained in the pre-enhanced measurement of electric potential on the scalp to form, thereby measuring the electrical potential on the scalp with a depressed phase signal; and

a system of suppression of radio interference to suppress RF noise measurement, the electric potential on the scalp with a depressed phase signal to generate the measurement of electric potential on the scalp with suppressed interference.

Amplifier with common mode noise filter and suppression system interference is preferably configured to support, basically, the total gain, phase and delay along each signal path measuring the electrical potential on the scalp.

In prefer enom embodiment, the device further comprises:

the system of differential amplifier for amplifying the measurement of electric potential on the scalp with suppressed interference, to form reinforced the measurement of electric potential on the scalp; and

band-pass filter for filtering the amplified measuring the electrical potential on the scalp, in order, essentially, to minimize the effects of overprinting during the subsequent numbering.

The system of differential amplifier and band-pass filter preferably has a capability of supporting, basically, the total gain, phase and delay along each signal path measuring the electrical potential on the scalp.

Band-pass filter preferably has the form of a high pass filter with suppression of low-frequency transient noise and low-pass filter protection against high-frequency overlap. In a more preferred embodiment, the bandpass filter is configured to provide a suitable suppression of low-frequency intermittent interference and additionally made with the possibility of a weakening more than half of the level of quantization on the Nyquist frequency for a predefined analog-to-digital Converter. In a more preferred embodiment, the bandpass filter is an amplifier with a symmetrical bandpass filter of the sixth order is a, with bandwidth from 1 Hz to 40 Hz.

In a preferred embodiment, the input signal to the differential amplifier can be selected from any of groups of signals containing a common reference signal, the average signal is pre-amplified and buffered sensor signal.

In a preferred embodiment, the device further comprises:

digital Converter for digitizing at least one measuring the electrical potential on the scalp and

a first processor for processing signals, the at least one measuring the electrical potential on the scalp and generate an output signal.

The output signal is preferably transmitted over the air to the second processor.

In a preferred embodiment, the device further comprises a module interchannel communication made with the possibility of suppressing inter-channel RF interference between each signal path measuring the electrical potential on the scalp.

Module interchannel communication performed with selectable measuring the electrical potential on the scalp from the group consisting of: channel mode relative to the reference channel, the channel mode relative to the average for channels and interchannel differential mode.

In accordance with the second aspect of the invention features the manual measurement of electrical potentials on the scalp, containing phases in which:

take the initial measurement of electric potential on the scalp at the sensor while measuring shoot through the hair and the air; and

pre-amplify the initial measurement of electric potential on the scalp amplifier with high input impedance in order to form a pre-amplified measuring the electrical potential on the scalp.

In a preferred embodiment, the method further comprises the steps are:

suppress essential component in-phase signal and noise pre-amplified measuring the electrical potential on the scalp to form, thereby measuring the electrical potential on the scalp with a depressed phase signal; and

suppress RF noise measurement, the electric potential on the scalp with a depressed phase signal to generate the measurement of electric potential on the scalp with suppressed interference.

In a preferred embodiment, the method further comprises the step of amplification of measuring the electrical potential on the scalp with suppressed interference, to form reinforced the measurement of electric potential on the scalp for digitizing.

In a preferred embodiment, the method further comprises the steps are:

apply bandpass fil is a radio from short-term noise and reinforced overlay measuring the electrical potential on the scalp, in order to form a smoothed measurement of electric potential on the scalp for digitizing;

then digitizes the smoothed measurement of electric potential on the scalp, in order to form a sequence of digitized values of electric potentials on the scalp;

process a sequence of digitized values of electric potentials on the scalp, in order to form the waveform of the electric potential on the scalp; and

form the shape of the measurement.

In a preferred embodiment, the method further comprises the step of transmitting the output signal wirelessly to receive the second processor.

Take the initial measurement of electric potential on the scalp preferably measured through hair and air contact area; however, the contact area creates a high AC impedance source connection with the scalp; and preamp made with the possibility of having an input impedance substantially higher than the impedance generated by the contact area of the source. In a preferred embodiment, the input impedance is active and increases with the stage of applying feedback.

In accordance with a third aspect of the invention proposes a method of measuring the electrical potential on the scalp, containing the taps, on which:

accept an input signal source electric potential on the scalp from a variety of sensors for formation of the respective channels;

choose the configuration mode from the group consisting of: channel mode relative to the reference channel, the channel mode relative to the average for channels and interchannel differential mode;

shifting the input signal while maintaining high input impedance;

agree on the gain channel to a differential signal channel;

suppress radio frequency interference signal channel with the support of the approval of gain and phase as a secondary phase while providing a processed signal channel;

suppress common mode interference signal channel as an additional step in providing the processed signal channel;

perform bandpass filtering of the signal channel as an additional step in providing the processed signal channel and

then digitizes the processed channel signal to provide a digital signal measuring the electrical potential on the scalp, characterizing the input signal, measured in accordance with the selected mode of measurement.

High input impedance preferably provide a preamplifier containing the amplifier you who akim input impedance to enhance the original measuring the electrical potential on the scalp, in order to form a pre-amplified measuring the electrical potential on the scalp. Input impedance is preferably significantly higher than the impedance associated with the contact area between the source and the sensor. The impedance of the contact area of the source is preferably established any contact with the environment, skin and subjacent tissues. In a preferred embodiment, the input impedance is active and increased by applying feedback. The preamplifier preferably contains a broadband high-impedance input and the active bias circuit, configured to generate an input impedance of more than 10 POM in the range from 0.01 Hz to 400 Hz.

In accordance with an additional aspect of the invention proposes a device for measuring the electrical potential on the scalp, containing:

multiple sensors, one of which can be considered as a differential, support or General made with the original measuring the electrical potential on the scalp through the hair and air contact area; however, the contact area creates a high and variable source impedance at the connection point with the scalp; and

the preamplifier associated with the sensors; and preamp made with the possibility of having an input impedance much more you who okim, than the impedance generated by the contact area of the source and the preamp takes the original measured electric potential on the scalp and generates a pre-amplified measuring the electrical potential on the scalp.

BRIEF DESCRIPTION of DRAWINGS

Below, by way of example, the description of the preferred option, with reference to the accompanying drawings, on which:

figure 1 is an exemplary block diagram of a device for measuring the electrical potential on the scalp;

figure 2 is an exemplary high-level diagram of the device according to figure 1;

3 is an exemplary high-level block diagram of the analogue circuits in accordance with figure 2;

4 is an exemplary diagram of the preamplifier module in accordance with figure 2;

5 is an exemplary diagram of the amplifier module in accordance with figure 2;

6 is an exemplary diagram of the interface module in accordance with figure 2;

7 is an exemplary diagram of the module the analog-to-digital conversion in accordance with figure 2;

Fig is an exemplary diagram of the processor module in accordance with figure 2;

figure 9 is an exemplary diagram of the module port programming in place in accordance with figure 2;

figure 10 is an exemplary circuit configuration of the power and ground signals in accordance with figure 2 and figure 3; and

11 is an exemplary block diagram of the operational sequence of the way DL is measuring the electrical potential on the scalp.

DETAILED DESCRIPTION

Preferred embodiments of the method and device for measuring the electrical potential on the scalp described with reference to the drawings.

The following implementation options provide a method and apparatus for processing signals from the sensor, preferably having the shape of the electrode, so that the measurement of electrical potentials on the scalp was performed with a relatively small amount or no scalp preparation and skin. Thereby, decreases the constant need for traditional measuring EEG in desquamation of dead cells multilayered epithelium or the application of abrasive or conductive gels. It should be understood that the sensor in the above-mentioned embodiments is preferably electrode. Additionally, it should be understood that the sensor may be a passive or active device.

As shown first in figure 1, an exemplary block diagram 100 of a variant of implementation contains the sensors (or electrodes) 110, a preamplifier 120, the amplifier 125 with common mode noise filter, the filter 130 to suppress radio interference, differential amplifier 140, the filter 150 protection against transient interference and overlay digital Converter 160, a digital processor 170 and a display or storage device 180. In this embodiment implementing the Oia differential amplifier 140 amplifies the difference between the two sensor signals, one of which can be considered as the selected total or a reference signal.

Figure 2 shows a high-level schematic diagram 200 of a variant implementation, containing 4 input sensor. Each input contains the corresponding sensor module 210 preamp. These modules preamplifiers provide a preamplifier and a filter to suppress radio interference. Each module of the preamplifier associated with the corresponding module 220 of the amplifier.

In this embodiment, each module 220 amplifier provides a differential amplifier and filter protection overlay in the form of a bandpass amplifier. In the preferred embodiment, differential amplifier selectively amplifies the difference between the reference signal and the average value of the input signal or other input signal. Bandpass amplifier configured to perform signal filtering for protection overlay. A separate module 230 reference preamplifier provides a buffered reference signal for the system.

The outputs of the mentioned modules 220 amps and module 230 reference preamplifier is connected through the interface module 240, which then sends signals to the module 250 power supply and analog-to-digital conversion. This interface module 240 also provides the amplifier with a feedback phase signal that excites the sensor is 241 feedback in-phase signal, and buffer reference signal that excites the sensor 242 grounding of power.

The module 250 power supply and analog-to-digital conversion discretetime time and quantum each measured signal. Mentioned discretized in time and quantized signal in the processor module 260. The processor module performs additional processing of the discretized signals to generate measurements of electrical potentials on the scalp for output. The results generated by the processor module, is displayed through the module 270 Bluetooth.

Provided with other modules. The accumulator unit 280 provides stable power to the system and contains the battery / charging system. Also shown is the port 290 for on-site programming as a means for programming and communication with the processor module 260.

Figure 3 shows the approximate overall processing circuit 300 of the analog signal. This high-level diagram shows, mainly the conversion of the signal in one channel. Analog processing represented by this scheme is repeated for each input signal of the sensor.

In this embodiment, the signal input of the sensor is processed by the preamplifier 305. First, the sensor signal is buffered by buffer 310 with unity gain and feedback designed to increase I the underwater impedance. In this embodiment, the input impedance is active and increased by the introduction of feedback. The buffered signal 311 of the sensor is applied to the buffer 330 with averaging the adder and RF (radio frequency) filter signal module 340 feedback filter in-phase signal and amplifier. The buffered signal 311 of the sensor is passed through a differential filter 315 lower frequency for suppression of interference signals and then buffered by the second buffer 320 unity gain. Pre-amplified and buffered signal 321 is supplied to the interface module as the reference signal 351 and is passed to a differential amplifier 350.

This diagram additionally shows that all buffered signals 311 input sensors preferably are averaged and buffered in the buffer 330 with averaging the adder and RF-filter signal to generate an averaged signal 331. Mentioned averaging amplifier contains a diagram summarizing an RF low pass filter, buffered low noise amplifier with unity gain, to generate an output averaged signal 331, which is the average over all the input signals of the sensors. Mentioned average signal 331 is applied to measurement mode "interchannel medium (hereinafter MODE 2). This scheme has the characteristics of the phase shifts and the backside of the speed signal, selected to align with the differential RF filter 315.

Module 340 feedback filter in-phase signal and the amplifier is used to suppress common mode signals and enhance the performance of the attenuation of the common mode signal in differential mode. The feedback amplifier includes a summing circuit, forming part of the filter circuit with feedback around the amplifier. The feedback amplifier generates an output signal 341 suppression of common-mode signal in the circuit of the negative feedback with high gain, which is served in the sensor 342 feedback in-phase signal and then continues as the signal 343 channel 5 in module 380 analog-to-digital conversion.

In this embodiment, the buffer 345 unity-gain reference signal/ground power supply generates an output signal 346 ground power supply that excites the sensor 347 grounding power. Thus completes the construction of the scheme external feedback, which contains all the contact impedances of the feedback circuit, grounding power supply and sensors, as well as subcutaneous tissue impedances, regarding internal tissues of the scalp and underlying tissue.

Pre-amplified and buffered signal 351 via the communication alternating current is supplied to a differential amplifier 50. In this embodiment, another input 352 of the differential amplifier is selected either from the reference signal 353 (MODE 1), or averaged signal 321 (MODE 2), or other pre-amplified and buffered signal 321 (MODE 3). Then the selected signal 352 through connection AC current is fed into a differential amplifier. Differential amplifier 350 amplifies the difference between the pre-amplified and buffered signal 351 and the selected signal 352 and generates a differential signal 353. In this embodiment, the input signal can be selected from any of at least one of the group of signals including a common reference signal, the average signal is pre-amplified and buffered sensor signal.

The number of signals can be different, depending on the selected mode. These opportunities are presented in the table below given N input signals.

ModeSignals based on the results of the measurement of N sensors
Mode 1Signal (n), referred to as SIG_REF
N possible signals
Mode 2Signal (n), referred to as the averaged signal is al
N possible signals
Mode 3Signal (n), referred to as signal (m)
(N-1)+(N-2)+...+1 possible signals

Then the differential signal 353 is filtered link 360 bandpass filter to reduce due to the imposition of artifacts arising from the subsequent digitization of the signal. In this embodiment, the link 360 filter contains three serial link. The links contain the bandpass filter 361, filter 362 of the lower frequencies and the filter 363 upper frequencies. Then bandpass filtered signal 364 is served in module 370 analog-to-digital conversion.

Buffer 370 reference signal/signal ground allocates buffers and the reference signal 381 creating, thereby, signal 382 grounding, which is transmitted in the circuit bandpass filter, a differential amplifier and preamplifier.

The following is a more detailed description of the modules that are part of option implementation.

Figure 4 shows a diagram of the module 400 preamp. The signal input 410 of the sensor is applied sequentially to the buffer 420 unity gain, the filter 430 of the lower frequencies and the buffer 440 unity-gain.

Screen input sensor actively excited by the display signal 450. This display signal is mainly excited by the output signal of the buffer unit 420 pileni the M.

The buffer 420 is under a bias voltage applied circuit 460 feedback, and represents the input impedance of 2 Gω DC signal input 410 of the sensor. Input impedance AC is supported by the feedback scheme with the multiplication by the gain of the open loop buffer amplifier. In this embodiment, the selected scheme to create impedance at least 1 POM (1015Ω) in the range from 1 Hz to 40 Hz. This input impedance for alternating current, preferably much higher than the impedance of the contact region of the source created any contact with the environment, skin and subjacent tissues.

Resistive connection exists mainly between the scalp and the input sensors. In direct contact with skin bond has a relatively low source impedance. When the sensor is separated from the skin, hair, sweat can form an electrolytic conductive path and, still, to create a relatively low impedance source. This input impedance is typically increases when an air gap between the sensor and the scalp.

The preamplifier 420 unity-gain provided relatively high and accordingly agreed by the input impedance, which allows improved detection signal is in on the scalp. Methods have been developed to create the mentioned high input impedance by providing accurate matching of the gain channels and amplification of the signals.

In a preferred embodiment, the preamplifier 420 contains a broadband high-impedance input and the active bias circuit that generates more than 10 POM (1016Ω) in the range from 0.01 Hz to 400 Hz. Low-noise operational amplifier with high gain at field-effect transistors with input signal with amplitude equal to the supply voltage, input impedance 10 (1019Ω), in combination with shielded feedback circuit and the offset is used to create the desired input impedance. This solution is used for weakening effect caused by the variation of the impedances of the sources in the result of differences in the characteristics of the sources that are created by a combination of factors, including the skin, hair and moisture conditions. This solution also provides high-precision matching gain preamps between the channels before the subsequent signal processing.

In this embodiment, the feedback circuit and the shift to high-impedance preamplifier uses positive feedback AC unity gain with the Central point of the two high impedance resistors with whom edenia DC. To ensure stability criteria for excluding oscillations, performs a mathematical analysis. Mentioned circuit maintains a high input impedance in the frequency band of the system, so that, preferably, to maintain precision coordination of gain between channels. Positive feedback unity-gain is also used for excitation of the active shielding of the inputs of the preamplifier and sensor.

In a preferred embodiment, the circuit 430 to suppress radio interference, in combination with a circuit connection 625 (shown in Fig.6), is the noise filter and suppresses both the differential and common-mode interference, with the support of high-precision matching of gain between channels and correction of phase shifts and delays inherent in the common methods to suppress radio interference.

As shown, this scheme to suppress radio interference uses the configuration type "Delta" configuration instead of type "Pi"used in traditional differential schemes. This design facilitates the suppression of radio interference in a multi-channel system without compromising precision matching of gain between channels.

In this embodiment, the output signal of the filter to suppress radio interference is buffered low noise buffer 440 unit is selenium before submitting the final output signal at the amplifier module. Phase response of this circuit construction is preferably consistent with the phase shift and delay of the input to the averaging amplifier. Scheme for the construction of this scheme to suppress radio interference isolates scheme to suppress radio interference differential type from the high-impedance bias network amplifier cascade and, in fact, supports high-precision coordination of gain between channels.

Figure 5 shows a sample layout of the module 500 amplifier. This amplifier module delivers the input signal 510 generated by the circuit shown in figure 4, and the selected signal 520 in cascaded differential amplifier 530, the bandpass filter 540, filter 550 low pass filter 560 upper frequencies.

Differential amplifier 530 preferably includes an integrated circuit high-precision low-noise instrumental differential amplifier with high gain. This amplifier is used for selective amplification of the differential signal at the common mode rejection. High-impedance circuit 535 offset and communications AC is selected to support the frequency response and high-precision matching of gain between channels.

In this embodiment, the gain instrument amplifier us is built, to provide ±1 mV dynamic range when binding to the sensor input. It is assumed that the gain should be set so that the amplified output signal was within the dynamic range of the stress cascade digitizing. Therefore, the gain of the intermediate filter protection overlay should be included in this calculation.

Filtering for protection overlay is preferably three-stage band-pass filter consisting of a bandpass filter 540 cascade 1, filter 550 bass cascade 2 and filter 560 upper frequency cascade 3. Characteristics of the low pass filter band pass filter reduces the effect of blending caused by taking the discrete time samples of the signal. In a preferred embodiment, the attenuation of the filter at the frequency of the Nyquist frequency or higher reduces the signal level is below the level of quantization of the following system of digitization. Therefore, the characteristics of the protection filter overlay and digitizing system should be considered together after the establishment of design constraints.

Characteristics of the high-pass filter bandpass filter 540 reduces the effects of low-frequency transient noise arising due to the movement sensor, which, otherwise, would generate the signals is greater than the dynamic range of the helmet is as filtration and subsequent numbering.

In this embodiment, is applied to the amplifier with a symmetrical bandpass filter of the sixth order with a bandwidth from 1 Hz to 40 Hz. This filter is selected to provide attenuation is stronger than half the level of quantization on the Nyquist frequency, which can easily be obtained by using low-power analog-to-digital Converter, and to provide a suitable suppression of low-frequency transient noise.

Buffer 570 reference signal unity-gain provides important isolation channel and the branching of the signal ground in the cascades filter, a differential amplifier and preamplifier corresponding channel.

Figure 6 shows a sample layout of the interface module 600. This diagram shows the preferred pair of signals, when the dimension in the channel relative to the reference channel (MODE 1), from each of the modules amplifiers for each module 610 of the sensor output signals 620 and module 615 reference preamplifier. The data output signals 620 form the input to an analog-to-digital Converter. The reference signal is supplied from the module 615 reference preamplifier in each of the modules 610 sensors.

In another embodiment, alternative configurations for the implementation of the measurement signal relative to the mean signal (MODE 2) or massignan the th measurement (MODE 3). Figure 6 does not show the buffer 330 with averaging the adder and RF (radio frequency) filter the signal.

Schematic RF (radio frequency) connection 625, parallel modules 610 sensors and module 615 reference preamplifier, completes the construction of the differential filter to suppress radio interference.

In this interface module has a built-in amplifier 640 and the feedback filter the common mode signal. This amplifier 640 and the feedback filter in-phase signal provides the output 645 suppression of common mode noise, which is connected to the sensor 241 feedback phase signal.

In this interface module includes a buffer 650 reference signal with unity gain. This buffer 650 reference signal unity-gain provides isolation and excitation power for output 655 ground power supply that connects to the sensor 242 grounding power. Thus completes the construction of the scheme suppress common-mode signal.

A diagram additionally shows alternative designs for either rigidly mounted or switchable input connection module 640 feedback phase signal. In this embodiment, rigidly mounted variant with only resistors "Rn", while a switchable option provided by resistors "Rns" and sequential swap what catelani. Switchable option allows connection of the selected inputs to the amplifier 640 and the feedback filter in-phase signal or their isolation from the mentioned module by turning on or off the electronic switch 635.

7 shows an exemplary diagram for module 700 power supply and analog-to-digital conversion. This module contains common point 705 GND AGND", schema 710 analog-to-digital Converter circuit 720 filter battery power supply and circuit 730 power supply and the reference signal.

The General point 705 GND AGND" preferably formed grounded screen related to the analog part analog-to-digital Converter. In a preferred embodiment, a separate connection to earth independently carried out for the negative pole of the battery, zero-voltage analog part, a zero voltage reference signal and the digital ground digital modules.

Circuit 710 analog-to-digital Converter (ADC) performs the discretization in time and quantum input signals 711, provided the above interface module. ADC is classified according to its n-bit digital output 712, which is presented in a format that is compatible with the latest processor module.

In this embodiment, the ADC has a resolution in the Junior is voicem discharge (LSB), at least 0.5 µv and a full range ±1 mV when binding to the sensor input. To ensure that this dynamic range is applied at least twelve bits of the ADC. The output is presented in a format serial peripheral interface (SPI).

Therefore, when designing protection filter overlay to align with the twelve ADC requires weakening, at least 72 dB at the frequency of the stopband. Filter Butterworth low pass third order boundary frequency 40 Hz is the weakening of 72 dB at a frequency of 640 Hz. To suppress overlay on the boundary frequency of 40 Hz is required sampling frequency of 680 samples per second. To suppress overlay on the frequency stopband 640 Hz is required sampling rate 1280 samples per second.

After the signals are digitized, performs additional processing of the processor module.

On Fig and 9 shows an example of processing modules and wiring in accordance with the embodiment. The processor module 800 includes a processor 810. This processor controls the analog-digital Converter and receives the signal from the analog-to-digital Converter through the SPI interface 820. In this embodiment, the signals then can be processed and analyzed by the processor. The original signal may also lane shall be given to the external processor for storage and further processing. Typical external and internal processing includes the decimation of the samples, the fast Fourier transform and applications. The configuration functions of the firmware can be configured commands.

In this embodiment, the processor communicates with other devices, including source and transmits the resulting data through the port 830 Bluetooth interface or port 840 RS232 interface. Port 840 of the RS232 interface also supports programming in the operating mode (ISP) to load and update software.

Figure 9 shows a sample layout for the interface module 900 standard RS232. Interface module 900 standard RS232 facilitates the conversion of the logical signals standard signal level through standard RS-232 and provides the reset and initiate a download of the software.

The scheme inter-channel communication facilitates a number of features measurement modes, as well as provides the ability to suppress inter-channel interference and selection reference signal. The potentials on the scalp can be measured in three modes:

(MODE 1) Mode of measurement in the channel relative to the reference channel;

(MODE 2) Mode of measurement in the channel relative to the channel medium;

(MODE 3) Mode interchannel differential measurement.

This variations is the implementation of the interface module, shown in Fig.6, is rigidly mounted only for measurement in the channel relative to the reference channel (mode 1). In other embodiments, the implementation of the interface module can be used for other modes, or when a separate hard erection, or the ability to switch, as shown in figure 3.

Regardless of which mode is used to measure the signals, in other embodiments, the implementation can be applied to digital signal processing for reconstruction of signals in other modes of measurement.

Figure 10 shows a sample configuration 1000 ground and power signals, in particular concerning the analog part of the build system. The main components of the configuration of the ground and power signals are module 1010 analog-to-digital conversion and module 1020 power supply of the analog part and the reference signal consisting of a block 1021 power analog part and a block reference signal and the reference voltage analog-to-digital conversion 1022, junction independent inputs and outputs.

The mentioned module 1010 analog-to-digital conversion includes analog-to-digital Converter 1011 and its corresponding common point 1012 ground, shown as a common point 705 ground 7. Food 1013 analog part is independent and isolated from their own zero voltage is the group of the analog part. The reference signal 1014 conducted independently and isolated from their own zero voltage signal. This module receives analog signals "FSig" and "CMSig" 1015 from the interface module 1050 and is connected to a processor in a digital modules 1040 on a digital bus 1016.

The battery module 1030 consists of a rechargeable battery and charger 1031 system 1032. The positive and negative terminals of the battery connected to the power supply of the analog part of the module 1020 power supply of the analog part and the reference signal and continuing to digital modules 1040. In this embodiment, the power supply of the digital part 1041 consists of separate power supplies 3.3 V and 1.8 V, the junction of the independent inputs and outputs. Food 1042 digital part carried out independently in analog-to-digital Converter 1011 and digital circuit 1043 and untied own zero voltage digital part.

Interface module 1050 distributes food 1013 analog part and the reference signal and the reference voltage 1014 analog-to-digital conversion, independently isolated, each(OE) with its own zero-voltage modules 1060 preamplifier and analog processing. This module also receives the reference signal RSig" 1051, signals "ESig" sensors and signal suppression radio interference "RFS" connections 1052 of the modules 1060 preamplifier and analog processing and and passes the filtered and amplified signals "FSig" 1053 sensors in channels 1-4 analog-to-digital Converter module 1011 1010 analog-to-digital conversion. The reference signal is propagated back as the reference signal "DSig" 1054 differential amplifiers, differential amplifiers 1061 module 1060 preamps and analog processing. The signal 1055 feedback phase signal in channel 5 analog-to-digital Converter module 1011 1010 analog-to-digital conversion and provides feedback on the in-phase signal using sensors 1056 feedback in-phase signal and ground power.

In this embodiment, the modules 1060 preamplifier and analog processing consists of four modules 1061 preamp sensors, coupled with four analog modules 1062, and a separate module 1061 reference preamplifier. Modules 1061 preamp sensors contain compounds 1063 signal SSig" sensor and signal GND SGnd with a differential amplifier coupled analog modules 1062. Bandpass filter coupled analog modules 1062 delivers the filtered signal "FSig" 1064 in the interface module 1050. Module 1061 reference preamplifier receives the reference signal "SRef" 1065 from the interface module 1050 and delivers the reference signal RSig" 1066 in the interface module 1050. Modules 1061 reference preamplifier and preamplifier sensor signal "ESig" sensors and signals with suppressed interference "RFS" connections 1067 interface module 050.

In each of the analog stages of the selection should be done carefully so that the unit ensured a relatively low noise design, high common-mode rejection signal and interference.

In this embodiment, a low noise components are selected for the preamplifier and buffer operational amplifiers, differential amplifier and analog-to-digital Converter. Are also strategically important schemes of signals, power, ground and the junction. This variant implementation further comprises a low noise circuit power supply and the reference voltage, together with a separate ground signal and power ground and ways of decoupling the power source. The noise from the high-impedance components is eliminated using the methods of effective noise attenuation input referred components.

In this embodiment, a participative feedback to suppress common-mode signal, to increase the common-mode rejection signal. Negative feedback with high gain and pre-emphasis in the range from 50 Hz to 60 Hz is provided by bandpass amplifier. This solution is implemented using point-to-point connection to the source, as opposed to the conventional ways is one of the compounds with low gain and active excitation.

In this embodiment, feedback, power ground and the sensors are typically configured with geometric symmetry, to ensure optimal suppression of common-mode signal.

Data are embodiments of various devices for measuring the electrical potential on the scalp contain:

(a) approval of the gains of the channels before the differential signal is received in each channel

(b) the offset of the input signal while maintaining high input impedance and matching of gain,

(c) suppression of interference in a multi-channel system with the support of the approval of the amplification coefficients and correction of phase shifts and delays signals

(d) the attenuation and suppression of common-mode signal, in particular, the weakening of the interference power and radio frequency interference,

(e) the resolution digitization dynamic range and blending,

(f) methods with a low noise level and attenuation of noise,

(g) embedding configuration measuring mode in a way to preserve the most important elements.

As shown in figure 11, the preferred method 1100 measure the electrical potential on the scalp in accordance with any of the previously described embodiments includes the steps are:

(a) take an initial measurement of electric potential on the scalp on d is tchicai, stage 1110;

(b) pre-amplify the initial measurement of electric potential on the scalp agreed amplifiers with high input impedance, step 1120 to form a pre-amplified measuring the electrical potential on the scalp to strengthen;

(c) inhibit an essential component of the common mode noise, step 1130, pre-enhanced measurement of electric potential on the scalp, in order to form the measurement of electric potential on the scalp with a depressed phase signal;

(d) suppress RF noise, step 1140, measuring the electrical potential on the scalp with a depressed phase signal to generate the measurement of electric potential on the scalp with suppressed interference;

(e) increase, step 1150, the measurement of electric potential on the scalp with suppressed interference, to form reinforced the measurement of electric potential on the scalp for digitizing;

(f) apply bandpass filtering to protect from intermittent noise and reinforced overlay measuring the electrical potential on the scalp, step 1160, in order to form the measurement of electric potential on the scalp with limited bandwidth for digitizing;

(g) then digitizes the measurement of electric potential on the scalp with limited bandwidth prop is Scania, step 1170, in order to form a sequence of digitized values of the electric potential on the scalp;

(h) process sequence of digitized values of the electric potential on the scalp, step 1180 to shape the waveform of the electric potential on the scalp; and

(i) create/retain their shape measuring step 1190.

This method usually allows you to take the initial measurement of electric potential on the scalp, at step 1110, the sensor through the hair, without any preparation of the scalp or applying conductive gel between the scalp and the sensor. These source measurements of electric potential on the scalp pre-amplified at step 1120 amplifier with, essentially, a high input impedance and consistent gain, phase and delay, in order to form a pre-reinforced measurements of electrical potentials on the scalp.

In a preferred embodiment, the suppression at step 1130 essential components of the common mode noise signal is pre-amplified measurements of electrical potential on the scalp generates measurements of electric potential on the scalp with a depressed phase signal, while maintaining consistent gain, phase and delay.

Suppression of radio frequency Shu is and on stage 1140 measurements of electrical potential on the scalp with a depressed phase signal is applied, in order to form measurements of electric potential on the scalp with suppressed radio " noise, while maintaining consistent gain, phase and delay.

The gain stage 1150 measuring the electrical potential on the scalp with suppressed radio noise is used to form reinforced the measurement of electric potential on the scalp for digitizing.

The use of bandpass filtering to protect against the imposition of enhanced measuring the electrical potential on the scalp at step 1160 is used to form the measurement of electric potential on the scalp with limited bandwidth for digitizing.

Digitization of measuring the electrical potential on the scalp with limited bandwidth at step 1170 is used to generate a sequence of digitized values of the electric potential on the scalp.

The processing sequence of digitized values of the electric potential on the scalp at step 1180 is used to shape the waveform of the electric potential on the scalp.

Forming/maintaining the shape measuring step 1190.

The above measurements can be taken during the entire lifetime of the corresponding power source or to limit the storage capacity of the respective device for zapisywania. Sensors and related electronics can be secretly embedded in a hat such as a baseball cap, or can be built into a helmet.

Precision measurements of electrical potentials on the scalp generated variants demonstrated implementation, sufficient to effectively classify reference mental state. These measurements of electrical potentials on the scalp are comparable with traditional EEG measurements, which usually needs a stable conductive contact area between the scalp and the sensor for analysis of certain mental States.

Analysis of measurements of electrical potentials on the scalp provides a means for determining fatigue or drowsiness of a person in real time. While providing the above-mentioned control system in real time, which can be worn without special preparation of the scalp, the system can control the fatigue of a person while operating the equipment, such as cars or aircraft equipment.

This method and apparatus designed to measure electrical potentials on the scalp in real time and in motion without interference. It should be understood that the method and apparatus can be applied in the condition is s motion or stationary conditions. For processing real-time data can include software for processing, to further process the data of measurements of electrical potentials on the scalp. Data and signals can be transmitted in original or processed state wired or wireless data transmission system. The electricity to power these devices is provided by traditional means using rechargeable batteries or wirelessly using the scheme with the loop inductance. Specialists in the art should further be understood that the described method and apparatus can be used in clinical settings to eliminate the need in the stage of preparation of the scalp and reduce the time of consultation.

It should be understood that these embodiments of enable measurement of electric potential on the scalp through the hair, with little preparation of the scalp or in the absence of such training.

Above the invention is described with reference to specific examples, however, specialists in the art should understand that the invention can be implemented in many other ways.

Interpretation

In the context of this document, the term "wireless" and its derivatives can be used the ü to describe circuits, devices, systems, methods, methods, communication channels, etc. that can transfer data using modulated electromagnetic radiation through a non-solid medium. This term does not imply that the corresponding device does not contain any wires, although, in some embodiments, implementation, wires may be missing.

Unless specifically stated otherwise, as should be evident from the foregoing discussion, it should be understood that the description text in the use of such terms as "processing", "computing", "calculating", "determining" or similar terms refers to the action and/or processes in a computer or computer system, or similar electronic computing device, that processes and/or transforms data represented physical, such as electronic, quantitative measurements, other data similarly represented by quantitative physical measurements.

Similarly, the term "processor" may refer to any device or host device(St) handles electronic data, for example, from registers and/or memory, for the conversion of electronic data into other electronic data that, for example, can be stored in registers and/or memory. The term "computer" or "computer"or "vychislitel the Naya platform may include, at least one processor.

In addition, some embodiments of described in this application in the form of method or combination of methods that may be executed by the processor or computer system, or other means to perform the function. Thus, a processor with the necessary commands to perform the above-mentioned method or element method constitutes a means for performing the method or element of a method. In addition, this element options exercise device is an example of a tool to perform the function performed by the element with the purpose of carrying out the invention.

Here in this description presents a large number of specific details. However, it is clear that embodiments of the invention can be implemented in practice without these specific details. In other instances, well known methods, designs and methods are not presented in detail in order not to complicate the explanation in this description.

In this description, the reference to "this option implementation", "one implementation" or "an implementation option" means that a particular feature, a specific structure, or characteristic described(th) in connection with the embodiment, it is contained in at least one embodiment, the present and the gain. Therefore, the phrase "in one embodiment" or "in an embodiment"appearing in various places in the text of this description do not necessarily apply in all cases to the same version, but can be treated. Furthermore, the particular features, structures or characteristics may be combined in any suitable manner in at least one embodiment, that should be obvious to a specialist with an average level of competence in the art from the present description.

For the purposes of the present description, unless otherwise specified, the use of adjectives, which is the ordinal numeral, i.e. "first", "second", "third", etc. to describe an object simply means that the mentioned different instances of similar objects, and should not assume that the objects described thus must be in the sequence, in time or in space, rank or otherwise.

If the context is obviously not required otherwise in the description and the claims, the words "include", "contains", etc., shall be interpreted in an encompassing sense, as opposed to an exclusive or exhaustive sense; that is, in the sense of "containing, but without limitation".

Similarly, it should be noted that the term is associated", when used in the claims, should not be interpreted in the sense of limitations only direct connections. Perhaps the use of the terms "connected" and "coupled" together with their derivatives. It should be understood that these terms should not be regarded as synonyms of one another. Therefore, the scope of the expression "A device associated with device B" should not be limited to devices or systems in which the output of device A is directly connected to the input of device B. It means that there is a path between the output a and input B, which may be a path containing other devices or means. The term "associated" can mean that, or at least two elements are in direct physical or electrical contact, or, at least, two elements have no direct contact with each other, but interact with each other.

Thus, although the above embodiments of the present invention are preferred, specialists in the art it will be clear that in the above-mentioned embodiments of you can make other and further modifications, not outside of the invention and it is intended to claim all such modifications and modifications that are within the volume and the gain. For example, any of the above formulas only describe procedures that can be applied. Functions can be added in the flowchart or excluded from them, and the operations of the functional blocks can be rearranged. Stages can be added to the described methods or exclude them, within the scope of the present invention.

1. Device for measuring the electrical potential on the scalp, containing:
multiple sensors made with the original measuring the electrical potential on the scalp through the hair and air contact area; in fact the contact area creates a high AC impedance source connection with the said scalp;
many preamplifiers associated with a corresponding one of the mentioned sensors; each of the said preamplifier includes:
(i) broadband high-impedance input and the active bias circuit, configured to generate an input impedance of more than 10 POM in the range from 0.01 Hz to 400 Hz;
(ii) a low noise operational amplifier with high gain input impedance 10 Volume; and
(iii) screened the feedback circuit and the offset; and
everyone referred to the preamp made with the possibility of having the input impedance, much more is high, than the impedance created by the aforementioned contact area-sensor source; and referred to the preamplifier accepts these source measurement of electric potential on the scalp and generates a pre-amplified measuring the electrical potential on the scalp.

2. The device according to claim 1 in which the said impedance contact area-sensor source is any contact with the environment, skin and subjacent tissues.

3. Device according to any one of the preceding paragraphs, in which the mentioned input impedance is active and increased by applying feedback.

4. The device according to claim 1, in which the mentioned low-noise operational amplifier with high gain is a power amplifier field-effect transistors with input signal with amplitude equal to the supply voltage.

5. The device according to claim 1, additionally containing:
amplifier with common mode noise filter associated with said preamplifier, these common mode noise filter is configured to suppress essential components in-phase signal and noise contained in said pre-amplifying measuring the electrical potential on the scalp to form, thereby measuring the electrical potential on the scalp with a depressed phase signal; and
systems is to suppress radio interference to suppress RF noise mentioned measuring the electrical potential on the scalp with a depressed phase signal, in order to form the measurement of electric potential on the scalp with suppressed interference.

6. The device according to claim 5 in which the said amplifier with common mode noise filter and the above-mentioned suppression system interference is made with the possibility of supporting, basically, the total gain, phase and delay along each signal path measuring the electrical potential on the scalp.

7. The device according to claim 5 or 6, further comprising:
the system of differential amplifier to amplify the above-mentioned measuring the electrical potential on the scalp with suppressed interference, to form reinforced the measurement of electric potential on the scalp; and
bandpass filter for filtering mentioned reinforced measuring the electrical potential on the scalp, in order, essentially, to minimize the effects of overprinting during the subsequent numbering.

8. The device according to claim 7, in which the system of the differential amplifier and the above-mentioned band-pass filter configured to support, basically, the total gain, phase and delay mentioned along each signal path measuring the electrical potential on the scalp.

9. The device according to claim 7, in which the mentioned band-pass filter has the form of a high-pass filter for protection against low-frequency crathur the Menno noise and low-pass filter protection against high-frequency overlap.

10. The device according to claim 7, in which the mentioned band-pass filter is arranged to provide a suitable suppression of low-frequency intermittent interference and additionally made with the possibility of a weakening more than half of the level of quantization on the Nyquist frequency for a predefined analog-to-digital Converter.

11. The device according to claim 7, in which the mentioned band-pass filter is an amplifier with a symmetrical bandpass filter of the sixth order with a bandwidth from 1 Hz to 40 Hz.

12. The device according to claim 7, in which the input signal for the above-mentioned differential amplifier can be selected from any of groups of signals containing a common reference signal, the average signal is pre-amplified and buffered sensor signal.

13. The device according to claim 1, additionally containing:
digital Converter for digitizing at least one measuring the electrical potential on the scalp; and
a first processor for performing signal processing mentioned,
at least one measuring the electrical potential on the scalp and generate an output signal.

14. The device according to item 13, in which the mentioned output signal is transmitted over the air to the second processor.

15. The device according to claim 1, additionally containing module micanol the telecommunication, made with the possibility of suppressing inter-channel RF interference between each signal path measuring the electrical potential on the scalp.

16. The device according to item 15, in which the said module interchannel communication performed with selectable measuring the electrical potential on the scalp from the group consisting of:
the mode of the channel relative to the reference channel, the channel mode relative to the average for channels and interchannel differential mode.

17. The method of measuring the electrical potential on the scalp, containing phases in which:
take the initial measurement of electric potential on the scalp on the sensor, these measurements are shooting through the hair and the air; and
previously referred to reinforce the initial measurement of electric potential on the scalp preamplifier with high input impedance in order to form a pre-amplified measuring the electrical potential on the scalp, and the said preamplifier includes:
(i) broadband high-impedance input and the active bias circuit, configured to generate an input impedance of more than 10 POM in the range from 0.01 Hz to 400 Hz;
(ii) a low noise operational amplifier with high gain input impedance 10 Volume; and
(iii) a shielded circuit about atoi communication and offset.

18. The method according to 17, further comprising stages, which are:
suppress essential component in-phase signal and noise mentioned previously reinforced measuring the electrical potential on the scalp, in order to form the measurement of electric potential on the scalp with a depressed phase signal; and suppressing RF noise mentioned measuring the electrical potential on the scalp with a depressed phase signal to generate the measurement of electric potential on the scalp with suppressed interference.

19. The method according to 17 or 18, further containing a milestone in the above-mentioned measuring the electrical potential on the scalp with suppressed interference, to form reinforced the measurement of electric potential on the scalp for digitizing.

20. The method according to claim 19, further comprising stages, which are:
apply bandpass filtering from short-term interference and imposition mentioned reinforced measuring the electrical potential on the scalp to form a smoothed measurement of electric potential on the scalp for digitizing;
digitize mentioned smoothed measurement of electric potential on the scalp, in order to form a sequence of digitized values of electric potentials on the scalp;
process upon the mentioned sequence of digitized values of electric potentials on the scalp, in order to form the waveform of the electric potential on the scalp; and
form the shape of the measurement.

21. The method according to 17 or 18, further containing the step of transmitting the output signal wirelessly to receive the second processor.

22. The method according to 17 or 18, in which the mentioned accept the initial measurement of electric potential on the scalp measure through hair and air contact area; in fact the contact area creates a high AC impedance source connection with the said scalp; and the said preamplifier made with the possibility of having an input impedance substantially higher than the impedance created by the aforementioned contact area of the source.

23. The method according to item 22, in which the mentioned input impedance is active and increases with the stage of applying feedback.

24. The method of measuring the electrical potential on the scalp, containing phases in which:
accept an input signal source electric potential on the scalp from a variety of sensors for formation of the respective channels;
perform pre-amplification of the above-mentioned signal source electric potential on the scalp preamplifier with high input impedance in order to form predvaritelnyye the measurement of electric potential on the scalp, moreover, the said preamplifier includes:
(i) broadband high-impedance input and the active bias circuit, configured to generate an input impedance of more than 10 POM in the range from 0.01 Hz to 400 Hz;
(ii) a low noise operational amplifier with high gain input impedance 10 Volume; and
(iii) screened the feedback circuit and the offset;
choose the configuration mode from the group consisting of:
the mode of the channel relative to the reference channel, the channel mode relative to the average for channels and interchannel differential mode;
shift mentioned previously reinforced the measurement of electric potential on the scalp with the support referred high input impedance;
agree on the gain channel to a differential signal channel;
suppress radio frequency interference mentioned signal channel with the support of the approval of gain and phase as a secondary phase while providing a processed signal channel;
suppress the common mode rejection of the mentioned channel signal as an additional step in ensuring mentioned processed signal channel;
perform bandpass filtering of the mentioned channel signal as an additional step to ensure the above-mentioned processing is sent to the steering channel signal; and
digitize mentioned the processed channel signal to provide a digital signal measuring the electrical potential on the scalp, characterizing mentioned input signal, measured in accordance with said selected mode of measurement.

25. The method according to paragraph 24, in which the input impedance of the above-mentioned preamplifier is much higher than the impedance associated with the contact area between the source and the above-mentioned sensor.

26. The method according A.25, in which the said contact impedance source area established any contact with the environment, skin and subjacent tissues.

27. The method according to any of PP or 26, in which the mentioned input impedance is active and increased by applying feedback.



 

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SUBSTANCE: invention relates to field of medicine, namely to oncologic neurosurgery, neurology and functional diagnostics. Estimation of clinical status and neurovisualisation data and EEG examination are carried out in preoperative period. Depending on anatomical-topographical and histological version of tumour, as well as detected clinical-EEG complex of symptoms risk of development of complications in early postoperative period in patients after ablation of tumours of basal-diencephalic localisation is predicted.

EFFECT: method extends arsenal of means for predicting development of complications in early postoperative period in patients with different anatomical-topographical versions of tumours of basal-diencephalic localisation.

3 ex

FIELD: medicine.

SUBSTANCE: invention relates to field of medicine, namely to oncologic neurosurgery, neurology and functional diagnostics. Electroencephalographic (EEG) examination is performed. Coherent connections of brain regions, intensity of EEG rhythms in alpha-, beta- and theta- ranges are determined. Taking into account obtained EEG data and in dependence with localisation of tumour position in basal-diencephalic region, degree of functional activity disorder is determined.

EFFECT: method extends arsenal of means for estimation of degree of disorder of cerebral functional activity in patients with tumours of basal-diencephalic region.

1 tbl, 3 ex

FIELD: medicine.

SUBSTANCE: invention relates to filed of medicine, namely to pediatric neurology. Electroencephalographic examination of children's brain is performed in mode of drug-free afternoon sleep in corrected age of one month. In the phase of slow sleep quantity of sigma-spindles per one minute and their duration are determined. If quantity of sigma-spindles equals 2 and lower with duration 1 sec and shorter, formation of ICP in children with extremely low and very low body weight at birth is predicted.

EFFECT: method extends arsenal of means for prediction of formation of infantile cerebral paralysis in children with extremely low and very low body weight at birth.

2 tbl, 4 ex

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