Electric motor

FIELD: electricity.

SUBSTANCE: electric motor (1) consists of the first structure (4) that includes some magnetic poles formed by a certain sum of magnetic poles (4a) organised in certain direction and arranged in such a way that every two neighbouring magnetic poles (4a) have polarity that differ from one another, the second structure (3) that includes some armatures located opposite to the said magnetic poles for generating movable magnetic fields moving in certain direction between the row of armature and row of magnetic poles under the influence of certain sum of armature magnetic poles generated in the armatures (3c - 3e) at electric power supply to them, and the third structure (5) that includes a row of elements from magnetic-soft material formed by certain sum of elements (5a) from magnetic-soft material organised in certain direction with a one gap in relation to the other and arranged in such a way that a row of elements from magnetic-soft material is located between a row of magnetic poles and a row of armatures, number of magnetic poles (4a) and number of elements (5a) from magnetic-soft material is determined by the ratio 1 : m : (1 + m)/2 (m ≠ 1.0).

EFFECT: decrease of dimensions and manufacturing cost of the said electric motor with simultaneous provision of possibility to increase freedom degree at its designing.

6 cl, 19 dwg

 

The technical field to which the invention relates.

The present invention relates to a motor, which includes a set of movable elements or stationary stators and converts the input electric power to the driving force generated at the movable elements.

Background of invention

As a motor of this type of prior art known to the electric motor disclosed in patent literature 1. The motor is the so-called rotating machine and includes a first rotor and a second rotor connected respectively with the first rotating shaft and the second rotating shaft, and a stator. The first and second rotating shafts placed concentrically to one another, and the first rotor, the second rotor and the stator is placed in the direction of the radius of the first rotating shaft in this order from the inner side.

The first rotor includes a set of first permanent magnets and second permanent magnets arranged in the circumferential direction. First and second permanent magnets arranged parallel to one another in the direction of the axis of the first rotor. The stator is made so that when supplying the electric power generates the first rotating magnetic field and the second rotating magnetic the field, which rotate in the circumferential direction. The first rotating magnetic field is generated between the stator and the plot of the first rotor of the first permanent magnets and the second rotating magnetic field is generated between the stator and the plot of the first rotor from the side of the second permanent magnets. The second rotor includes a set of first cores and the second cores are arranged in the circumferential direction. These first and second cores formed by elements of magnetic material. The first cores are placed between the plot of the first rotor of the first permanent magnets and the stator, and the second cores are placed between the plot of the first rotor from the side of the second permanent magnets and the stator. The number of the magnetic poles of the first and second permanent magnets, the number of magnetic poles of the first and second rotating magnetic fields and the number of first and second cores are set equal to each other.

In the motor described above constructions in the magnetization of the first and second cores under the action of the magnetic poles of the first and second rotating magnetic fields generated by supplying electric power to the stator, between the elements of the generated magnetic lines of force. Under the action of magnetic forces in the direction of the magician is etnich power lines of the first and second rotors are driven, and on the first and second rotating shafts driving force is produced.

To ensure proper action of the magnetic forces in the direction of the magnetic field lines, causing the conversion of electric power supplied to the stator, the driving force generated at the first and second rotating shafts, in the construction described above traditional motor requires not only the first row of elements of magnetic material consisting of the set of first cores, but also the second number of elements of magnetic material consisting of the set of second cores, which inevitably increases the size of the motor and increasing the value of its production. Furthermore, the design of this motor makes the possibility of its realization only when the ratio between the speeds at which the difference between the number of revolutions of the first and second rotating magnetic fields and rotational speed of the second rotor and the difference between the rotational speed of the second rotor and the rotational speed of the first rotor become equal to one another, which reduces the degree of freedom when designing the motor.

The present invention is aimed at resolving the above problems, and its purpose is to create a motor with dimmed the mi size, reduced manufacturing cost and an increased degree of freedom in its design.

Patent literature 1

Publication No. 2008-67592 application laid Japan (Kokai).

Disclosure of inventions

To achieve the above objectives in claim 1 of the formula of the invention proposes a motor 1, 31, containing the first structure, the first rotor 4, the first rotating shaft 6, the second stator 34), comprising a number of magnetic poles, where the number of magnetic poles formed a certain amount of magnetic poles (permanent magnets 4A, 34a), which are arranged in a certain direction and are arranged so that each two adjacent magnetic poles have polarity different from each other, the second structure (3 stator, the first stator 33), which includes a number of anchors, where the number of anchors formed by a set of anchors (iron core 3A, the coil 3C-3E inductance U-W-phase, iron core 33a, coil 33C-e inductance U-W-phases), arranged in a certain direction and placed in front of a number of magnetic poles for generating a moving magnetic field moving in a certain direction, between adjacent anchors and near the magnetic poles due to some combination of the magnetic poles of the anchors generated by a set of anchors while applying thereto an electric power, and a third structure (second R the top 5 the second rotating shaft 7, the movable element 35, which includes a number of elements of magnetic material, where the number of elements of magnetic material is formed to a specific set of elements of magnetic material (cores 5A, the core 35b), arranged in a certain direction with a clearance to one another and are arranged so that the number of elements of magnetic material is located between adjacent magnetic poles, and a number of anchors, and the ratio between the number of magnetic poles of the anchors, the number of magnetic poles and the number of elements of magnetic material within a certain area along a particular direction is given by the ratio of 1:m:(1+m)/2(m≠1.0 in).

In this motor the number of magnetic poles of the first structure and the number of anchors of the second structure are positioned one against the other, and the number of elements of magnetic material of the third structure is placed so that it is located between adjacent magnetic poles, and a number of anchors. The aggregate of the magnetic poles, anchors and elements of magnetic material, forming respectively the number of magnetic poles, the number of anchors and the number of elements of magnetic material, arranged in a certain direction. In addition, when supplying electric power to a number of anchors is generated by the combination of the magnetic poles of the Yak is Rey, and due to the magnetic poles anchors between adjacent anchors and near the magnetic poles are generated moving magnetic field moving in a certain direction. With every two adjacent magnetic poles have polarity different from each other, and every two neighboring element of magnetic material are placed with a gap of one relative to another. As mentioned above, between the adjacent magnetic poles and the number of anchors under the action of the totality of the magnetic poles anchors are generated moving magnetic field, and between adjacent magnetic poles and the number of anchors placed a number of elements of magnetic material, therefore, under the action of the magnetic poles of the anchors and the magnetic poles of the elements of magnetic material subjected to magnetization. This magnetization, as well as placement of every two adjacent elements of magnetic material with a gap of one relative to another causes the generation of magnetic field lines connecting the magnetic poles, the elements of magnetic material and the magnetic pole anchors each other. In addition, the action of magnetic forces in the direction of the magnetic force lines converts electric power supplied to the anchors, the driving force generated at the first structure, the second structure and the third structure.

In this is case, for example, when the electric motor according to the present invention has a structure satisfying the following conditions (a) and (b), the ratio between the velocities of the moving magnetic fields of the first and third structures and the relationship between torques structures of the three are expressed in the following way, and the equivalent circuit corresponding to the motor has the form shown Fig.

(a) Motor is a rotating machine, and anchors have three-phase coils of U-phase, V-phase and W-phase.

(b) the Number of the magnetic poles of the anchors is 2, the number of magnetic poles is 4, that is, the number of magnetic pole pairs of anchors, in which the N pole and the S pole form one pair is 1, the number of pairs of magnetic poles, in which the N pole and the S pole form one pair is 2 and the number of elements of magnetic material - 3.

Around the description of the invention, the term "pair of poles" means a pair of poles formed by the N pole and the pole S.

In this case, the magnetic flux Ψk1 magnetic poles crossing the first element of magnetic material composed of elements of magnetic material, is expressed by the following equation (1):

where ψf is the maximum value of the magnetic flux of the magnetic pole, and θ1 and θ2 - sootvetstvenno rotation of the magnetic pole and the angle of rotation of the element of magnetic material relative to the coils of U-phase. In addition, in this case, since the ratio of the number of pairs of magnetic poles to the number of magnetic pole pairs of anchors is 2.0, then the magnetic flux of the magnetic pole rotates (changes) with a repetition period at twice the repetition period of the moving magnetic fields that in the above equation (1) is expressed by multiplying (θ2-θ1) of 2.0.

Therefore, the magnetic flux Ψu1 magnetic poles crossing the coil of U-phase through the first element of magnetic material, is expressed by the following equation (2)obtained by multiplying equation (1) cosθ2.

Similarly, the magnetic flux Ψk2 magnetic poles crossing the second element of magnetic material composed of elements of magnetic material, is expressed by the following equation (3):

As the angle of rotation of the second element of magnetic material relative to the anchor ahead of the angle of rotation of the first element of magnetic material by 2π/3, then in the above equation (3) is expressed by the summation of 2π/3 θ2.

Therefore, the magnetic flux Ψu2 magnetic poles crossing the coil of U-phase through the second element of magnetic material, is expressed by the following equation (4)obtained by umngeni the equation (3) to (θ2+2π/3).

Similarly, the magnetic flux Ψu3 magnetic poles crossing the coil of U-phase by means of a third element of magnetic material composed of elements of magnetic material, is expressed by the following equation (5):

In the motor shown in Fig, the magnetic flux Ψu of the magnetic pole, crossing the coil of U-phase, through the elements of magnetic material, is obtained by summation of the magnetic flux Ψu1-Ψu3 expressed by the above equations (2), (4) and (5), and therefore, the magnetic flux Ψu is expressed by the following equation (6):

When the generalization of equation (6), the magnetic flux Ψu of the magnetic pole, crossing the coil of U-phase, through the elements of magnetic material, is expressed by the following equation (7):

where a, b and C represent respectively the number of pairs of magnetic poles, the number of elements of magnetic material and the number of magnetic pole pairs of anchors.

When converting the above equation (7) given the formula amounts and compositions of trigonometric functions, we get the following equation (8):

If in equation (8) position the th that b=a+C, given the fact that cos(θ+2π)=cosθ, equation (8) becomes the following equation (9):

When converting this equation (9) subject to the addition theorems of trigonometric functions, we get the following equation (10):

Under the condition that a-C≠0, the second term in the right-hand side of equation (10) when the conversion is based on the sum of a number and the Euler formula becomes 0, as shown in the following equation (11):

In addition, under the condition that a-C≠0, the third term in the right-hand side of equation (10) when the conversion is based on the sum of a number and the Euler formula, as shown in the following equation (12)becomes 0:

From the above equations it follows that if a-C≠0 the magnetic flux Ψu of the magnetic pole, crossing the coil of U-phase, through the elements of magnetic material, is expressed by the following equation (13):

If in this equation (13) to assume that a/=α, then we obtain the following equation (14):

Furthermore, if equation (14) to believe that s·θ2=θ2, and·θ1=θe1, you get the following equation (15):

In this equation, as follows from the fact that θ2 one is by the product of the angle θ2 of rotation of the element of magnetic material relative to the coils of U-phase with the magnetic poles of the anchors, θ2 is an electrical angle of an element of magnetic material relative to the coils of U-phase. Moreover, as follows from the fact that θ1 is the product of the angle of rotation θ1 of the magnetic poles relative to the coils of U-phase to the number of magnetic pole pairs of anchors, θ1 represents the electrical angle of the magnetic poles relative to the coils of U-phase.

Similarly, as the electric angle of the coils of V-phase is ahead of the electrical angle of the coils of U-phase by 2π/3, then the magnetic flux Ψv magnetic pole across the inductor V-phase through the elements of magnetic material, is expressed by the following equation (16). In addition, since the electrical angle to the coil of W-phase is ahead of the electrical angle of the coils of U-phase by 2π/3, then the magnetic flux Ψw magnetic poles crossing the inductor W-phase through the elements of magnetic material, is expressed by the following equation (17):

In addition, if the magnetic fluxes Ψu-Ψw expressed by the above equations (15)-(17), and are subjected to differentiation by time, we get the following equations(18)-(20):

where ω1 denotes the value obtained by dierentiating θe1 time, i.e. a value obtained by converting the angular velocity of the first structure relative to the second structure in the electrical angular velocity, and ω2 denotes the value obtained by dierentiating θ2 time, i.e. a value obtained by converting the angular velocity of the third structure relative to the second structure in the electrical angular velocity.

Furthermore, the magnetic fluxes crossing the inductor U-W-phases directly, without the aid of elements of magnetic material, are very small, and their influence can be neglected. Therefore, dΨu/dt-dΨw/dt, which is the value obtained by dierentiating accordingly, magnetic flux Ψu-Ψw (equations (18)-(20)) of the magnetic poles crossing the inductor U-W-phases through the elements of magnetic material, in time, represent the voltage proteoids (voltage inductional EMF)generated in the coils U-W-phases during the rotation (movement) of the magnetic poles and elements of magnetic material relative to the number of anchors.

From the above equations it follows that the electric currents Iu, Iv and Iw, FR is flowing respectively through the coil of U-phase, V-phase and W-phase are expressed by the following equations (21), (22) and (23):

where I represents the amplitude (maximum value) of each of the electric current flowing through the coil U-W-phases.

From the above equations (21)-(23) it follows that the electrical angle θmf vector of rolling of the magnetic field (rotating magnetic field) relative to the coils of U-phase is expressed by the following equation (24), and the electrical angular velocity ωmf of rolling of the magnetic field relative to the coil of U-phase is expressed by the following equation (25):

When the number of anchors as well as the second structure is stationary, mechanical power (driving force) W generated at the first and third structures, resulting in the leakage currents Iu-Iw through the inductor, respectively U-W-phases, expressed, except for the section with magnetic resistance, the following equation (26):

When converting this equation (26) by substituting equations (18)-(23) is obtained by the following equation (27):

The ratio between the mechanical power W, the enemy is surrounding the time T1, passed on the first structure through the magnetic poles (hereinafter referred to as "the first torque T1), the torque T2 is transmitted to the third structure through the elements of magnetic material (hereinafter referred to as "the second torque T2"), the electrical angular velocity ωe1 the first structure and the electrical angular velocity ω2 third structure is expressed by the following equation (28):

As follows from the above equations (27) and (28), the first and second torques T1 and T2 are expressed by the following equations (29) and (30):

Assuming that torque equivalent to the electric power supplied to a number of anchors, and the electrical angular velocity ωmf of the movable magnetic field is equivalent to the torque of The actuator, since the electric power supplied to a number of anchors, and mechanical power W equal to one another (when neglecting losses), from equation (28) is equivalent to the torque of The actuator is expressed by the following equation (31):

From the above equations (29)-(31) is obtained by the following equation (32):

The ratio of torque between the moments, expressed by equation (32), and the correlation between the electrical angular velocities, expressed by the above equation (25)are completely the same as the ratio between the rotational speeds and the ratio between the torques on the sun gear, the ring gear and the planetary mechanism. Thus the ratio between the electrical angular velocities and the ratio between the torques are not limited to the described above case of the second stationary structure, but also run under all conditions relating to the mobility of the structures from the first to the third. For example, the above ratio is performed also in the case when the second structure is made with the possibility of movement, and electric power is supplied in a state in which the driving force is applied to the second structure, and when the addition of the second stationary structure made of the first or the third structure, and electric power is supplied to a number of anchors in the state in which the driving force is applied to the first or the third structure. In addition, these ratios are also carried out when the second structure is made with the possibility of movement, and the first and/or the third structure(s) is stationary and electric power is supplied in SOS is the right, in which the driving force is applied to the first and/or third structure(s).

As mentioned above, provided that b=a+C and a-C≠0, are the ratio between the electrical angular velocities, expressed by equation (25), and the ratio between the torques, expressed by the equation (32). If we assume that the number of magnetic poles is p, and the number of magnetic poles anchors - q, the condition above b=a+C will have the expression b=(p+q)/2, b/q=(1+p/q)/2. However, if we assume that p/q=m, we obtain the expression b/q=(1+m)/2, and the fulfillment of the above conditions b=a+C would mean that the ratio between the number of magnetic poles of the anchors, the number of magnetic poles and the number of elements of magnetic material expressed by the ratio of 1:m:(1+m)/2. While performing the above conditions a-C≠0 would mean that m≠1.0 in. As in the motor according to the present invention within a certain area along a particular direction, the ratio between the number of magnetic poles of the anchors, the number of magnetic poles and the number of elements of magnetic material is set by the ratio of 1:m:(1+m)/2 (m≠1.0)and then run the correlation between the electrical angular velocities, expressed by equation (25), and the ratio between the torques, expressed by the equation (32), which suggests that electrodisintegration properly.

Unlike traditional motor discussed above, the motor according to the invention can operate even when the same number of elements of magnetic material, which allows to reduce the size and reduce the manufacturing cost of the motor. Moreover, as follows from equations (25) and (32), setting α=a/C, i.e. the ratio of the number of pairs of magnetic poles to the number of magnetic pole pairs of anchors provides the opportunity to freely set the relationship between the electrical angular velocities of moving magnetic fields of the second and third structures, and the relationship between torques structures of the three and therefore the possibility of increasing the degree of freedom in design of the motor. The same useful effects can be obtained even when the number of phases of the coils of the set of anchors is different from the discussion above 3, and when the motor is not rotating machine, and a linear motor. In the case of a linear motor is provided free job ratio is not between "torques", and between "traction forces".

In claim 2 of the motor 1, 31 according to claim 1 further comprises a means of measuring the relative vzaimoporozhdeniya (first sensor 21 of the rotation angle, the second sensor 22 at the La rotation, Converter 16b of the electrical angle, the position sensor 41 for measuring the relative vzaimoporozhdeniya structures of the three and a controller (ECU 16) for controlling the moving magnetic fields based on the measured relative vzaimoporozhdeniya between the structures from the first to the third.

With this design is a means of measuring the relative vzaimoporozhdeniya measures the relative vzaimopoleznoe between the structures from the first to the third, and means controls the moving magnetic fields based on the measured relative vzaimoporozhdeniya between the structures of the three. This allows you to properly generate magnetic lines of force between magnetic poles, the elements of magnetic material and magnetic poles, anchors and provide, therefore, the possibility of proper action of magnetic forces in the direction of the magnetic lines of force and, consequently, the ability to ensure reliable operation of the electric motor.

In section 3 of the claims in the motor 1, 31 according to claim 2, the means of measuring the relative vzaimoporozhdeniya (first sensor 21 of the rotation angle, the second sensor 22 of the angle transducer 16b electrical angle) measures as relative vzaimoporozhdeniya structures of the three electrical angles of the first structure and the third is the structure relative to the second structure, and means controls the moving magnetic fields on the basis of the difference between the value obtained by multiplying the measured electrical angle of the second electrical angle θER2 rotor) of the third structure to (1+m), and a value obtained by multiplying the measured electrical angle (electric angle θER1 the first rotor of the first structure on m.

With this design, the control of the moving magnetic fields is based on the difference between the value obtained by multiplying the measured electrical angle of the third structure relative to the second structure to (1+m), and a value obtained by multiplying the measured electrical angle of the first structure relative to the second structure on m. As follows from claim 1, m is the ratio of the number of magnetic poles to the number of magnetic poles of the anchors. As mentioned above, during operation of the motor according to claim 1 ratio between the electrical angle of the movable magnetic fields and electric angles of the second and third structures is expressed by equation (24). In equation (24) α represents the ratio (a/C) the number of pairs of magnetic poles to the number of magnetic pole pairs of anchors, i.e. the ratio of the number of the magnetic poles to the number of magnetic poles anchors equal to m. Therefore, the design described above in which makes it possible to ensure more reliable operation of the electric motor.

In paragraph 4 of the claims in the motor 1, 31 according to any one of items 1 to 3, the magnetic poles are magnetic poles of the permanent magnets 4A, 34a.

With this design is used as the magnetic poles of poles of permanent magnets, unlike the case of using the magnetic poles of the magnets eliminates the need for electrical circuits and inductors for supplying electric power to the electromagnets. It also allows you to reduce the size of the motor and to simplify its design. In addition, for example, in the case where the first structure having magnetic poles made with the possibility of rotation, when using as the magnetic poles of the poles of the electromagnets is possible to do without collector rings for supplying electric power to the electromagnets, which provides the possibility of reducing the size of the motor and the possibility of increasing its effectiveness.

In claim 5 of the formula of the invention, the motor 1 according to claim 1 is rotating machine.

With this design provides the possibility of obtaining useful effects described in relation to the motor according to claim 1, and rotating machines.

In claim 6 of the formula of the invention the electric motor 31 according to claim 1 is a linear motor.

With this design enables p is produce useful effects, described as applied to the motor according to claim 1, and a linear motor.

Brief description of drawings

Figure 1 - schematic view of the cross section of the motor according to the first embodiment of the present invention.

Figure 2 - block diagram of the motor presented in figure 1, and an ECU (electronic control unit).

Figure 3 is a schematic view of the stator and the first and second rotors of the motor is presented in figure 1, expanded in the circumferential direction of the state.

4 is a schematic collinear chart illustrating an example of the relationship between the electrical angular velocity of the magnetic fields and the electrical angular velocities of the first and second rotors of the motor is presented in figure 1.

5 is a schematic view of the motor presented in figure 1, illustrating the operation of the motor in the case of supply of electric power to the stator in a stationary state of the first rotor.

6 is a schematic view of the electric motor, which is a continuation of the illustration of figure 5.

7 is a schematic view of the electric motor, which is a continuation of illustrations 6.

Fig is a schematic view of the motor illustrating vzaimopoleznoe between the magnetic poles of the armatures and cores after the rotation of the magnetic poles of the anchors on the angle 2π and the state, shown in figure 5.

Fig.9 is a schematic view of the motor illustrating the operation of the motor presented in figure 1, in the case of supply of electric power to the stator in a fixed position of the second rotor.

Figure 10 is a schematic view of the electric motor, which is a continuation of illustration Fig.9.

11 is a schematic view of the electric motor, which is a continuation of illustrations figure 10.

Fig is a schematic graph illustrating an example of changes of stress proteoids U-W-phases in the case of the stationary state of the first rotor of the electric motor according to the present invention.

Fig is a schematic graph illustrating an example of changes of the equivalent torque of the actuator and torque transmission of the first and second rotors in case fixed to the first rotor of the electric motor according to the present invention.

Fig is a schematic graph illustrating an example of changes of stress proteoids U-W-phases in the case of stationary second rotor of the electric motor according to the present invention.

Fig is a schematic graph illustrating an example of changes of the equivalent torque of the actuator and torque transmission of the first and second rotors in the case of stationary second rotor of the electric motor according to the present image is the shadow.

Fig - schematic front view of the motor according to the second embodiment of the present invention and the functional units providing this motor.

Fig - schematic top view of the motor presented on Fig.

Fig is a schematic view of the motor presented on Fig illustrating the relationship between the number of magnetic poles, anchors, core, and the magnetic poles of the motor.

Fig is a schematic view of an equivalent circuit of the motor according to the present invention.

The best option of carrying out the invention

Below is a detailed description of the present invention, followed by reference to the drawings illustrating the preferred embodiment of this invention. Figure 1 shows a motor 1 according to the first embodiment of the present invention. The motor 1 is made in the form of a rotating machine, the operation of which is controlled by the ECU 16, shown in figure 2. As shown in figure 1, the motor 1 consists of a stationary housing 2, a stator 3, is installed inside the housing 2, the first rotor 4 mounted inside the housing 2 opposite the stator 3, the second rotor 5 mounted between the stator 3 and the first rotor 4, the first rotating shaft 6 and the second rotating shaft is 7. While for convenience of illustration of some of the elements in figure 1, such as the first rotating shaft 6 and others, shown schematically. In addition, down the hatch sections in figure 1 and other figures discussed below.

The housing 2 includes a hollow cylindrical circumferential wall 2A and a pair of disc-shaped side walls 2b and 2C, are installed on opposite ends of the circumferential wall 2A, forming a single structure. In the center of these side walls 2b and 2C are respective mounting holes 2d and 2E, with appropriate bearings 8 and 9.

The above first and second rotating shafts 6 and 7 are supported by appropriate bearings 8 and 9 with the possibility of free rotation and placed concentrically to one another. Part and the first and second rotating shafts 6 and 7 is located inside the housing 2, and the rest stands out from the housing 2. Above the stator 3, the second rotor 5 and the first rotor 4 is placed concentrically to one another in the direction of the radius of the first rotating shaft 6 (hereinafter simply referred to as "radial" or "radially") and arranged in the specified order, starting with the outside.

The stator 3 is designed to generate a rotating magnetic field and, as shown in figure 3, includes himself iron core 3A and the coil 3C, 3d and 3E inductance respectively of the U-phase, V-phase and W-phase, mounted on an iron core 3A. Thus in figure 1 for convenience shown only the coil 3C inductance of the U-phase. Iron core 3A, having the form of a hollow cylinder composed of steel plates, passes in the direction of the axis of the first rotating shaft 6 (hereinafter simply referred to as "axial direction" or "axis") and is installed on the inner circumferential surface of the circumferential wall 2A of the housing 2. On the inner circumferential surface of the iron core 3A has twelve grooves 3b. The grooves 3b are held in the axial direction and are arranged with equal spacing to one another in the circumferential direction of the first rotating shaft 6 (hereinafter simply referred to as "circumferential direction" or "circumference"). Coil 3C-3E inductance U-W-phases are wound in the grooves 3b in the form of a distributed winding (wave winding) and connected to an adjustable source 15 power (see figure 2). Adjustable source 15 power, which is a combination of electrical circuits comprising an inverter, and batteries, is connected to the ECU 16.

In the stator 3 having the design described above, when supplying electric power from the regulated power source 15, at the end of the iron core 3A side of the first rotor 4 with the same clearances of one relative to another district in which direction is generated by four magnetic poles (see 5), and due to these magnetic poles of the rotating magnetic field rotating in the circumferential direction. Next, the magnetic poles generated on the iron core 3A, referred to as the "magnetic poles anchors". In addition, every two magnetic pole anchors, spaced in the circumferential direction one next to the other have polarities different from one another. While figure 5 and other figures discussed below, the magnetic poles of the anchor is indicated on the iron core coils 3A and 3C-3E inductance U-W letters (N) and (S).

As shown in figure 3, the first rotor 4 includes a number of magnetic poles, eight permanent magnets 4A. These permanent magnets 4A arranged with equal spacing to one another in the circumferential direction, and the number of magnetic poles is located opposite the iron core 3A. Each permanent magnet 4A is held in the axial direction and the length in the axial direction is set equal to the length of the iron core 3A of the stator 3.

Permanent magnets 4A are installed on the outer circumferential surface of the annular retainer 4b. This annular retainer 4b are composed of elements of magnetic material such as iron or steel plate, and its inner peripheral surface of the retainer 4b attached to the outer district is the surface of the disc-shaped flange 4C, forming a single concentric design with the first rotating shaft 6. This allows free rotation of the first rotor 4, comprising permanent magnets 4A, as a single structure with the first rotating shaft 6. Furthermore, since the permanent magnets 4A, as indicated above, attached to the outer circumferential surface of the annular retainer 4b formed by the elements of magnetic material, at the end of each permanent magnet 4A side of the stator 3, you receive the magnetic pole (N) or (S). Thus in figure 3 and other figures discussed below, the magnetic poles of the permanent magnets 4A are indicated by letters N and S). Every two permanent magnet 4A located in the circumferential direction one next to the other have polarities different from one another.

The second rotor 5 includes a number of elements of magnetic material, consisting of six cores 5A. These cores 5A arranged with equal spacing to one another in the circumferential direction, and the number of elements of magnetic material is placed between the iron core 3A of the stator 3 and the first rotor 4 with defined gaps from one another. Each core 5A composed of elements of magnetic material, such as steel plate, and is held in the axial direction. Also, as well as that of the permanent magnet 4A, the length of the core 5A in the axial direction is set equal to the length of the iron core 3A of the stator 3. Through the hollow cylindrical connecting element 5s, held at a small distance in the axial direction, the core 5A is fixed on the outer end of the disc-shaped flange 5b. The flange 5b forms a single concentric design with the second rotating shaft 7. This allows free rotation of the second rotor 5, which includes the cores 5A as a single structure with the second rotating shaft 7. Figure 3 connecting element 5 C and the flange 5b omitted for convenience.

In addition, as shown in figure 2, the motor 1 is equipped with a first sensor 21 of the rotation angle and the second sensor 22 angle, each of which is a sensor of magnetic induction type. The first sensor 21 angle measures the angle of rotation of a separate permanent magnet 4A of the first rotor 4 (hereinafter referred to as "angle θR1 rotation of the first rotor) relative to the individual coils of U-phase 3C of the stator 3 (hereinafter referred to as "reference inductor"), and generates a signal characterizing the measured angle θR1 rotation of the first rotor received in the ECU 16. Above the second sensor 22 angle measures the angle of rotation of a separate genial, OEM is ka 5A of the second rotor 5 relative to the reference coil inductance (hereinafter referred to as "angle θR2 rotation of the second rotor") and generates a signal characterizing the measured angle θR2 rotation of the second rotor received in the ECU 16.

In addition, the motor 1 is supplied with the first current sensor 23 and the second sensor 24 current. The first and second sensors 23 and 24 of the current measure currents flowing through the respective coils 3C and 3d inductance respectively of the U-phase and V-phase (hereinafter respectively the "current Iu of the U-phase and the current Iv of the V-phase"), and produce signals characterizing respectively the measured current Iu of the U-phase current Iv of the V-phase coming into the ECU 16.

The ECU 16, implemented as a microcomputer that contains the interface I/o, CPU (Central processing unit), RAM (random access memory) and ROM (permanent memory), and controls the operation of the motor 1 based on the signals received from the above sensors 21-24.

In this example, the implementation of the permanent magnets 4A correspond to the magnetic poles in the present invention, and the first rotor 4 and the first rotating shaft 6 correspond to the first structure in the present invention. Iron core 3A and the coil 3C-3E inductance U-W-phases correspond to the anchors in the present invention, and the stator 3 corresponds to the second structure of the present invention. The cores 5A correspond to elements of magnetic material in the present invention, and the second rotor 5 and the Torah rotating shaft 7 correspond to the third structure of the present invention. The ECU 16 corresponds to a management tool in the present invention, and the first and second sensors 21 and 22 of the angle of rotation 21 and 22 correspond to the means of measuring the relative vzaimoporozhdeniya in the present invention.

As mentioned above, the motor 1 includes four magnetic pole anchors, eight magnetic poles of the permanent magnets 4A (hereinafter referred to as "magnetic poles of the magnets) and six cores 5A. Thus, the ratio between the number of magnetic poles of the anchors, the number of magnetic poles of the magnets and the number of cores 5A (hereinafter referred to as "ratio of the number of poles) is given by the ratio 1:2,0:(1+2,0)/2. As follows from this equation and the above equations (18)-(20), the voltage proteoids generated by the coils 3C-3E inductance U-W-phases during the rotation of the first rotor 4 and the second rotor 5 relative to the stator 3 (hereinafter referred to as "voltage Vcu of produoed U-phase, voltage Vcv, proteoids V-phase and the voltage Vcw, proteoids W-phase"), are expressed by the following equations (33), (34) and (35):

In these equations, I represents the amplitude (maximum value) of the current flowing through the coils 3C-3E inductance U-W-phases, a ψF is the maximum value of magnetic flux of the magnetic poles of the magnets. θER1 represents the value obtained in the result of the conversion angle θR1 rotation of the first rotor as the so-called mechanical angle in electrical angle (hereinafter referred to as "electric angle of the first rotor"), that is, the value obtained by multiplying the angle θR1 rotation of the first rotor to the number of magnetic pole pairs of anchors, i.e. by 2. θER2 is a value obtained by converting the angle θR2 rotation of the second rotor mechanical angle in electrical angle (hereinafter referred to as "electric angle of the second rotor"), that is, the value obtained by multiplying the angle θR2 rotation of the second rotor by the number (2) pairs of magnetic poles anchors. ωER1 is a value obtained by differentiating θER1 time, that is, the value obtained by converting the angular velocity of the first rotor 4 relative to the stator 3 in an electrical angular velocity (hereinafter referred to as "electrical angular velocity of the first rotor"). ωER2 is a value obtained by differentiating θER2 time, that is, the value obtained by converting the angular velocity of the second rotor 5 relative to the stator 3 in an electrical angular velocity (hereinafter referred to as "electrical angular velocity of the second rotor").

As follows from the above, the ratio of numbers of poles and the above equations (21)-(23), the current Iu of the U-phase current Iv of the V-phase current (hereinafter referred to as "current Iw of the W phase)flowing through the coil 3E inductance W-phase, are expressed with therefore, its following equations (36), (37) and (38):

As follows from the above, the ratio of numbers of poles and the above equations (24) and (25), the electrical angle of the vector of the rotating magnetic fields of the stator 3 with respect to the reference coil inductance (hereinafter referred to as "electric angle θMFR magnetic fields") is expressed by the following equation (39), and the electrical angular velocity of the rotating magnetic fields relative to the stator 3 (hereinafter referred to as "electric angular velocity ωMFR magnetic fields") is expressed by the following equation (40):

Therefore, when the correlation between the electrical angular velocity ωMFR magnetic field electrical angular velocity ωER1 first rotor electrical angular velocity ωER2 second rotor is expressed by the so-called collinear graph, this value is displayed, for example, as in figure 4.

In addition, assuming that torque equivalent to the electric power supplied to the stator 3, and the electrical angular velocity ωMFR magnetic fields is equivalent torque TSE drive, then, as follows from the above, the ratio of numbers of poles and the above equation (32), the ratio between the equivalent torque TSE drive, torque is omentum TR1, transmitted to the first rotor 4 (hereinafter referred to as "torque TR1 transmission of the first rotor, and torque TR2 transmitted to the second rotor 5 (hereinafter referred to as "torque TR2 transmission of the second rotor"), is expressed by the following equation (41):

The correlation between the electrical angular velocities, expressed by equation (40), and the ratio between the torques, expressed by the equation (41)are completely the same as the ratio between the rotational speeds and the ratio between the torques on the sun gear, the ring gear and the planetary mechanism, the gear ratio between the sun gear and a ring gear which is set by the ratio 1:2.

The ECU 16 controls the current passing through the coils 3C-3E inductance U-W-phases based on the above equations (39) and, thus, controls the rotating magnetic fields. In particular, the ECU 16 includes, as shown in figure 2, the block 16A calculate the target current, the inverter 16b electrical angle Converter 16C coordinates of the current block 16d calculating the difference, the current regulator a and Converter 16f coordinate voltage, provides regulation of the currents Iu, Iv and Iw of the U-W-phases in the so-called method of vector control and, thus, controls the rotations is engaged in magnetic fields. In this embodiment, the inverter 16b electrical angle corresponds to a measure of the relative vzaimoporozhdeniya.

Unit 16A calculate the target current, calculates a corresponding target current value Id axis d and current Iq axis q (hereinafter respectively the "target current Id_tar axis d and the target current Iq_tar axis q"), discussed below, and supplies the result of calculation of the target current Id on the axis d and the target current Iq axis q in the unit 16d calculating the difference. The target current Id_tar axis d and the target current Iq_tar axis q are calculated, for example, in accordance with the load on the motor 1.

In the inverter 16b of electrical angle are entered angles θR1 and θR2 rotation of the first and second rotors, the measured first and second sensors 21 and 22 of the angle of rotation. Converter 16b electrical angle calculates the electrical angles θER1 and θER2 the first and second rotors by multiplying the entered angles θR1 and θR2 rotation of the first and second rotors on the number (2) pairs of magnetic poles, anchors and supplies the result of calculation of the electric angles θER1 and θER2 the first and second rotors in the Converter 16C coordinate current and the Converter 16f coordinate voltage.

In addition to electrical angles θER1 and θER2 the first and second rotors in the Converter 16C coordinates of the current injected currents Iu and Iv U-phase and V-phase, measured respectively the first and second sensors 23 and 24 current. On the basis of input currents Iu and Iv respectively of the U-phase and V-phase and electrical angles θe1 and θ2 the first and second rotors Converter 16C coordinates converts current flowing currents Iu-Iw U-W-phases in three-phase coordinate system AC current Id on the axis d and the current Iq axis q in the coordinate system dq. This coordinate system dq, in which the axis d is (3·θER2-2·θER1), and the axis C - axis orthogonal to the axis d, the rotation speed (3·ER2-2·ωER1). In particular, the current Id on the axis d and the current Iq axis q are calculated by the following equation (42):

The resulting calculations, the current Id on the axis d and the current Iq axis q are entered by the coordinate Converter 16C current block 16d calculating the difference.

Unit 16d calculating the difference computes the difference between a target current Id_tar axis d and the current Id on the axis d (hereinafter referred to as "difference dId currents along the axis d") and the difference between a target current Iq_tar on the q axis current Iq on the q axis (hereinafter referred to as "difference dIq currents along the axis q"). Obtained by computing the difference between dId and dIq currents unit 16d calculating the difference gives the regulator a current.

On the basis of input of a difference dId the currents along the axis d and the difference dIq currents along the axis q by using a specific algorithm of the feedback control, for example, a PI (proportional-integral is o) control algorithm, the regulator a current calculates the voltage Vd on the axis d and the voltage Vq of q axis. As a result, the calculation of the voltage Vd axis d so that the current Id on the axis d becomes equal to the target current Id_tar axis d, and calculating the voltage Vq axis q is carried out in such a way that the current Iq axis q becomes equal to the target current Iq_tar axis q. The resulting calculation of the voltage Vd and Vq, respectively, along the axis d and q axis controller e power supplies Converter 16f coordinate voltage.

On the basis of input electrical angles θER1 and θER2 the first and second rotors Converter 16f coordinate voltage converts the voltage Vd on the axis d and the voltage Vq axis q in the values of the command voltages Vu, Vv, and Vw of the U-W-phases in three-phase coordinate system of an alternating current (hereinafter referred to as "value Vu_cmd command voltage U-phase", "value Vv_cmd command voltage V-phase" and "value Vw_cmd command voltage of the W-phase"). In particular, the values Vu_cmd-Vw_cmd command voltage U-W-phases are calculated by the following equation (43):

The resulting value calculations Vu_cmd-Vw_cmd command voltage U-W-phases Converter 16f coordinate voltage supplies in the above adjustable source 15 power.

When this voltage Vu-Vw U-W-phases, apply an adjustable source 15 and the power e is tradigital, become equal to the corresponding values of Vu_cmd-Vw_cmd command voltage U-W-phases, which results in the regulation of the currents Iu-Iw U-W-phases. In this case, these currents Iu-Iw expressed above, the relevant equations (36)-(38). And the amplitude I of the electric current is determined based on the target current Id_tar axis d and the target current Iq_tar axis q.

The described above process management using the ECU 16 provides the possibility of regulating the electrical angle θMFR magnetic fields, which is the above equation (39), and the possibility of such regulation electrical angular velocity ωMFR magnetic fields, which is the above equation (40).

The motor 1 having the design described above, is used, for example, as follows. When the fixed state of the first or second rotor 4 or 5 or in a state where the driving force is applied to one of these rotors, electric power supplied to the stator 3 is converted into a driving force and is produced at the other of the rotors. In the same state, when the driving force is produced simultaneously on the first and second rotors 4 and 5, the electric motor is used as the source of motive power devices such as propellers of opposite rotation, in which torque is agrusti, satisfying the equation (41), at the same time acts on the first and second rotor 4 and 5.

Next is a detailed description of the process of converting electric power supplied to the stator 3, the driving force generated by the first rotor 4 and the second rotor 5. First of all, with reference to figure 5-7 describes the case of a supply to the stator 3 of the electric power at a fixed position of the first rotor 4. This position numbers characterizing the constituent elements of the motor, figure 5-7 omitted for convenience. This applies to other figures discussed below. In addition, the same magnetic pole of the armature and the same core 5A figure 5-7 marked for clarity the hatch.

Let, as shown in figure 5(a), generating a rotating magnetic field rotating in figure 5(a) to the left starts from a state in which the center of one particular core 5A and the center one particular of the permanent magnet 4A are combined with one another in the circumferential direction, and the center of each of the third core 5A from this one particular core 5A aligned in the circumferential direction with the center of each of the fourth permanent magnet 4A from this one particular permanent magnet 4A. At the initial stage of generation of the rotating magnetic field position of each of the two magnetic poles anchor is th, having the same polarity aligned in the circumferential direction from the centers of the permanent magnets 4A, the centers of which are aligned with the centers of the cores 5A and polarity of these magnetic poles, anchors, and these magnetic poles of the permanent magnets 4A are different.

As mentioned above, rotating magnetic fields are generated by using the 3 stator between the stator 3 and the first rotor 4, and the second rotor 5 having the cores 5A, is placed between the stator 3 and the first rotor 4, so under the action of the magnetic poles of the anchors and the magnetic poles of magnets each core 5A is subjected to magnetization. This magnetization, as well as placement of every two neighboring cores 5A with a gap of one relative to the other lead generating magnetic force lines ML, connecting magnetic pole anchors, the cores 5A and the magnetic poles of the magnets with some others. The magnetic force lines ML of the iron core 3A and the retainer 4b figure 5-7 omitted for convenience. This applies to other figures discussed below.

In the state shown in figure 5(a), the magnetic force lines ML are generated in such a way that connects the magnetic poles of the anchors, the cores 5A and the magnetic poles of the magnets, combined one with the other in the circumferential direction, and the magnetic pole anchors, the cores 5A and magnetic p is Luca magnets, located in the circumferential direction one next to the other on opposite sides of the above combined with some other magnetic poles, anchors, cores 5A and the magnetic poles of the magnets. Since in this state the magnetic lines of force are straight, no magnetic forces, providing the ability to rotate the cores 5A in the circumferential direction, the cores 5A do not apply.

When the rotation of the magnetic poles of the anchors from the positions shown in figure 5(a), in the position shown in figure 5(b), due to rotation of the rotating magnetic fields of the magnetic force lines ML are bent, and as a result, the cores 5A start to operate the magnetic forces that allow straightening of the magnetic force lines ML. In this case, the bending of the magnetic force lines ML on the cores 5A occurs with the formation of bulges in the direction opposite to the direction of rotation of the rotating magnetic field (hereinafter referred to as "direction of rotation of the magnetic fields"), relatively straight lines connecting the magnetic pole anchors and magnetic poles connected to one another magnetic force lines ML, and therefore above the magnetic forces provide an opportunity to drive the cores 5A in motion in the direction of rotation of the magnetic fields. Under the action of magnetic forces in healthy lifestyles the Institute such that magnetic force lines ML cores 5A are driven in the direction of rotation of the magnetic field and rotated into position, shown in figure 5(c), in which the second rotor 5 with cores 5A and the second rotating shaft 7 is also rotated in the direction of rotation of the magnetic fields. While a dashed line in Fig.(5b) and 5(c) indicate that the amount of magnetic flux of the magnetic force lines ML is extremely small, and the magnetic connection between the magnetic poles, anchors, core 5A and the magnetic poles of the magnets is weak. This applies to other figures discussed below.

Upon further rotation of the rotating magnetic fields of the sequence of the phases described above, i.e. the bending of the magnetic force lines ML on the cores 5A with a bulge in the direction opposite to the direction of rotation of the magnetic field → the emergence of magnetic forces acting on the cores 5A, and provides for the rectification of the magnetic force lines ML → rotating the cores 5A, the second rotor 5 and the second rotating shaft 7 in the direction of rotation of the magnetic field, as shown in Fig.6(a)-6(d) and 7(a), 7(b)is repeated. Under the action of magnetic forces in the direction of these magnetic force lines ML electric power supplied to the stator 3 is converted into a driving force generated by the second rotating shaft 7.

Fig illustrates the condition which is magnetic on the YUS anchors after turning from the state of shown in figure 5(a), the electrical angle 2π. From the comparison Fig and figure 5(a), it follows that when the cores 5A are rotated in the same direction by 1/3 of the rotation angle of the magnetic poles of the anchors. This coincides with the result ωER2=ωMFR/3, obtained by the substitution ωER1=0 in the above equation (40).

What follows is a description of the operation of the motor when electric power is supplied to the stator 3 in a stationary state of the second rotor 5, followed by references to figures 9-11. Thus one and the same magnetic pole of the armature and the same permanent magnet 4A figure 9-11 labeled for clarity hatching. Let, as shown in Fig.9(a), generating a rotating magnetic field rotating in Fig.9(a) to the left begins the same way as figure 5(a), from a state in which the center of one particular core 5A and the center one particular of the permanent magnet 4A are combined with one another in the circumferential direction, and the center of each of the third core 5A from this one particular core 5A aligned in the circumferential direction with the center of each of the fourth permanent magnet 4A from this one particular permanent magnet 4A. At the initial stage of generation of the rotating magnetic field position of each of the two magnetic poles anchors having the same polarity, combined in the district directed and with the centers of the permanent magnets 4A, the centers of which are aligned with the centers of the cores 5A and polarity of these magnetic poles, anchors, and these magnetic poles of the permanent magnets 4A are different.

In the state shown in Fig.9(a), as figure 5(a), the magnetic force lines ML are generated in such a way that connects the magnetic poles of the anchors, the cores 5A and the magnetic poles of the magnets, combined one with the other in the circumferential direction, and the magnetic pole anchors, the cores 5A and the magnetic poles of the magnets arranged in the circumferential direction one next to the other on opposite sides of the above combined with some other magnetic poles, anchors, cores 5A and the magnetic poles of the magnets. Since in this state the magnetic lines of force are straight, no magnetic forces, providing the possibility of turning permanent magnets 4A in the circumferential direction, the permanent magnets 4A are not valid.

When the rotation of the magnetic poles of the anchors from the positions shown in Fig.9(a), in the position shown in Fig.9(b), due to rotation of the rotating magnetic fields of the magnetic force lines ML are bent, and as a result, the permanent magnets 4A start to operate the magnetic forces that allow straightening of the magnetic force lines ML. In this case, these permanent magnets 4A occupy operi the abuser position relative to the continuation of the magnetic force lines ML, connecting the magnetic poles of the armatures and cores 5A one another in the direction of rotation of the magnetic fields, and therefore above the magnetic forces provide the location of the permanent magnets 4A on the continuation of these magnetic field lines, that is, the drive capability of the permanent magnets 4A in the direction opposite to the direction of rotation of the magnetic fields. Under the action of magnetic forces in the direction such that magnetic force lines ML permanent magnets 4A are driven in the direction opposite to the direction of rotation of the magnetic field, and rotates in the position shown in Fig.9(c), in which the first rotor 4, is equipped with permanent magnets 4A, and the first rotating shaft 6 is also rotated in the direction opposite to the direction of rotation of the magnetic fields.

Upon further rotation of the rotating magnetic fields of the sequence of the phases described above, i.e. the bending of the magnetic force lines ML → occupation permanent magnets 4A-ahead position relative to the continuation of the magnetic lines ML, connecting the magnetic poles of the armatures and cores 5A, in the direction of rotation of the magnetic field → the emergence of magnetic forces acting on the permanent magnets 4A and provides for the rectification of the magnetic force lines ML of the rotating permanent magnets 4A, the first rotor 4 and the first rotating shaft 6 in the direction opposite to the direction of rotation of the magnetic field, as shown in figure 10(a)-10(d) and 11(a), 11(b) is repeated. Under the action of magnetic forces in the direction of these magnetic force lines ML electric power supplied to the stator 3 is converted into a driving force generated by the first rotating shaft 6.

11(b) illustrates the state that the magnetic pole anchors after the rotation from the state shown in Fig.9(a), the electrical angle 2π. From a comparison of the 11(b) and Fig.9(a) that permanent magnets 4A are rotated in the opposite direction by 1/2 of the angle of rotation of the magnetic poles of the anchors. This coincides with the result-ωER1=ωMFR/2, obtained by the substitution ωER2=0 in the above equation (40).

On Fig and Fig presents the simulation results management process, in which the number of magnetic poles of the anchors, the number of cores 5A and the number of permanent magnets 4A are set corresponding figures 16, 18 and 20, the first rotor 4 is fixed and the second rotor 5 in the supply of electrical power to the stator 3 is generated driving force. Fig illustrates an example of changes of voltages Vcu-Vcw, proteoids U-W-phases over a period of time change of the electrical angle θER2 second rotor from 0 to 2π.

In this case, since the first rotor 4 is fixed, and the number of magnetic pole pairs of anchors and the number of pairs of magnetic poles of magnets is respectively 8 and 10, when applying the above equations (25) the correlation between the electrical angular velocity ωMFR magnetic fields and the electrical angular velocities ωER1 and ωER2 the first and second rotors turns ωMFR=2,25·ωER2. As shown in Fig, for the time period of the electrical angle θER2 second rotor from 0 to 2π the number of periods generate voltages Vcu-Vcw, proteoids U-W-phases is approximately 2,25. On Fig also shows the changes of the voltages Vcu-Vcw, proteoids U-W-phases of the second rotor 5. As shown in the figure with an electric angle θER2 the second rotor as the horizontal axis, voltage proteoids ranked by the voltage Vcw, proteoids W-phase voltage Vcv, proteoids V-phase and the voltage Vcu of proteoids U-phase. This means that the second rotor 5 rotates in the direction of rotation of the magnetic fields. As shown above, and presented on Fig the simulation results allow to confirm expression ωMFR=2,25·ωER2.

Fig illustrates an example of changes in equivalent torque TSE drive and torques TR1 and TR2 transmission of the first and second rotors. As in this case, the number of magnetic pole pairs I have Ouray and the number of pairs of magnetic poles of magnets is respectively 8 and 10, applying the above equations (32) the ratio between the equivalent torque TSE and the actuator torques TR1 and TR2 transmission of the first and second rotors turns TSE=TR1/1,25=-TR2/2,25. As shown in Fig equivalent torque TSE drive is approximately-TREF, torque TR1 transmission of the first rotor is approximately 1.25·(-TREF), and torque TR2 transmission of the second rotor is approximately 2,25·TREF. TREF is a certain value of torque (for example, 200 Nm). Thus, presented at Fig the simulation results allow to confirm expression TSE=TR1/1,25=-TR2/2,25.

On Fig and 15 presents the simulation results management process, in which the number of magnetic poles of the anchors, the number of cores 5A and the number of permanent magnets 4A are set the same as in the case illustrated on Fig and 13, the second rotor 5 is fixed, and on the first rotor 4 in the supply of electrical power to the stator 3 is generated driving force. Fig illustrates an example of changes of voltages Vcu-Vcw, proteoids U-W-phases over a period of time change of the electrical angle θER1 first rotor from 0 to 2π.

In this case, since the second rotor 5 is fixed, and the number of magnetic pole pairs of anchors and the number of pairs of magnetic poles of magnets is with therefore, its 8 and 10, applying the above equations (25) the correlation between the electrical angular velocity ωMFR magnetic fields and the electrical angular velocities ωER1 and ωER2 the first and second rotors turns ωMFR=-1,25·ωER1. As shown in Fig, for the time period of the electrical angle θER1 first rotor from 0 to 2π the number of periods generate voltages Vcu-Vcw, proteoids U-W-phases is approximately 1.25. On Fig also shows the changes of the voltages Vcu-Vcw, proteoids U-W-phases of the first rotor 4. As shown in the figure with an electric angle θER1 the first rotor as the horizontal axis, voltage proteoids built in order voltage voltage Vcu of proteoids U-phase voltage Vcv, proteoids V-phase and the Vcw proteoids W-phase. This means that the first rotor 4 rotates in the direction opposite to the direction of rotation of the magnetic fields. As shown above, and presented on Fig the simulation results allow to confirm expression ωMFR=-1,25·ωER1.

Fig illustrates an example of changes in equivalent torque TSE drive and torques TR1 and TR2 transmission of the first and second rotors. In this case, as in the case illustrated Fig, when applying the above equations (32) the ratio between the equivalent torque TSE and the actuator torques TR and TR2 transmission of the first and second rotors turns TSE=TR1/1,25=-TR2/2,25. As shown in Fig equivalent torque TSE drive is approximately TREF, torque TR1 transmission of the first rotor is approximately 1.25·TREF, and torque TR2 transmission of the second rotor is approximately -2,25·TREF. TREF is a certain value of torque (for example, 200 Nm). Thus, presented at Fig the simulation results allow to confirm expression TSE=TR1/1,25=-TR2/2,25.

As shown above, following the above embodiment, the motor 1 can operate even when the same number of elements of magnetic material formed by the cores 5A, which allows to reduce the size and reduce the manufacturing cost of the motor 1. And the job of the ratio of the number of pairs of magnetic poles of the magnets to the number of magnetic pole pairs of anchors provides the opportunity to freely set the relationship between the electrical angular velocity ωMFR moving magnetic fields and the electrical angular velocities ωER1 and ωER2 the first and second rotors, and the ratio between the equivalent torque TSE and the actuator torques TR1 and TR2 transmission of the first and second rotors and, consequently, the possibility of increasing the degree of freedom in design of the motor 1.

Regulation of the same electrical angle θMFR magnetic fields, the project is the abuser of the above equation (40), allows you to ensure reliable operation of the electric motor 1. And use as the magnetic poles of the magnet poles of the permanent magnets 4A, unlike the case of using the magnetic poles of the magnets eliminates the need for electrical circuits and inductors for supplying electric power to the electromagnets, which leads to a further reduction in size of the motor 1 and to simplify its construction. In addition, when using as the magnetic poles of the magnet poles of the electromagnets is possible to do without collector rings for supplying electric power to the electromagnets, which provides the possibility of reducing the size of the motor 1 and the possibility of increasing its effectiveness.

In the above first embodiment, the first and second rotors 4 and 5 are made with the possibility of free rotation, however, the invention is not limited to such construction, and one of the rotors 4 and 5 can be performed non-rotating, and the other with the possibility of free rotation, and it can generate a driving force. As in this case, one of the rotors 4 and 5 are made non-rotating, then, as follows from the above equations (39), the electrical angle of one of the rotors 4 and 5 becomes equal to 0, and control of rotating magnetic fields can realize who I am only in accordance with the electrical angle of the other rotor, measured, for example, a sensor. With the possibility of free rotation can be performed and the stator 3. In this case, the electric motor is used, for example, as follows. In a state where the driving force is applied to one of the rotors 4 and 5 and the stator 3, the electric power, behaviour to the stator 3 is converted into a driving force and is produced at the other of the rotors 4 and 5. When the fixed state of the first or second rotor 4 or 5 (or in a state where the driving force is applied to one of these rotors) the driving force is produced simultaneously on the stator 3 and the other of the rotors 4, 5, and the electric motor is used as the source of motive power devices such as propellers of opposite rotation, in which the torque load, satisfying the equation (41), at the same time acts on the stator 3 and the other of the rotors 4 and 5.

In addition, in the first embodiment, as the angles θR1 and θR2 rotation of the first and second rotors are measured respectively the angle of rotation of a separate permanent magnet 4A and the angle of rotation of a separate core 5A relative to the reference coil inductance, that is, with respect to a particular coil 3 of U-phase. In case, if the rotation angles of the first and second rotors 4 and 5 relative to the stator 3 can be expressed through the crystals turn other components of the construction, the measured angles of rotation of these parts of the structure. For example, as the angles θR1 and θR2 rotation of the first and second rotors can be measured respectively the angle of rotation of a separate section of the retainer 4b or the first rotating shaft 6 and the angle of rotation of a separate section of the flange 5b or the second rotating shaft 7 with respect to a particular 3d coil, V-phase, single coil 3E W-phase or single part of the body 2.

In addition, in the first embodiment, the electrical angle θMFR magnetic fields used to control a rotating magnetic fields, calculated according to equation (39) using the rotation angles θR1 and θR2 of the first and second rotors, the measured first and second sensors 21 and 22 of the angle of rotation. However, the calculation of the electrical angle θMFR magnetic fields can be implemented in the manner proposed in the application No. 2007-280916 patent Japan. In particular, take a planetary gear whose gear ratio between the sun gear and ring gear coincides with the ratio between the number of magnetic poles of the anchors and the number of the magnetic poles of the magnets, and one angle sensor. The sun gear or ring gear connected with the first rotor 4, and drove to the second rotor 5 and then measure the angle of rotation of the ring gear or Solna is the main gear with respect to a particular coil 3C inductance of the U-phase by using the angle sensor. In the case when the number of the magnetic poles of the anchor exceeds the number of the magnetic poles of the magnets, with the first rotor 4 connects the sun gear.

If we assume that the ratio of the number of magnetic poles of the magnets to the number of magnetic poles anchors - γ, the angle of rotation, measured above the angle sensor will have the expression (1+γ)θR2-γ·θR1. From this it follows that the measurement of electrical angle θMFR magnetic fields used to control a rotating magnetic fields, can be carried out using a planetary gear and one angle sensor and does not require two separate sensors to measure the rotation angles of the first and second rotors 4 and 5.

In addition, in the first embodiment, the stator 3 and the first rotor 4 is posted in the radial direction respectively on the outer side and inner side, however the invention is not limited to such construction, and possibly reverse the placement of the stator 3 and the first rotor 4 in the radial direction respectively from the inner side and outer side. The motor 1 may have a structure, not only the so-called radial type in which the stator 3 and the first and second rotors 4 and 5 are arranged in the radial direction, but also the construction of a so-called axial type in which the stator 3 and the first and vtoro the rotors 4 and 5 are arranged in the axial direction.

The following is a description of the motor 31 according to the second embodiment of the present invention makes reference to Fig and 17. Unlike the first embodiment, the motor 31 shown in these figures, has the design of a linear motor and can be used in relation to the conveyor. While the constituent elements of the matching components in the case of the first embodiment, indicated at Fig the same number of items. The focus in the following description focuses on differences from the first example.

As shown in Fig and 17, the electric motor 31 comprises a stationary housing 32, the first stator 33 is installed inside the housing 32, the second stator 34 installed inside the housing 32 opposite the first stator 33, and the rolling element 35 mounted between the stator 33 and 34.

The housing 32 includes a bottom wall 32A in the form of a plate whose forward-backward (in the direction away from the observer on Fig, and the vertical direction on Fig) is the direction of its length, and side walls 32b and 32C forming a unitary structure with the bottom wall 32A and passing upward from opposite ends of the bottom wall 32A opposite one another.

The first stator 33 is designed to Generalov is of moving magnetic fields and, as shown in Fig, includes an iron core coil 33a and 33C, 33d and a inductance respectively of the U-phase, V-phase and W-phase, mounted on an iron core 33a. Iron core 33a having the shape of a rectangular parallelepiped, recruited from steel plates, runs along the entire length of the housing 32 in the direction of back and forth and installed on the side wall 32b of the housing 32. On the surface of the iron core 33a side of the second stator 34 has a large number of grooves 33b. The grooves 33b are held in the vertical direction and are arranged with equal spacing to one another in the direction of back and forth. Coil 33c-e inductance U-W-phases are wound in the slots 33b in the form of a distributed winding (wave winding) and connected to an adjustable source 15 power.

In the first stator 33 having the design described above, when supplying electric power from the regulated power source 15, at the end of the iron core 33a side of the second stator 34 with the same clearances to one another in the forward-backward generated a large number of magnetic poles (see Fig), and due to these magnetic poles of the rotating magnetic field moving in the direction back and forth. Furthermore, just as in the first embodiment, the magnetic poles generated on f the m core 33a, referred to as the "magnetic poles anchors". At Fig, as in figure 5, the magnetic pole anchors are indicated on the iron core coils 33a and 33C-e inductance U-W letters (N) and (S). In this case, as shown in the figure, the number of magnetic poles of anchors within a certain area INT along the direction of the forward-backward is four.

The second stator 34 includes a number of magnetic poles, consisting of a large number of permanent magnets 34a. These permanent magnets 34a arranged with equal spacing to one another in the direction of back and forth, and the number of magnetic poles placed opposite to the iron core 33a of the first stator 33. Each permanent magnet 34a has the shape of a rectangular parallelepiped whose length in the vertical direction is set to the same as the length of the iron core 33a. Through the latch 34b permanent magnets 34a mounted on the right end of the upper surface of the bottom wall 32A (with the "right" side Fig). The latch 34b made in the form of an element of magnetic material such as iron. Permanent magnets 34a fixed to the retainer 34b made, as indicated above, of iron, and therefore, at the end of each permanent magnet 34a side of the first stator 33 receive the magnetic pole (N) or (S). At Fig and 18, as well as the and 3, the magnetic poles of the permanent magnets 34a (hereinafter, as in the case of the first embodiment, the magnetic poles of the magnets") are indicated by letters N and S). In addition, as shown in Fig, the polarity of each of the two permanent magnets 34a, located in the forward-backward one next to the other, are different, and the number of permanent magnets 34a within a certain area INT is eight.

The movable element 35 includes an upper plate 35A mounted on the first and second stators 33 and 34, and the number of elements of magnetic material formed with six cores 35b mounted on the upper plate 35A. The dimensions of the upper plate 35A in the forward-backward and left-right direction is smaller than the housing 32. Partially the upper plate 35A closes the first and second stators 33 and 34.

Each core 35b has the shape of a rectangular parallelepiped, drawn from elements of magnetic material, such as steel plate, and the length of this core 35b in the vertical direction is set to the same as the length of the iron core 33a. By means of connecting elements 35C mounted on the upper ends of the cores 35b, these six cores 35b are connected to one another and are arranged with equal spacing to one another in the direction of forward ' n the ass moreover, the number of elements of magnetic material formed by the cores 35b, is placed between the iron core 33a of the first stator 33 and near the magnetic poles of the second stator 34C defined distance from one another. At the bottom of each core 35b has wheels 35d. These wheels 35d core 35b mounted on rail guides (not shown) on the upper surface of the bottom wall 32A, providing free movement of the moving element 35, which includes the core 35b in the direction of back and forth, but the stiffness of this element in the left-right direction. At Fig and 18 connecting elements omitted for convenience.

In this embodiment, the second stator 34 corresponds to the first structure in the present invention, and the permanent magnets 34a correspond to the magnetic poles in the present invention. The first stator 33 corresponds to the second structure in the present invention, and the iron core coil 33a and 33C-e inductance U-W-phases correspond to the anchors in the present invention. The movable element 35 corresponds to the third structure of the present invention, and the cores 35b correspond to elements of magnetic material in the present invention.

In addition, the motor 31 is equipped with an optical position sensor 41 (the tool is measuring the relative vzaimoporozhdeniya), generating a signal characterizing the position of the individual core 35b of the rolling element 35 with respect to a particular coil 33C inductance of the U-phase of the first stator 33 (hereinafter referred to as "position of the rolling element), which comes in the ECU 16. On the measured position of the rolling element, the ECU 16 determines the relative vzaimopoleznoe between the movable element 35 and the first and second stators 33 and 34 and on the basis of this vzaimoporozhdeniya controls the passage of current through the coils 3C-3E inductance U-W-phases and, thus, controls the rotating magnetic fields. In particular, the control is performed as follows.

As shown in Fig, within a certain area INT the same way as in the case of the first embodiment, the number of magnetic poles is four anchors, the number of magnetic poles of magnets - eight, and the number of cores 35b - six. Thus, the ratio between the number of magnetic poles of the anchors, the number of magnetic poles of the magnets and the number of cores 35b is set by the ratio 1:2:(1+2)/2. As in this embodiment, the permanent magnets 34a is stationary, applying the above equations (39) the regulation of the electrical angle of the vector of the rotating magnetic field (hereinafter referred to as "electric angle θMFM magnetic fields") is sudestada thus, what is the ratio θMFM=3·θEM, where θEM is a value obtained by converting the position of the moving element in the electric angle (hereinafter referred to as "electric angle of the rolling element). In particular, θEM is a value obtained by multiplying the measured position of the moving element by the number of magnetic pole pairs of anchors, i.e. by 2. In this case, as in the first embodiment described above, the process control is carried out by regulating the electric current flowing through the coils 33C-e inductance U-W-phases, the method of vector control.

Regulation of the same electrical angular velocity of the moving magnetic fields (hereinafter referred to as "electric angular velocity ωMFM magnetic fields") is carried out in such a way that you value ωMFM=3·ω where ω denotes the value obtained by dierentiating the electrical angle θEM rolling element according to time, i.e. a value obtained by converting the speed of the rolling element 35 in the electrical angular velocity (hereinafter referred to as "electrical angular velocity of the rolling element). In addition, if we assume that the traction force, the equivalent electric power supplied to the first stator 33, and the electrical angular velocity ωMFM magnetic fields, the two which is the equivalent of pulling force FSE drive, applying the above equations (41) the ratio between the equivalent traction force FSE and traction force FM that is transmitted to the movable element 35 (hereinafter referred to as "traction FM transmitting rolling element"), takes the form of FSE=-FM/3.

As mentioned above, pursuant to this embodiment, as in the first embodiment, the motor 31 can operate even when the same number of elements of magnetic material formed by six cores 35b, which allows to reduce the size and reduce the manufacturing cost of the motor 31. In addition, setting the ratio of the number of pairs of magnetic poles of the magnets to the number of magnetic pole pairs of anchors within a certain area INT provides the opportunity to freely set the relationship between the electrical angular velocity ωMFM moving magnetic field and an electric angular velocity ω rolling element, and a relationship between the equivalent traction force FSE drive and traction force FM transmitting rolling element and, consequently, the possibility of increasing the degree of freedom in design of the motor 31.

Regulation of the same electrical angle θMFM magnetic fields that satisfies the relation θMFM=3·θEM, helps to ensure reliable operation of the electric motor 1. And the use of ka is este magnetic poles of the magnet poles of the permanent magnets 34a, as in the first embodiment, leading to a further reduction in size of the electric motor 31 and the simplification of its design.

When the motor 31 can have the following design. The connection of permanent magnets 34a of the second stator 34 with each other the top plate than the upper plate 35A, forms a second movable element made with the possibility of free movement in the forward-backward relative to the housing 32. As in the first embodiment, the driving force may be generated on the movable element 35 and/or the second movable element. In addition, the consolidation of the iron core 33a of the first stator 33 in the top plate forms a third movable element made with the possibility of free movement in the forward-backward relative to the housing 32. In this case, as described above in the first embodiment, the driving force may be generated on the movable element 35, the second movable element or the third movable element.

In the case where the second movable element is designed as described above, with the help of the sensor is measured not only the position of the rolling element 35, and the position of the individual permanent magnet 34a of the second rolling element with respect to a particular coil 33C U-phase electric angle θMM magnetic fields is calculated based on equation (39) in accordance with the position of the rolling element and the measured position of the second moving element. While the resulting calculation of the electrical angle θMFM magnetic fields used in the control of rotating magnetic fields.

In the second embodiment, as the position of the moving element is measured, the position of the individual core 35A with respect to a particular coil 33C inductance of the U-phase. In case, if the position of the rolling element 35 relative to the first stator 33 can be expressed through the position of the other component parts of the design, measured the position of this part of the design. For example, as the position of the moving element can be measured position of the individual constituent parts of a design, such as the upper plate 35A, with respect to a particular coil 33d V-phase, single coil e W-phase and single site housing 32. This applies to the above second and third movable elements.

The present invention is in no way limited to the above embodiments and can be implemented in various forms. For example, in the above embodiments, the magnetic pole is formed of a magnetic pole of one permanent magnet 4A or 34a, but can be formed and the magnetic poles of the combination of permanent magnets. For example, using inanaga pole, formed by magnetic poles of the two permanent magnets arranged in the form of an inverted V so that the closing of the magnetic poles of the two permanent magnets with one another comes from the stator 3 (the first stator 33), provides an opportunity to strengthen the direction of the magnetic force lines ML. Instead of the permanent magnets 4A or 34a, used in the above embodiments, can be used electromagnets or anchors with the possibility of generating a moving magnetic field. In the above embodiments, the coil 3C-3E and 33C-e inductance U-W-phases are wound in the slots 3b and 33b in the form of a distributed winding, however, the invention is not limited to such construction, and the coil can be wound around the grooves in the form of a concentrated winding. In addition, in the above embodiments, the coil 3C-3E and 33C-e inductance U-W-phases are three-phase coils U-W-phases, however, the number of phases of the coils is arranged to generate a moving magnetic field (rotating magnetic field)can be arbitrary.

Of course, the number of grooves 3b and 33b can be arbitrary and may differ from the number of grooves in the above embodiments. In addition, in the above embodiments, the groove is 3b and 33b, permanent magnets 4A and 34a, and the cores 5b and 35b are placed with equal spacing from one another, but the placement and uneven gaps. In the above embodiments, the number of magnetic poles is four anchors, the number of magnetic poles of magnets - eight, and the number of cores 5A or 35b - six, but within a ratio of 1:m:(1+m)/2 (m≠1.0) number of the magnetic poles of the anchors, the magnetic poles of the magnets and cores can be arbitrary. In addition, in the above embodiments, the first sensor 21 of the rotation angle, the second sensor 22 and the rotation angle of the sensor 41 are sensors of magnetic induction type, however, it is possible to use sensors optical type. In the above embodiments as a means of control used by the ECU 16, however, it is possible to use a combination of microcomputer and electrical circuits. In addition, within the essence and scope of the present invention may change and new elements of design.

Industrial applicability

The motor according to the present invention allows to reduce the size and reduce the manufacturing cost of the motor and provides the possibility of increasing the degree of freedom in the design.

1. The motor containing:
the first structure on the emitting range of the magnetic poles, where the specified number of magnetic poles formed a certain amount of magnetic poles that are arranged in a certain direction and are arranged so that each two adjacent magnetic poles have polarity different from each other;
the second structure, comprising a number of anchors, where the specified number of anchors formed by a set of anchors arranged in a certain direction and placed opposite to the specified number of magnetic poles for generating a moving magnetic field moving in a certain direction, between the specified number of anchors and the specified adjacent magnetic poles under the action of a certain set of magnetic poles anchors generated in the specified set of anchors while applying thereto an electric power; and
the third structure, which includes a number of elements of magnetic material, where the specified number of elements of magnetic material is formed to a specific set of elements of magnetic material, arranged in a certain direction with a clearance to one another and are placed so that the specified number of elements of magnetic material is located between the specified near the magnetic poles and the specified number of anchors,
moreover, the ratio between the number of magnetic poles of the anchors, the number of magnetic poles and cyclobutanone elements of magnetic material within a certain area along a particular direction is given by the ratio of 1:m:(1+m)/2 (m≠1.0 in).

2. The electric motor according to claim 1, characterized in that it further comprises:
a means of measuring the relative vzaimoporozhdeniya for measuring the relative vzaimoporozhdeniya between these structures from the first to the third; and
means to control the moving magnetic fields based on the measured relative vzaimoporozhdeniya between these structures from the first to the third.

3. The electric motor according to claim 2, characterized in that the said means of measuring the relative vzaimoporozhdeniya measures as relative vzaimoporozhdeniya of these structures from the first to the third electrical angles specified the first structure and the third structure relative to the specified second patterns, and
this tool controls the moving magnetic fields on the basis of the difference between the value obtained by multiplying the measured electrical angle specified third structure on the (1+m), and a value obtained by multiplying the measured electrical angle specified first structure on m.

4. The electric motor according to any one of claims 1 to 3, characterized in that the magnetic poles are magnetic poles of permanent magnets.

5. The electric motor according to claim 1, characterized in that the electric motor is a rotating machine.

6. Elektrodvigatel the ü according to claim 1, wherein said motor is a linear motor.



 

Same patents:

FIELD: electricity.

SUBSTANCE: two diodes (D3, D4) which have insignificant cost and dimensions are introduced to single-pole or two-pole isolating converter with three windings (Lp, Ls1, Ls2) and one magnetic conductor.

EFFECT: reducing the cost of isolating converter supplying constant voltage to load terminals and decreasing the dimensions of the scheme.

14 cl, 25 dwg

FIELD: electricity.

SUBSTANCE: in the method to control an induction propulsion engine, using the difference between the preset and measured values of active power, the angle of optimal sliding and angle of rotor rotation calculated in accordance with the invention formula, the induction engine stator field rotation angle is determined, by summation of the optimal sliding angle and the rotor rotation angle, using the calculated values of the voltage vector amplitude and the angle of the induction engine stator field rotation, according to the vector PDM law, signals are generated to control an autonomous voltage inverter, and in the mode of induction engine field weakening, using the difference between maximum specified and calculated values of the voltage vector amplitude, additional sliding is generated, with account of which a new value is produced for the angle of the stator field rotation, and signals are generated to control an autonomous voltage inverter, at which sliding and current of the induction engine increase, and the mode of power constancy is preserved as the field weakens.

EFFECT: control of an induction propulsion engine in a wide range of rotation frequency under conditions of power limitations of an incoming source of power in a vehicle.

2 dwg

FIELD: electricity.

SUBSTANCE: in the method to control an induction propulsion engine, using the difference between the preset and measured values of active power, the angle of optimal sliding and angle of rotor rotation calculated in accordance with the invention formula, the induction engine stator field rotation angle is determined, by summation of the optimal sliding angle and the rotor rotation angle, using the calculated values of the voltage vector amplitude and the angle of the induction engine stator field rotation, according to the vector PDM law, signals are generated to control an autonomous voltage inverter, and in the mode of induction engine field weakening, using the difference between maximum specified and calculated values of the voltage vector amplitude, additional sliding is generated, with account of which a new value is produced for the angle of the stator field rotation, and signals are generated to control an autonomous voltage inverter, at which sliding and current of the induction engine increase, and the mode of power constancy is preserved as the field weakens.

EFFECT: control of an induction propulsion engine in a wide range of rotation frequency under conditions of power limitations of an incoming source of power in a vehicle.

2 dwg

FIELD: electricity.

SUBSTANCE: in the method to control an induction propulsion engine, using the difference between the preset and measured values of active power, the angle of optimal sliding and angle of rotor rotation calculated in accordance with the invention formula, the induction engine stator field rotation angle is determined, by summation of the optimal sliding angle and the rotor rotation angle, using the calculated values of the voltage vector amplitude and the angle of the induction engine stator field rotation, according to the vector PDM law, signals are generated to control an autonomous voltage inverter, and in the mode of induction engine field weakening, using the difference between maximum specified and calculated values of the voltage vector amplitude, additional sliding is generated, with account of which a new value is produced for the angle of the stator field rotation, and signals are generated to control an autonomous voltage inverter, at which sliding and current of the induction engine increase, and the mode of power constancy is preserved as the field weakens.

EFFECT: control of an induction propulsion engine in a wide range of rotation frequency under conditions of power limitations of an incoming source of power in a vehicle.

2 dwg

FIELD: electricity.

SUBSTANCE: reversing electromechanical gear comprises an electric motor case (1), a shaft (rotor) (2) of the electric motor, bearing supports (3), a controller (4) of a moment of inertia of the shaft (2), a braking disc (5), current-carrying sliding contacts (6). The device operates on the basis of the technical system kinetic moment variation law to produce a reverse effect and to convert the value and the direction of the machine actuator velocity. Depending on the ratio of the moments of inertia - the value and the direction of the electric motor case (1) with the braking disc (5) will vary. The value of the ratio may be changed using the controller (4) of the shaft (2) moment of inertia.

EFFECT: invention provides for reversing and smooth control of the angular velocity value.

2 cl, 1 dwg

FIELD: electricity.

SUBSTANCE: method of asynchronous control for four-quadrant converter is implemented by asynchronous sine pulse-width modulation with shift of clock and modulating signals in reference to main voltage phase. Switching of converter power keys is made at instant of time determined by ratio of modulation voltage and sweep voltage of sawtooth voltage generator on the basis of logic functions. Control pulses are generated by means of clock signal comparison with pre-set modulating sine signal variable in frequency and amplitude: sign of modulating signal is changed to the opposite one twice for instants of time corresponding to points of output voltage natural commutation. In compared channel high level of pulse-width modulated signal is generated if clock signal is less than pre-set signal or low level of pulse-width modulated signal is generated if clock signal is more than pre-set signal. In output channel two coupled output control signals are generated with inversion to each other from the first and second converter arms and simultaneously with commutation of modulating signals output signals are inverted in reference to pulse-width modulated signals in compared channel. Sawtooth signal is used as a clock signal. While generating control signals for converter keys clock signal is shifted in phase in reference to mains voltage transition through zero. Value of clock signal angle of shift is equal to value of modulating signal phase. Thus, phase shift of modulating signal in reference to mains voltage is asynchronous in regulation process.

EFFECT: generation of line current waveform of improved shape, close to sine wave, which contributes to increase of power factor and efficiency factor of four-quadrant converter due to form factor of input current within the whole range of loads.

6 dwg

FIELD: electricity.

SUBSTANCE: control (17A) unit is configured to open shutting down contactor (16) of electric motor not at the moment when detected current condition is determined as abnormal but at the moment when moment when current condition is determined as normal even when basic "MKCO" command becomes switching-off command (L level).

EFFECT: creation of driving controller for alternating current motor which can prevent excessive voltage generation between electric motor lines and between electric motor shutting down contactor contacts, and continuous electric arc creation between shutting down contactor contacts.

13 cl, 9 dwg

FIELD: electricity.

SUBSTANCE: motor torque setting corrector is introduced into alternating current drive and is used for formation of stator current vector by forming instantaneous phase values of stator current, which amplitude and frequency depend on setting and correction signals. Maintenance of optimal level for stator current amplitude and frequency provides optimal angle φ0 between vectors of stator current and rotor magnetic linkage equal to 45° and minimises consumption of stator current. Maintenance of optimal level φ0 is ensured by closed loop of angle control; measurement of angle φ0 is done by measurement of phase shift angle between instantaneous values of stator current and calculated values of rotor magnetic linkage. Invertor generates rotor phase currents with amplitude and frequency required to generate torque setting provided that current consumption by stator is minimised and magnetic circuit is used completely. Magnetic circuit operates with real three-phase system of coordinates that excludes coordinates conversion which complicate calculation and set strict requirements to controller.

EFFECT: design simplification and improvement of dynamic behaviour.

3 dwg

FIELD: electricity.

SUBSTANCE: motor torque setting corrector is introduced into alternating current drive and is used for formation of stator current vector by forming instantaneous phase values of stator current, which amplitude and frequency depend on setting and correction signals. Maintenance of optimal level for stator current amplitude and frequency provides optimal angle φ0 between vectors of stator current and rotor magnetic linkage equal to 45° and minimises consumption of stator current. Maintenance of optimal level φ0 is ensured by closed loop of angle control; measurement of angle φ0 is done by measurement of phase shift angle between instantaneous values of stator current and calculated values of rotor magnetic linkage. Invertor generates rotor phase currents with amplitude and frequency required to generate torque setting provided that current consumption by stator is minimised and magnetic circuit is used completely. Magnetic circuit operates with real three-phase system of coordinates that excludes coordinates conversion which complicate calculation and set strict requirements to controller.

EFFECT: design simplification and improvement of dynamic behaviour.

3 dwg

FIELD: electricity.

SUBSTANCE: device for control of alternating current motor consists of three-phase invertor (2) which is connected to DC source (1) and outputs three-phase alternating currents to AC motor (6); current detector (3, 4, 5), which detects current of AC motor (6); command module (50) for control of voltage/PWM signals, which calculates command to control invertor (2) output voltage on the basis of current detector (3, 4, 5) signal and generates pulse-width modulated signal to control switching element in invertor (2) based on command of output voltage control; module (100A) for compensation of motor current unbalance, which generated compensation values for motor current unbalance for respective phases on the basis of current of at least any two phase of AC motor (6) current and sets compensation value for motor current unbalance for remaining phase equal to zero, and pulse-width modulated signal of two phases is directly or indirectly adjusted in command module (50) for control of voltage/PWM signals on the basis of compensation values for motor current unbalance in compliance with invertor (2) excitation mode.

EFFECT: car driving.

13 cl, 8 dwg

FIELD: engineering.

SUBSTANCE: suspension comprises a cradle (6) with a sphere (2) positioned inside. The first electric magnet array (5) is positioned on the external surface, while the second electric magnet array (7) is positioned inside the cradle. The sphere is suspended in the cradle by means of mutual magnetic repulsion of some of the magnets in both arrays in such a position where the partially spherical surfaces of the cradle and the sphere are almost concentrical in relation to their common centre. Such a position is required to control the attitude of the sphere in relation to the cradle by means of magnetic interaction between other magnets of the two arrays.

EFFECT: improved suspension durability; simplified assembly.

7 cl, 5 dwg

FIELD: electricity.

SUBSTANCE: linear electromagnet motor comprises an axial channel, where a working element (9) is placed in the form of a smooth bar or a wire, comprises cylindrical stator (1), return spring (8), the first cover (2), the first winding (3), the first pulling-drawing anchor (5) with a flat disc part (7). The motor is equipped with a mechanism for jamming of the working element as the anchor is pulled in, and a double-arm lever (13) for wedging, when the anchor is returned by the spring. The stator is divided inside in a transverse manner by a pole-orifice (19) into two identical parts and comprises same as the first ones the second cover (2), the second winding (4) and the second anchor (6), which actuates alternately with the first anchor. Movement of each anchor is limited when it is pulled into the winding by the pole-orifice, when returned by the spring - by covers. Ends of the return spring passing via the pole-orifice enter the cylindrical bores at the anchor ends. On the outer surface of the stator there is a circular rectangular slot made coaxially and symmetrically relative to the inner pole-orifice.

EFFECT: provision of working element reversal.

1 dwg

FIELD: transport.

SUBSTANCE: invention relates to motor drives for bicycles. Proposed motor drive comprises one or several reversible permanent-magnet machines fitted on one shaft (3) or coupled via couplings. Every said machine comprises annular stator (1-1), (2-1) with permanent magnet (1-3), (2-3) made up of a section of hollow torus with C-like slot arranged on its inner side. One or two windings are fitted on edges of rotor (1-2), (2-2) to displace in said C-like slot. Winding circular arc length equals that of permanent magnet (1-3), (2-3). Said windings are connected with constant current source via current conducting rings, brushes arranged on stator vase, and collectors. Stators (1-1), (2-1) are turned relative to each other.

EFFECT: simplified design and smaller dimensions.

6 dwg

FIELD: electricity.

SUBSTANCE: when a common switch (23) is put on, power is simultaneously supplied to all windings. Due to electromagnetic forces developed by windings, all anchors will attempt to approach poles of appropriate electromagnets. However, since gaps between anchors and electromagnets differ, the highest electromagnet force will occur between an electromagnet (1) and an anchor (6). A head of its cylindrical rod, touching the rear surface of an anchor (7), will move the anchor towards an electromagnet (2), reducing the distance between it and the electromagnet (2). Similar action will be performed by all cylindrical rods, pushing appropriate anchors. When the distance between the anchor (7) is reduced down to the value equal to δ, the interaction force between this anchor and the electromagnet (2) will achieve the pull-in level, and the anchor (7) will start active motion, pushing all subsequent anchors. Then a gap (5) is set between an anchor (8) and an electromagnet (3). Entering the period of active motion, it will push all remaining anchors by value δ. The process will continue, and at the final stage the interaction between an anchor (10) and an electromagnet (5) becomes active. At the same time the process of motion itself will somewhat remind the start-up of a multi-stage rocket: each new connection of a subsequent electromagnet gives additional acceleration to a movable system of anchors. Therefore the latest stage of connection will move with higher speed compared to previous ones with an increased gap between its contacts.

EFFECT: increased range of anchor motion, increased gap between movable and fixed contacts, kinetic energy of an anchor in process of motion and efficiency factor.

7 cl, 7 dwg

FIELD: electricity.

SUBSTANCE: fixed electromagnets (1, 2, 3, 4, 5) are arranged one after the other in axial direction. Each electromagnet is equipped with a movable anchor, accordingly (6, 7, 8, 9 and 10). Number of electromagnets and anchors depends on the value of the required gap between the last electromagnet along with the movement of anchors and its anchor. Movable anchors (6, 7, 8, 9, 10) of electromagnets are installed relative to each electromagnet with a gap that differs by the value nδ, where δ is gap of the first anchor along the anchor movement, n is a multiplier with an electromagnet number, to which this or that anchor is related. All neighbouring anchors at both sides are connected to each other by means of a flat V-shaped spring (11, 12, 13, 14 and 15). Electromagnets are equipped with excitation windings (16, 17, 18, 19, 20). All electromagnets are rigidly connected to each other by means of a common frame from longitudinal non-magnetic planks that cover the whole system at the ends. Between an anchor and an appropriate electromagnet there are return springs installed. Each electromagnetic drive is equipped with a normally open contact. Fixed contacts are joined with planks, and movable contacts - with anchors. The distance between contacts differs by the value nδ. Each drive is equipped with normally closed contacts.

EFFECT: increased range of anchor movement, larger gap between movable and fixed contacts, increased kinetic energy of an anchor in process of movement.

4 cl, 8 dwg

FIELD: electrical engineering.

SUBSTANCE: linear drive 1 comprises stator 2 accommodating slide 7 reciprocating there inside along axis 3. Note here that stator 2 incorporates magnetising core 4 with poles 5, 6. Note also that slide 7 comprises assemblage of alternating opposite-polarisation magnets 22, 23 arranged one after another along axis 3. Said stator 2 comprises at least two drive coils 16, 20 arranged opposed relative to slide 7. Besides said magnets 22, 23 of said slide 7 feature length L2 along axis 3 that corresponds, in fact, to sum of poles widths B1 and distance A1 between poles 5, 6. Skewed surface 9 of supports 8, 10 or appropriate selection of length of magnets 22, 23, slide 7, pole width B1 and distance A1 between poles 5, 6 improve control or adjustment of reciprocation of rotor 7.

EFFECT: higher accuracy and efficiency of control, power savings.

18 cl, 5 dwg

FIELD: electricity.

SUBSTANCE: invention is a machine (linear valve induction generator motor) that can equally operate as a generator and as a motor and possesses a number of characteristics allowing optimisation of weight and power ratio as well as production costs. The machine concerned has several air clearances crossed by a single magnetic flux wherein magnetising force is formed. The flux is generated by a series of coils (6) arranged on active parts The active parts are two frames (4) and (5) whereon the magnetic flux is grounded. In the above magnetic circuits other active parts may exist wherethrough the magnetic flux grounding fails to occur. A series of passive elements (habitually represented by transducers (1) and (2)) in the course of their motion relative to the active parts cause change of the circuit magnetic with respect to the position causing magnetic force. The most unique feature of the invention consists in the magnetic flux returning through only two butt-end active parts (4) and (5).

EFFECT: reduction of stray flux at the poles of the proposed generator motor and reduction of its mass, weight and cost.

2 cl, 2 dwg

FIELD: electrical engineering.

SUBSTANCE: invention relates to electrical engineering, particularly to linear permanent magnet stepper motors and can be used in industrial, transport and electromechanical systems. The linear stepper motor has main imbricated cores with stator heelpieces 1, with wide cores 2 and with narrow cores 3, high-coercivity permanent magnets 4, two-phase winding 5 with phases A and B, and an additional imbricated core 8. Plates 6 are mechanically connected to a nonmagnetic plate 10 and form a liner. Plates 7 are mechanically connected to the stator by a nonmagnetic plate 11. Each plate has alternating ferromagnetic and nonmagnetic elements, lying crosswise. All magnetic elements of the plates and all teeth have the same lateral dimensions. Magnetic elements of the plate of the liner are at equal distance from each other, which determines the tooth spacing. Teeth on the wide and narrow cores are shifted by half the tooth division, and teeth on cores of neighbouring stator magnetic circuits - by quarter of the tooth division. Teeth of main stator magnetic circuits, additional magnetic circuit and magnetic elements of the plate, joined to the stator, have the same longitudinal position. Phases A and B lie alternately on wide cores. Neighbouring permanent magnets are magnetised tangentially and head-on.

EFFECT: improved weight and size characteristics.

3 dwg

FIELD: electrical engineering.

SUBSTANCE: invention relates to electronics and can be used for making a machine with discrete translational unrestricted motion of the actuating element. The device contains a stator, which consists of a side member (2) and a bottom part (1). A winding (9) is put into a stator bore. The armature is composite and consists of a cylindrical part (3) and has disc-shaped part (4) on the side of the guide housing (6). Between the bottom part of the stator (1) and the cylindrical part of the armature (3) there is recoil spring (10). The actuating element (13) can be in form of a rope, flexible bar or wire, let through the axial channel of the armature through an opening in the guide housing (6) and the bottom part of the stator (1). Power articulation of the actuating element with the armature in the working stroke is provided by spring-loaded keying on cone-shaped elements (11), for example in form of locking pieces, opened by a releasing mechanism in form of a double-arm swivelling lever (5) during the working stroke, put into the cavity of the disc-shaped part of the armature (4) with one arm, and on locking members (11) by the second arm. The lever has a through-hole where the actuating element is put. Coaxiality of the armature and the stator is provided by guide pins (8).

EFFECT: simpler design with widening of operating capabilities and field of use.

1 dwg

FIELD: engines and pumps.

SUBSTANCE: invention is related to electric machines to linear step motors for discrete electric drive. Linear electric motor comprises the following: stator 1 that consists of magnetic body 2, inside of which between magnetic poles 3 magnetising coils 4, 5, 6 and 7 are installed, intermediate poles 8, which are fixed by non-magnetic inserts 9 on thread 10. Magnetic poles 3 of every coil 4, 5, 6, and 7 are separated between each other by non-magnetic rings 11, which are fixed by pins 12. End magnetic pole 13 is fixed to magnetic body 2 by bolt 14. Anchor 15 consists of magnetic 16 and non-magnetic 17 rings placed in alternating sequence on non-magnetic rod 18. Shape of section in ends of magnetic poles 3, intermediate poles 8 and end pole 13 is created with faces 19 and 20. Shape of section in ends of magnetic rings 16 is created by faces 21. The main magnetic flow F, which is separated into working magnetic flow F1, passing through working gap 5, and parasite magnetic flows F2 that swells to the side of magnetising coil 4, and F3, that closes practically in center of anchor 15.

EFFECT: increased efficiency factor.

1 dwg

FIELD: electricity.

SUBSTANCE: axial two-input contactless dynamo includes body, permanent multipolar magnet of induction coil subexciter, lateral axial magnetic conductor with polyphase armature winding of subexciter, single-phase winding of subexcitor and auxiliary excitation winding of exciter which is connected to DC power supply source through contacts, inner axial magnetic conductor with polyphase armature winding of exciter and single-phase excitation winding of main generator, lateral axial magnetic conductor with polyphase armature winding of main generator, shaft fixed in bearing assemblies and rigidly bound with permanent multipolar magnet of induction coil subexciter and inner axial magnetic conductor by means of respective discs. Single-phase excitation winding of exciter is connected to polyphase armature winding of subexciter through polyphase double-wave rectifier. Single-phase excitation winding of main generator is connected to polyphase armature winding of exciter through polyphase double-wave rectifier.

EFFECT: possibility of adding and conversion of mechanical power and DC electrical power into AC polyphase electrical power, simplification of magnet system manufacturing technology, quality improvement of generated voltage.

1 dwg

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