Method for automatic adjustment of frequency of supporting signal of receiving station, method for estimating mismatch of frequency of beam signals relatively to frequency of supporting signal, device for automatic adjustment of frequency of supporting signal of receiving station

FIELD: broadband cell radio communication systems, possible use for correcting frequency of supporting generator of mobile stations, necessary for provision of coherent message receipt mode.

SUBSTANCE: serial cyclic procedure of estimating mismatch and its compensation uses original algorithm for determining maximum of solving function by two of its values from the area where frequency is undetermined, thus making it possible to decrease frequency mismatch compensation time. Proposed procedure has increased interference resistance, because it uses additional digital supporting signal. Proposed algorithm can function with different, including substantial, values of original frequency mismatch. Algorithm is efficient both at beginning stage (in frequency capture mode) and during following automatic adjustment. Proposed variant of realization of frequency automatic adjustment allows precise adjustment of frequency of supporting generator even in case of very low signal-noise ratio for signal being received.

EFFECT: increased precision of estimation of frequency of input multi-beam signal, including cases with substantial frequency mismatches.

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The present invention relates to the field of broadband cellular radio communication systems and can be used, in particular, in the mobile stations in the communication systems according to the UMTS, cdma2000, etc. to adjust the frequency of the reference generator.

Quality-locked loop frequency control generator of the receiving station is determined by the efficiency of the adjustment of the frequency mismatch between the frequency and the frequency of the input signal.

During operation of the system broadband cellular communication possible misalignment ΔF between the carrier frequency of the received signal and the reference oscillator frequency of the receiving station. This misalignment (frequency shift detuning) may be due to Doppler frequency offset (due to the movement of the mobile station), the instability of the frequency of the reference generator base and mobile stations and random fading (fading) signal due to multipath propagation. Due to the detuning of the frequency of the communication quality can deteriorate. Therefore, the problem of estimating this frequency mismatch ΔF to further adjust the frequency of the reference oscillator of the receiving station for good reception of messages.

In any communication system, there is a priori interval of possible mismatches frequency [-Fmax,+Fmax]. For example, the R, for communication systems, organized in accordance with the standards UMTS and cdma2000, Fmaxcan be up to several kilohertz. In the operation of the system PLL frequency value ΔF for these systems must be reduced to values within a ±150 Hz.

In cellular communication systems, CDMA (Code Division Multiple Access - multiple access code division) for the purposes of the PLL uses the pilot signal. For example, the mobile station communication system of the UMTS signal pilot channel P-CPICH (Primary Common Pilot Channel General direct the pilot channel of the base station.

Locked loop frequency generator receiving station is performed after the establishment of the timing of the receiving station with the base station signal. Effect simultaneous transmission of the pilot and the information signal locked loop frequency information messages CDMA communication systems may be based on estimates of the carrier frequency signal of the P-CPICH.

The most commonly used methods are the phase-locked loop (PLL). All PLL implement the idea of detecting and filtering quasi-regular phase change and use the resulting estimates to generate a signal correction. Discriminatory characteristics of the digital phase detector is periodic and has a sawtooth shape. The periodic nature of discrimination the th characteristics is the cause of the capture of a false evaluation of the frequency, if the counting time interval there will be a shift signal in phase by more than ±π/n, where n is the multiplicity of manipulation when receiving photomanipulating signal.

The fundamental differences between all existing methods PLL consist in the implementation of the operation of estimating a constant phase shift (transformation phase shift in the measured parameter)that is uniquely associated with an existing frequency shift. As one evaluation phase under conditions of noise and fading of the signal is usually not enough to provide an estimate of the frequency shift produced the accumulation and averaging of the estimates. The duration of the averaging determines the accuracy of the generated estimate of the frequency shift and the inertia of the automatic frequency control system as a whole. The transformation function of the received signal evaluation phase in the control signal typically represents the dependence of the measured parameter from the detuning frequency and optimized in accordance with the requirement of a minimum of complexity.

One of the most simple ways to assess a constant phase shift complex photomanipulating signal is the selection of the phase shift between two successively adopted by the complex characters and their subsequent averaging [1. Jspencer. "Digital satellite communications". M: Communications. 1978, str - 404]. This operation can be implemented as a multiplication of the current is the first comprehensive reference received signal with the complex conjugate of the previous count followed by filtration of the obtained Raman component.

In the time domain, the average frequency of the signal can be estimated electron-counting frequency meter by counting the number of positive and negative transitions of the signal through the zero level per unit of time [2. Vservices. "Radioavtomatika". M: Owls. radio, 1982]. However, this estimate of the average frequency (through kvazichastitsy) always turns out to be too high in relation to the average value. Improving the accuracy of estimation of the mean frequency is possible by applying the algorithm using fractional differentiation signal in the time domain, but in this case, the procedure increases the computational complexity of the method.

The known method and device for synchronizing a receiver in a digital communication system described in [3. Patent US#4,938,906 "Frequency Estimation system", Jan.8, 1991]. This method uses the frequency estimation by the method of linear regression, analyzing the timing phase. Thus formed solution, the optimal least-squares. Described in the patent US#4,938,906 device allows to obtain an estimate of the frequency shift with high accuracy, but has the disadvantage common to all digital PLL, as it has a limit on the maximum phase shift between the analyzed samples. This imposes constraints on the maximum frequency detuning.

In the above communication systems for spread spectrum IP is resultsa orthogonal code sequence and scramblers codes. When receiving produce dispergirovanija (correlation processing). Typically, the signal-to-noise ratio for the input signal is very low, and the correlation treatment significantly increases the signal-to-noise.

On the other hand, as noted above, for all digital PLL there is a limit on the maximum phase shift between the times ±π/n. At large frequency shift of the phase shift for the received symbols of the useful signal will exceed the maximum allowed, which does not allow to apply the system PLL to correct significant difference in the frequency of a given a priori interval [-Fmax,+Fmax].

A known method of constructing the automatic frequency control system based on a frequency discriminator using a pair of adjacent filters. The basic idea implemented in this case, consists of nding the center of gravity of the power spectrum of the signal [4. Lindsley "synchronization Systems in communication and control". The owls. radio, 1979; 5. Patent US#5,487,186. "Automatic frequency control using split-band signal strength measurements", MKI N 04 1/16 In. Scarpa, Carl G.; Hitachi America, Ltd.].

This method allows you to control the frequency of the local oscillator, which provides accommodation for the spectrum of the received signal at the center of the bandwidth of the receiver without removing the imposed expansion sequences (i.e., no correlation signal processing). Taken with the drove is divided between two adjacent frequency filters, occupying half of the bandwidth, and compares the signal levels in each of these bands. The difference signal is used to adjust the local oscillator so that the average frequency of the received signal coincides with the average frequency bandwidth, the frequency of the receiver [5. Patent US#5,487,186. "Automatic frequency control using split-band signal strength measurements", MKI N 04 1/16 In. Scarpa, Carl G.; Hitachi America, Ltd.].

The disadvantage of this approach is the need to build two filters of high order and a great time savings to achieve sufficient accuracy assessment.

In terms of fading and multipath propagation of radio waves in communication systems based on CDMA technology, while taking aim to use energy just multipath signal. To do this, determine the delay of each signal beam and optimally summarize signals rays. In result increase the reliability of the reception of useful information. Such signal processing is usually performed using a Rake receiver.

The closest in technical essence to the proposed method PLL frequency are the method and the device described in [6. Patent US#6,278,725 B1. "Automatic frequency control loop multipath combiner for a rake receiver", MKI N 04 1/707; H 04 L 27/00. Antoine J.Rouphael, Farbod Kamgar. Date of Patent: Aug.21, 2001].

In this patent the proposed method and the automatic on the construction of frequency assessment results of frequency for a single multipath component of the signal. This method eliminates the effects of Doppler effect on the various components of a multipath signal and to improve the quality of received data during processing in a Rake receiver.

The method of automatic frequency reference signal receiving station, proposed in the prototype, is that for each detected signal beam

- emit narrow-band signal of the beam, forming the product of the signal beam on a pseudo-random sequence of the pilot signal, a temporary position which corresponds to the signal of the beam,

- Peremohy selected narrowband signal beam on the in-phase and quadrature components of the reference signal, forming in-phase and quadrature components of the selected narrowband signal beam,

- produce a digitized in-phase and quadrature components of the selected narrowband signal beam,

- perform filtering in-phase and quadrature digital components selected narrowband signal beam,

- form the signal detuning frequency of the signal beam with respect to the frequency of the reference signal using the filtered components of the selected narrowband signal beam,

- summarize the signals of the detuning frequency of the signal of each beam relative to the frequency of the reference signal,

- filter the coziness of the total signal detuning, forming the average detuning the frequency of the input beam signal,

- adjust the frequency of the reference signal at the average detuning the frequency of the input beam signal,

for each beam form the relative detuning of the frequency of this beam by subtracting the average detuning the frequency of the received multipath signal from the signal detuning frequency of the beam relative to the frequency of the reference signal.

According to the description of the prototype of the method of automatic frequency reference signal corresponds to the following formal mathematical model.

Input N multipath component signal has the form

where- a reference frequency, Andjis the amplitude, ωj- the frequency Θjis an unknown constant phase and τjis the time delay of the j-th component of the received signal, n(t) is additive noise.

It is assumed that the search procedure signal beams are pre-made and the time delays of the signals rays τjappreciated. Then the signal of the j-th beam

Labelingformula (2) can be written as

here Θj(t) is the unknown phase, time-dependent.

In case independently what about the noise of the low-frequency quadrature components of y Sj(t) and yCj(t) [6, Fig.1] signal of the j-th beam can be represented as follows

Frequency mismatch Δωj. between the frequency ωjthe received signal of the j-th beam and the reference frequencyyou can determine from the equation

As

the error frequency for the analog signal of the j-th beam

In the discrete case, the expressions for the derivatives can be represented in the form of a finite difference in the time t=nΔT, n=1...N

where ΔT is the sampling period, and the error frequency for the j-th beam

In this patent the detuning of the frequency of each of the j-th beam Δωjit is proposed to determine the relative frequency of the reference signalfrom the expressionIn turn, the detuning of the frequency of the reference signal Δωcfis estimated from the expression (8) for the total average errorin the steady state.

Since in steady mode.

On Rosstroy the Δ ωcfadjusts the reference frequency.

Thus, the frequency of the reference signal is generated by control signal corresponding to the average detuning of the frequency of all processed rays. The frequency of the signal for each j-th beam is produced considering the magnitude of the frequency mismatch δjaccording to the following expressionwhere δj=Δωj+Δωcf- evaluation of the frequency mismatch of the j-th component.

For the implementation of the prototype method can be used in the device block diagram is presented in figure 1. The device consists of N identical channels of signal beams, each of which contains the first multiplier 1, the second multiplier 4, the first analog-to-digital Converter (ADC) 5, the first filter 6, the third multiplier 7, the second analog-to-digital Converter 8, the second filter 9, the evaluation unit of the detuning frequency of the signal beam 10. The structure of the device also includes a phase shifter 2, the pseudo-random sequence generator (gpsa) 3, the first adder 11, N second adders 12-1-12-N, a voltage controlled oscillator (VCO) 13, a digital-to-analogue Converter (DAC) 14, the filter ring feedback 15.

First, the signal inputs of the first multiplier products 1-1-1-N United and Vlada input device. The second inputs of the first multiplier products 1-1-1-N connected to respective outputs of the gpsa 3, to which input signal control search results. The output of each of the first multiplier products 1-1-1-N corresponds to the narrowband signals detected beams and respectively connected with the first input of the second 4 and the third 7 multiplier products of the corresponding channel signal beams. The second inputs of each of the second multiplier 4 all N channels of signal processing beams connected to the output of the quadrature component of the reference signal of the phase shifter 2, and the second inputs of each of the third multiplier 7 all N channels of signal processing beams connected to the output of the in-phase component of the reference signal generator, voltage-controlled 13. The output of reference signal generator controlled by a voltage 13 is connected also to the input of the phase shifter 2.

In each channel the signal beams output quadrature component of the selected narrowband signal beam of the second multiplier 4 through the first analog-to-digital Converter 5 and the first filter 6 is connected to the first quadrature, the input of the evaluation unit of the detuning frequency of the signal beam 10, and the output of the in-phase component of the selected narrowband signal beam of the third multiplier 7 via a second analog-to-digital Converter 8 and the second filter 9 to connect the eh with the second phase, the input of the evaluation unit of the detuning frequency of the signal beam 10. The outputs of each of the blocks of the evaluation of the detuning frequency of the signal beam 10-1-10-N are output signals of the detuning frequency of the respective beams. The output signal of the detuning frequency of the beam of each assessment unit of the detuning frequency of the signal beam 10-1-10-N connected to the respective input of the first adder 11 and the first input of the corresponding second adder 12-1-12-n the output of the first adder 11, which is the output of the total detuning frequency through the filter ring feedback 15 is connected to the input of digital to analog Converter 14 and the second input of each second adders 12-1-12-n Output filter ring feedback 15 is the output signal of the average detuning of the frequency of the reference signal. The output of the digital to analogue Converter 14 is a control signal output and is connected to the controlled input of the generator, voltage-controlled 13. The output of each of the second adder 12-1-12-N corresponds to the signal of the relative detuning of the frequency of the corresponding signal beam and an output device.

Function prototype as follows.

It is assumed that you have already performed a search signal rays in the range multipath and obtained estimates of their temporary status. These estimates are used as signal control the Oia search results for setup time delays in the gpsa 3 during the formation of copies detected signals rays. Input wideband multipath signal is supplied to the first signal, the inputs of the first multiplier products 1-1-1-N, the second inputs of which the output gpsa 3 come SRP detected pilot signals, temporary position which corresponds to the signals of these rays. As a result, the outputs of the multiplier products 1-1-1-N form N narrowband signals rays. Each of the selected narrowband signals fed to the first inputs of the second and third multiplier products 4 and 7 of the respective channel signal processing beam. To the second input of the multiplier 7 receives the in-phase component of the reference signal output from the VCO 13. To the second input of the multiplier 4 receives the quadrature component of the reference signal from the output of the phase shifter 2. As a result, the outputs of the second 4 and the third 7 multiplier products form respectively the quadrature and in-phase components of the detected signals rays. Next, signals of the quadrature and in-phase components, passing respectively through the first 5 and the second 8 ADC, the first 6 and second 9 filters, converted to digital form and are shifted in frequency down to a video or an intermediate frequency. The output signals of filters 6 and 9 are respectively a digital quadrature and in-phase components of the selected narrowband signal beam, which act respectively on the first and second input block OC the NCI of the detuning frequency of the signal beam 10. The output of block 10 to form the signal detuning frequency signal corresponding beam Δωjregarding the frequency of the reference signal of the VCO 13. The generated signals of the detuning frequency signals rays are received at the first inputs of the respective second adders 12-1-12-N and to corresponding inputs of a first adder 11. In the first adder 11 summarize the signals of the detuning frequency of the signal of each beam relative to the frequency of the reference signal. The total signal detuning frequency is filtered in the filter ring feedback 15 forming the average detuning the frequency of the input beam signal, which is fed to the input of the DAC 14 and the second input of each of adders 12-1-12-n average detuning the frequency of the input multi-output DAC 14 is formed control signal, whereby adjusting the frequency of the reference signal at the output of the VCO 13. In the adders 12-1-12-N for each beam form the relative detuning of the frequency of this beam by subtracting the average detuning the frequency of the received multipath signal from the signal detuning frequency of the beam relative to the frequency of the reference signal. The outputs of adders 12-1-12-N are the outputs of the relative shift frequency signals rays and, respectively, the outputs of the device.

The way of estimating the signal detuning frequency signal is Ala beam relative to the frequency of the reference signal, used in the prototype is the following:

- delay digital filtered inphase and quadrature components of the selected narrowband signal beam,

- Peremohy not delayed filtered digital in-phase component of the selected narrowband signal beam and the delayed filtered digital quadrature component of the selected narrowband signal beam,

- Peremohy not delayed filtered digital quadrature component of the selected narrowband signal beam and the delayed filtered digital in-phase component of the selected narrowband signal beam,

- summarize formed works, evaluating the detuning frequency of the signal beam relative to the frequency of the reference signal.

To implement this way of estimating the signal detuning frequency of the signal beam relative to the frequency of the reference signal may be used by the evaluation unit of the detuning frequency of the signal presented in figure 2. The evaluation unit of the detuning frequency of the signal beam 10 in each processing channel includes first and second delay line 16, 18, the first and second multiplier products 17, 19 and the adder 20. Moreover, the input of the first delay line 16 and the second input of the second multiplier 19 are inputs digital in-phase component of the selected narrowband signal beam and soy is inany with the output of the second filter 9, the input of the second delay line 18 and the second input of the first multiplier 17 are inputs digital quadrature component of the selected narrowband signal beam and connected to the output of the first filter 6. The output of the first delay line 16 through the first multiplier 17 is connected to the first input of the adder 20, the output of the second delay line 18 via a second multiplier 19 is connected to the second input of the adder 20.

In each processing channel digital in-phase component of the selected narrowband signal beam received at the input of the first delay line 16 and to the second input of the second multiplier 19, and a digital quadrature component of the selected narrowband signal beam received at the input of the second delay line 18 and to the second input of the first multiplier 17. The first inputs of the multiplier products 17 and 19 are received respectively delayed digital in-phase component of the selected narrowband signal beam and the delayed digital quadrature component of the selected narrowband signal beam. The formed product with the output of multiplier products 17 and 19 summarize the given character in the adder 20, which form the signal detuning frequency signals rays. The generated signals of the detuning frequency signals rays are received at the first inputs of the respective second adders 12-1-12-N and to corresponding inputs of Pervov the adder 11.

The objective of the present invention, a more accurate evaluation of the frequency of the input beam signal, including a significant shift frequency.

The problem is solved by creating a group of inventions - how-locked loop frequency of the reference signal of the receiving station, the method of estimating the detuning of the frequency signals of the beams relative to the frequency of the reference signal and the device-locked loop frequency of the reference signal of the receiving station, which is performed in a single inventive concept and allow for the implementation to get an equivalent effect.

According to the claimed invention method PLL frequency reference signal receiving station, namely, that

- Peremohy the received signal to in-phase and quadrature components of the reference signal, forming in-phase and quadrature components of the received signal,

- perform filtering in-phase and quadrature components of the received signal,

- produce analog-to-digital conversion of the filtered in-phase and quadrature components of the received signal,

- form the real and imaginary part of the pseudo-random sequences pilot signal, a temporary position which corresponds to the delay signals of the detected rays,

for ka the Dogo found beam forming signal detuning frequency of the signal beam relative to the frequency of the reference signal and the signal beam, using digital filtered inphase and quadrature components of the received signal and the real and imaginary part of the pseudo-random sequences of the pilot signal of the beam,

- form the signal average detuning the frequency of the received multipath signal relative to the frequency of the reference signal, which

summarize the evaluation of the signal power of all rays,

for each beam form for assessing the strength of the signal beam to the sum of the estimated signal power of all rays,

for each beam Peremohy formed a relationship with the signal detuning frequency of the signal beam relative to the frequency of the reference signal,

form the average detuning the frequency of the received multipath signal relative to the reference signal, obtained by summing works on all rays,

- adjust the frequency of the reference signal at the average detuning the frequency of the received multipath signal relative to the reference signal,

- form relative detuning frequency of the signal for each beam, subtracting from the signal detuning frequency of the beam relative to the frequency of the reference signal average detuning the frequency of the received multipath signal relative to the reference signal.

A method of evaluating the detuning frequency signals rays versus frequency is pornoho signal, namely, that

- form the real and imaginary components of the in-phase component of the additional reference signal, computing the product of samples of the real and imaginary parts of the pseudorandom sequence, the delay corresponds to the delay of the signal of the beam on the samples in-phase component of the additional reference signal,

- form the real and imaginary components of the quadrature component of the additional reference signal, computing the product of samples of the real and imaginary parts of the pseudorandom sequence, the delay corresponds to the delay of the signal of the beam on the samples of the quadrature component of the additional reference signal,

form a first sum and the first differential reference signals, calculating the sum and the difference of valid components in-phase component of the additional reference signal and the imaginary components of the quadrature component of the additional reference signal,

- form the second sum and second differential reference signals, calculating the sum and the difference of the imaginary components of the in-phase component of the additional reference signal and the actual components of the quadrature component of the additional reference signal,

- create initial total in-phase and quadrature SOS is alausa, computing compositions of samples of the first total reference signal, respectively, at the timing phase and quadrature filtered digital in-phase and quadrature components of the received signal,

form a first differential in-phase and quadrature components, calculating the product of samples of the first differential reference signal, respectively, at the timing phase and quadrature filtered digital in-phase and quadrature components of the received signal,

form a second total in-phase and quadrature components, calculating the product of samples of the second total reference signal, respectively, at the timing phase and quadrature filtered digital in-phase and quadrature components of the received signal,

form a second differential in-phase and quadrature components, calculating the product of samples of the second differential reference signal, respectively, at the timing phase and quadrature filtered digital in-phase and quadrature components of the received signal,

- form an in-phase component corresponding to the increased frequency of the reference signal, summing the counts first overall in-phase component and the timing of the second differential quadrature component,

- form a quadrature component, according to stuudy increased the frequency of the reference signal, subtracting from the reading first total quadrature component samples of the second differential in-phase component,

- form an in-phase component corresponding to a reduced frequency of the reference signal, summing the counts of the first differential in-phase component and the second counts the total quadrature component,

- form a quadrature component, the corresponding reduced frequency of the reference signal by subtracting from the second counts the total in-phase component samples of the first differential quadrature component,

- accumulate N samples in-phase components corresponding to the increased frequency of the reference signal by N samples of the quadrature components corresponding to the increased frequency of the reference signal by N samples in-phase components corresponding to the reduced frequency of the reference signal by N samples of the quadrature components corresponding to the reduced frequency of the reference signal, where N is the number of coherent accumulations,

- calculate the squares of the results of the accumulation phase and quadrature components corresponding to the enlarged and reduced the frequency of the reference signal,

- form the coherent accumulation corresponding to the increased frequency of the reference signal, summing the squares of the results of the accumulation phase and quadrature component (s) is sufficiently increased the frequency of the reference signal,

- form the coherent accumulation corresponding to the reduced frequency of the reference signal, summing the squares of the results of the accumulation phase and quadrature components corresponding to the reduced frequency of the reference signal,

- form the estimate of the power of the signal beam corresponding to the increased frequency of the reference signal, accumulating the results of the coherent accumulation corresponding to the increased frequency of the reference signal, where K is the number of non-coherent accumulations,

- form the estimate of the power of the signal beam corresponding to a reduced frequency of the reference signal, accumulating the results of the coherent accumulation corresponding to the reduced frequency of the reference signal,

- find the estimate of the power of the signal beam, determining the maximum value of the evaluation signal power of the beam corresponding to the increased frequency of the reference signal, and estimates the signal power of the beam corresponding to the reduced frequency of the reference signal,

- form the ratio between the cardinality estimation of a signal beam corresponding to the increased frequency of the reference signal, and estimates the signal power of the beam corresponding to the reduced frequency of the reference signal, and estimating the signal power of the beam,

- form the signal detuning frequency of the signal beam relative to the reference signal, multiply formed Rel is the solution with additional frequency reference signal.

According to the invention, in a device-locked loop frequency of the reference signal receiving station, containing the first and second multiplier products, Phaser, the pseudo-random sequence generator, the first and second analog-to-digital converters, the first and second filters, the N blocks of the evaluation of the detuning frequency of the signal beam, a first adder, N second adders, a voltage controlled oscillator, and the first signal, the inputs of the first and second multiplier products are combined and input device, the first outputs of the N blocks of the evaluation of the detuning frequency of the signal beam are output signals of the detuning frequency signals rays relative to the frequency of the reference signal and connected to the first inputs of the respective second adders, the outputs of the second adders are the outputs of the relative detuning of the frequency of the signal beam, and output devices

added N multipliers, N divider, the third adder, the control unit, the second input of the first multiplier connected to the output of the quadrature component of the reference signal of the phase shifter, a second input of the second multiplier connected to the output of the in-phase component of the reference signal generator, voltage-controlled output reference signal generator, voltage controlled, is connected t the train to the input of the phase shifter, the output of the first multiplier, which is the output of the quadrature component of the received multipath signal through the first filter and the first analog-to-digital Converter connected to the second inputs of the N blocks of the evaluation of the detuning frequency of the signal beam, the output of the second multiplier, which is the output of the inphase component of the received multipath signal through the second filter and the second analog-to-digital Converter connected to the third inputs of the N blocks of the evaluation of the detuning frequency of the signal beam, the first inputs units estimates of the detuning frequency of the signal beam are connected to the outputs of the pseudorandom sequence generator that generates real and imaginary part of the pseudo-random sequences pilot signal beams, the input of the pseudo-random sequence generator is input control signal of the search results, the fourth inputs units estimates of the detuning frequency of the signal beam is connected to the control outputs of the control unit, the input of which is the input set the operation mode, the first outputs of blocks evaluation of the detuning frequency of the signal beam, which are the output signals of the detuning frequency signals rays relative to the frequency of the reference signal is connected to first inputs of respective multipliers, the second outputs of blocks evaluate the detuning of the hour is the notes of the signal beam, which are the outputs of the estimation of the signal power of the rays, is connected with the first inputs of the respective dividers and to the corresponding inputs of the first adder, the output of the first adder being the output of the sum of the estimates of the signal power of all rays, is connected to the second inputs of the dividers, the outputs of the dividers, which are the outputs of relationship cardinality estimation signal beam to the sum of the estimates of the signal power of all rays, are connected to second inputs of respective multipliers, the outputs of the multipliers are connected to the corresponding inputs of the third adder, the output of the third adder, the output of which is signal average detuning the frequency of the received multipath signal relative to the frequency of the reference signal, is connected to the second inputs second adders and the generator input, voltage-controlled.

Comparative analysis of the proposed method PLL frequency reference signal of the receiving station with the prototype shows that the inventive method is significantly different from the prototype.

The General features of the proposed method and the prototype:

- form the real and imaginary part of the pseudo-random sequences pilot signal, a temporary position which corresponds to the delay signals of the detected rays,

- form the signal detuning frequency signal each the beam relative to the frequency of the reference signal,

- form average detuning the frequency of the received multipath signal relative to the frequency of the reference signal,

- adjust the frequency of the reference signal at the average detuning the frequency of the received multipath signal relative to the reference signal,

- form relative detuning frequency of the signal for each beam, subtracting from the signal detuning frequency of the beam relative to the frequency of the reference signal average detuning the frequency of the received multipath signal relative to the reference signal.

Distinctive features of the proposed method from the prototype:

- form in-phase and quadrature components of the received signal, multiply the received signal to in-phase and quadrature components of the reference signal, and in prototype form in-phase and quadrature components of the selected narrowband signals rays,

- perform filtering in-phase and quadrature components of the received signal, and the prototype will filter the in-phase and quadrature digital components selected narrowband signals rays,

- produce analog-to-digital conversion of the filtered in-phase and quadrature components of the received signal, and produce prototype analog-to-digital conversion of in-phase and quadrature sostavlyajushie the selected narrowband signals rays,

for each found the beam forming signal detuning frequency of the signal beam relative to the frequency of the reference signal and the estimated power of the signal beam using a digital filtered inphase and quadrature components of the received signal and the real and imaginary part of the pseudo-random sequences of the pilot signal of the beam, as in the prototype signal detuning frequency of the signal beam relative to the frequency of the reference signal is formed using the filtered components of the selected narrowband signal beam,

- signal average detuning the frequency of the received multipath signal relative to the frequency of the reference signal is as follows:

summarize the estimates of the signal power of all rays,

for each beam form for assessing the strength of the signal beam to the sum of the estimates of the signal power of all rays,

for each beam Peremohy formed a relationship with the signal detuning frequency of the signal beam relative to the frequency of the reference signal,

form the average detuning the frequency of the received multipath signal relative to the reference signal, obtained by summing works on all rays,

and in prototype form, the average detuning the frequency of the received multipath signal, summing the signals of the detuning frequency of each beam Rel the relative frequency of the reference signal and filtering the obtained amount.

Comparative analysis of the proposed method of estimating the detuning of the frequency signals of the beams relative to the frequency of the reference signal with the prototype shows that the evaluation of the detuning frequency of the signal beam relative to the frequency of the reference signal is completely different and all operations of the method are different from the operations of the prototype. Assessment of the strength of the signal beam in the prototype is not generated.

Comparative analysis of the claimed device-locked loop frequency of the reference signal of the receiving station with the prototype shows that the proposed device is substantially different from the prototype.

Common features of the claimed device and prototype

Both devices contain common blocks: first and second multiplier products, Phaser, the pseudo-random sequence generator, the first and second analog-to-digital converters, the first and second filters, the N blocks of the evaluation of the detuning frequency of the signal beam, a first adder, N second adders, a voltage controlled oscillator.

In the prototype, and in the proposed device can identify the following General relations: first, the signal inputs of the first and second multiplier products are combined and input device, the first outputs of blocks evaluation of the detuning frequency of the signal beam are output signals of the detuning frequency signals rays relative to what astate reference signal and connected to the first inputs of the respective second adders, the outputs of the second adders are the outputs of the relative detuning of the frequency of the signal beam, and outputs of the device.

Distinguishing features of the claimed device from prototype

In the inventive device and the prototype of the procedure of processing of the received signal are different. The relationship between the common blocks in the inventive device in the prototype are also different. In addition, added new blocks: N multipliers, N divider, the third adder, the control block.

In addition, each assessment unit of the detuning frequency of the signal beam addition signal detuning generates a score for the strength of the signal beam. This assessment power of the signal beam used to form the weighting factor in obtaining the average detuning the frequency of the received multipath signal, while in the prototype, the average detuning the frequency of the received multipath signal are generated without the weights rays.

New relationships that are necessary for the operation of the device, following.

The second input of the first multiplier connected to the output of the quadrature component of the reference signal of the phase shifter, a second input of the second multiplier connected to the output of the in-phase component of the reference signal generator, voltage-controlled output reference signal generator, voltage-controlled, with whom United with the input of the phase shifter, the output of the first multiplier, which is the output of the quadrature component of the received signal through the first filter and the first analog-to-digital Converter connected to the second inputs of the N blocks of the evaluation of the detuning frequency of the signal beam, the output of the second multiplier, which is the output of the inphase component of the received signal through a second filter and a second analog-to-digital Converter connected to the third inputs of the N blocks of the evaluation of the detuning frequency of the signal beam, the first inputs units estimates of the detuning frequency of the signal beam are connected to the outputs of the pseudorandom sequence generator that generates real and imaginary part of the pseudo-random sequences of the pilot signal detected rays, the input of the pseudo-random sequence generator is a login Manager signal search results, fourth inputs units estimates of the detuning frequency of the signal beam is connected to the control outputs of the control unit, the input of which is the input set the operation mode, the first outputs of blocks evaluation of the detuning frequency of the signal beam, which are the output signals of the detuning frequency signals rays relative to the frequency of the reference signal, is connected to first inputs of respective multipliers, the second outputs of blocks evaluation of the detuning frequency signal is teaching, which are the outputs of the estimated power of the signal beams, connected with the first inputs of the respective dividers and to the corresponding inputs of the first adder, the output of the first adder being the output of the sum of the estimated power of the signal beams, connected to the second inputs of the dividers, the outputs of the dividers, which are the outputs of relationship cardinality estimation signal beam to the sum of the estimates of the signal power of all rays, are connected to second inputs of respective multipliers, the outputs of the multipliers are connected to the corresponding inputs of the third adder, the output of the third adder, the output of which is signal average detuning the frequency of the received multipath signal relative to the reference signal, is connected to the second inputs of the second adders and the generator input, voltage-controlled outputs of the second adders are the output signals of the relative detuning of the frequency of the signal beam, and outputs of the device.

A comparison of the proposed objects of the invention with the prototype and other well-known technical solutions in this field of technology is not allowed to reveal the totality of the claimed features, and therefore they provide the claimed technical solution according to the criteria of "novelty", "significant differences" and "inventive step".

Graphical is e materials used description:

Figure 1 - structural diagram of the device-locked loop frequency of the reference signal of the receiving station of the prototype.

Figure 2 - block diagram of the evaluation unit of the detuning frequency of the signal beam prototype.

Figure 3 Graphs the decisive function L(δ) at different values of the duration of the coherent accumulation So

4 is a Graph of the evaluation of the detuning frequencywhen L+=L-.

Fig 5 is a Graph of the evaluation of the detuning frequencywhen L->L+.

6 is a Graph of the evaluation of the detuning frequencywhen L+>L-.

7 is a structural diagram of the device is locked loop frequency of the reference signal to the receiving station.

Fig - variant execution control block.

Fig.9 is a variant of the structural scheme of assessment unit of the detuning frequency of the signal beam relative to the frequency of the reference signal of the device.

The proposed method of automatic frequency reference signal of the receiving station includes the following sequence of operations:

- Peremohy the received signal to in-phase and quadrature components of the reference signal, forming in-phase and quadrature components of the received signal,

- implemented Aut filtering in-phase and quadrature components of the received signal,

- produce analog-to-digital conversion of the filtered in-phase and quadrature components of the received signal,

- form the real and imaginary part of the pseudo-random sequences pilot signal, a temporary position which corresponds to the delay signals of the detected rays,

for each found the beam forming signal detuning frequency of the signal beam relative to the frequency of the reference signal and the estimated power of the signal beam using a digital filtered inphase and quadrature components of the received signal and the real and imaginary part of the pseudo-random sequences of the pilot signal of the beam,

- form the signal average detuning the frequency of the received multipath signal relative to the frequency of the reference signal, which

summarize the estimates of the signal power of all rays,

for each beam form for assessing the strength of the signal beam to the sum of the estimates of the signal power of all rays,

for each beam Peremohy formed a relationship with the signal detuning frequency of the signal beam relative to the frequency of the reference signal,

form the average detuning the frequency of the received multipath signal relative to the reference signal, obtained by summing works on all rays,

- adjust the frequency of the reference signal cf the days of the detuning of the frequency of the received multipath signal relative to the reference signal,

- form relative detuning frequency of the signal for each beam, subtracting from the signal detuning frequency of the beam relative to the frequency of the reference signal average detuning the frequency of the received multipath signal relative to the reference signal.

As evaluationthe detuning of the carrier frequency signal ωsregarding the frequency of the reference signal of the receiving station accepts an argument of the maximum crucial functions L(δ)that is monotonically related to the functionality of the likelihood ratio.

The proposed method PLL frequency reference signal receiving station corresponds to the following formal mathematical model.

The expression of crucial functions L(δ) for each component of an input beam signal has the form

Each component of the k-th time interval of stationarity duration T in (9) can be represented as

where

x(t)=s(t)+n(t) is an implementation of the input signal, s(t) is the useful signal, n(t) is additive Gaussian noise, tk+1=tk+T, k=0,...,K-2, K - number of non-coherent accumulations, ωs- frequency pilot signal, δ=ω-ωs- detuning frequency, ω - the frequency of the reference C is Nala, Ik(t), Qk(t) - known orthogonal pseudorandom code sequence (SRP) the pilot channel of the k-th time interval of stationarity.

For the evaluation of the detuning frequency of the input signal relative to the frequency of the reference signal isthe decisive argument of the function L(S)at which it reaches its maximum, that is,

The calculation of L(δ) includes coherent accumulation interval T (11), (12) and the procedure additional non-coherent accumulation To intervals of duration T (9).

The duration of the coherent accumulation of T is chosen so that the area of uncertainty values of the detuning frequency of the input signal was within the main lobe deterministic component of the crucial functions L(δ).

The deterministic component of the crucial functions L(δ) reaches its maximum when the ω=ωsand decreases within the main lobe with increasing values of detuning

The width of the main lobe of the crucial functions L(δ) is inversely proportional to the duration of the coherent accumulation of T and is related to the width W of the interval of uncertainty frequency as follows

To find the argument of the maximum crucial functions L(δ) (13) this method will use a simple and effective procedure for the calculation results of the values L(δ) at two points δ=δg-Δω and δ=δg+Δω within the main lobe. Assessment of the current detuning is defined by the expression

where

δg- preceding value of the detuning frequency ωgthe reference signal relative to the input signal frequency ωsof the interval of uncertainty W.

The case L+=L-corresponds to the situation when the argumentthe maximum decisive function L(δ) coincides with δg(figure 4). From expression (16) it follows thatSetting the frequency of the reference signal is believed to be accurate,and ωgs.

When L+≠L-- evaluation of the detuning of the carrier frequencydifferent from zero (see figure 5, 6). As can be seen from (16), module sizeincreases the difference between the L+-L-.

From (16), (17) it follows that assessment belongs to the interval

Thus, excluded the blunder of assessment that makes the proposed algorithm stability.

Thus, for the current assessment of the detuning of the carrier frequency the proposed method uses the evaluation values of the crucial functions (9) in two points L+and L-within the main lobe.

To determineuse the expression (16), which fills in the values of L+and L-. For each subsequent measurement of the detuning frequency asuse the value from the previous evaluation

The current estimation of the frequency of the input signalis determined from the expression

where- is the current estimate of the detuning frequency and ωgthe frequency of the reference signal of the previous step correction.

Feature of the proposed method of assessment is the fast convergence to the exact value of the carrier frequency signal, and the stability of the algorithm at low relationship power signal and noise.

In terms of resolvable multipath suggested to adjust the reference frequency according to shift h is the frequency of each multipath component with regard to energy ratios between the rays.

Let L-(n), L+(n) and- correspond to the values of L-, L+andobtained for the n-th beam (n=1,...,N, N≥2) according to the expressions (17) and (19). Then the resulting estimate of the detuning frequencyis using a weighted sum of the estimates of the shift frequency signals rays with corresponding weight factors andnbased on the relative energy contribution of each beam:

where

The sum (20) allows to take into account neravnoznachnost evaluation results of the detuning frequency for different rays. More reliable are the estimates for the signals of beams with large capacity.

Thus, evaluation of the detuning frequency of the input beam signal is formed by using a linear combination of (20) estimates of the frequency shift obtained independently for each multipath components of the expressions(16)-(19).

The current estimate of the frequency of i-th componentinput multipath signal is determined from the expression

where- is the current estimate of the detuning frequency of i-th component and ωgthe frequency of the reference signal of the previous step correction.

Terms of the procedure of automatic frequency reference signal of the mobile station for the various areas of uncertainty W are taken into account by the choice of the parameters N, It ±Δω. For example, in the first phase-locked loop frequency duration of the coherent accumulation selects the minimum, ensuring maximum interval of uncertainty, and the number of non-coherent accumulations selects the maximum. At subsequent stages, the duration of the coherent accumulation is increased, and the number of non-coherent accumulation is reduced. The interval of uncertainty is reduced, and the accuracy of determining the detuning is gradually increased.

To implement the proposed method of automatic frequency reference signal of the mobile station, the proposed device is based on the maximum likelihood method.

Structural diagram of the device is presented on Fig.7. The device includes first and second multiplier products 1-1, 1-2, Phaser 2, the pseudo-random sequence generator (gpsa) 3, the first and second analog-to-digital converters (ADC) 5, 8, the first and second filters 6, 9, N blocks of the evaluation of the detuning frequency of the signal beam 10-1-10-N, the first adder 11, N second adders 12-1-12-N, a voltage controlled oscillator (VCO) 13, N multipliers 21-1-21-N, N dividers 22-1-22-N, the third adder 23, the control unit 24.

The first signal inputs of the first and second multiplier products 1-1-1-2 are combined and input devices. The second input of the first paramnesia what I 1-1 is connected to the output of the quadrature component of the reference signal of the phase shifter 2, and the second input of the second multiplier 1-2 connected to the output of the in-phase component of the reference signal VCO 13. The output of reference signal generator, voltage-controlled 13, is connected also to the input of the phase shifter 2. The output of the first multiplier 1-1 corresponding to the quadrature component of the received signal through the first filter 6 and the first analog-to-digital Converter 5 is connected to the second inputs of the N blocks of the evaluation of the detuning frequency of the signal beam 10-1-10-n the output of the second multiplier 1-2, the corresponding in-phase component of the received signal through the second filter 9 and the second analog-to-digital Converter 8 is connected to third inputs of the N blocks of the evaluation of the detuning frequency of the signal beam 10-1-10-n First inputs units estimates of the detuning frequency of the signal beam 10-1-10-N are connected to the outputs of the gpsa 3, forming the real and imaginary part of the pseudo-random sequences pilot signal beams, input gpsa 3 receives the control signal of the search results. On the fourth inputs units estimates of the detuning frequency of the signal beam 10-1-10-N receives control signals from the output of the control unit 24, to which input signal setup mode. The first outputs of blocks evaluation of the detuning frequency of the signal beam 10-1-10-N are output signals of the detuning frequency signals rays relative to the frequency of the reference C is Nala and connected with the first inputs of respective multipliers 21-1-21-N and with the first inputs of the respective second adders 12-1-12-n The second outputs of blocks evaluation of the detuning frequency of the signal beam 10-1-10-N, the corresponding estimate of the power of the signal beams, connected to respective inputs of the first adder 11 and the first inputs of the respective dividers 22-1-22-n the output of the first adder 11, corresponding to the sum of the estimates of the signal power of all rays, is connected to the second inputs of the dividers 22-1-22-n Outputs of the dividers 22-1-22-N are connected to second inputs of respective multipliers 21-1-21-n signal at the output of each divider 22-1-22-N corresponds to the ratio of the cardinality estimation of the signal beam to the sum of the estimates of the signal power of all rays. The outputs of multipliers 21-1-21-N are connected to corresponding inputs of the third adder 23, the output signal which is a signal of the average detuning the frequency of the received multipath signal relative to the reference signal. The output of the third adder 23 is connected to the second inputs of the second adders 12-1-12-N and the input of the VCO 13. The signals at the outputs of adders 12-1-12-N are signals relative detuning of the frequency of the signal beam, and outputs of the device.

The proposed device automatic frequency reference signal of the receiving station as follows.

It is assumed that you have already performed a search signal rays in the range multipath and obtained estimates of their times, the CSO position. These estimates are used as the control signal search results for setup time delays in the gpsa 3 during the formation of copies detected signals rays. Input wideband multipath signal is supplied to the first signal, the inputs of the multiplier products 1-1 and 1-2. To the second input of the first multiplier 1-1 from the output of the phase shifter 2 receives the quadrature component of the reference signal and the second input of the second multiplier 1-2 output from the VCO 13 is fed in-phase component of the reference signal. Phaser 2 provides a phase shift of the signal π/2. In the result of multiplying the received signal into in-phase and quadrature components of the reference signal at the outputs of multiplier products 1-1 and 1-2 respectively form the quadrature and in-phase components of the received signal. In the first 6 and second 9 filters will filter accordingly and quadrature-phase components of the received signal. Filtered quadrature and in-phase components of the received signal are received respectively in the first ADC 5 and the second ADC 8 where it is analog-to-digital conversion. The obtained digital signals are respectively second and third inputs units estimates of the detuning frequency of the signal beam 10-1-10-n first inputs units estimates of the detuning frequency of the signal l is cha 10-1-10-N output gpsa 3 receives signals of the real and imaginary parts of the SRP pilot signal, temporary position which corresponds to the delay signals of the detected radiation. On the fourth inputs units estimates of the detuning frequency of the signal beam 10-1-10-N from the output of the control unit 24 receives control signals mode of operation.

In accordance with the control signals mode of operation in each assessment unit of the detuning frequency of the signal beam 10-1-10-N set the duration of the coherent and non-coherent accumulations, as well as the frequency of the additional reference signal. The signal detuning frequency signal corresponding to the beam relative to the frequency of the reference signal and the estimated power of the signal beam is formed using a digital filtered inphase and quadrature components of the received signal and the signals of the real and imaginary parts of the SRP pilot signal detected rays. The signal detuning frequency signal of each beam relative to the frequency of the reference signal is supplied to first inputs of respective multipliers 21-1-21-N and to the first inputs of the respective second adders 12-1-12-n

Using estimates of the signal power of the rays, find the relative contribution of each component of the input beam signal. To do this in the first adder 11 summarize the estimates of the signal power of all rays and the corresponding divider 22-1-22-N for each beam form for assessing the strength of the signal beam to the sum of ozena is the signal power of all rays. In the multipliers 21-1-21-N for each beam Peremohy formed relationships cardinality estimation signal beam to the sum of the estimates of the signal power of all rays with the corresponding signal detuning frequency of the signal beam relative to the frequency of the reference signal. Summing the received works on all rays in the third adder 23, at its output form the average detuning the frequency of the received multipath signal relative to the reference signal. On average detuning the frequency of the received multipath signal relative to the reference signal to adjust the frequency of the reference signal VCO 13 and the outputs of the second adders 12-1-12-N-average detuning and the signal detuning frequency signal corresponding to the beam relative to the frequency of the reference signal to generate the relative pitch difference of the signal frequency of the beam.

The signals at the outputs of adders 12-1-12-N are output signals of the device.

Embodiment of the control unit 24 presents on Fig.

The control unit 24 contains a node select the number of coherent accumulations 25, site selection the number of non-coherent accumulations 26, the counter 27, the clock pulses (GTI) 28 and a persistent storage device (ROM) 29.

Memory ROM 29 is divided into subregions, which addresses listed sets of control parameters: the number of coherent accumulations N, Chi is La non-coherent accumulations To, the additional frequency reference signal Δω. The input control signal of the control unit 24 sets the value of a priori uncertainty ranges of the frequency detuning W and polechova-noise (signal-to-noise ratio in the channel). It is known that the width of the main lobe of the crucial functions L(δ) is inversely proportional to the number of coherent accumulations N.

Therefore, site selection the number of coherent accumulations 25 largest W determine the value of N and the frequency of the additional reference signal Δω. Then according to the value of N and the signal-to-noise ratio at node 26 exercise choice in the number of non-coherent accumulations. Based on the options selected in block 26 form the division ratio of which is fed to the counter 27. This division factor determines the output value of the counter 27, which corresponds to the address of the sub memory ROM 29 in which is placed a selected set of control parameters N, K, Δω. In the next step clock output GTI 28 output value of the counter 27 is changed and corresponds to the memory address of the ROM 29 new set of control parameters N, K, Δω.

In the control unit 24 can be used a standard counter with a variable division ratio, as described, for example, in the book "Digital radio systems". Ed. by M. Iljitsch. M: RA is IO and communication. 1990, p.45.

An example implementation of the ROM 29 is shown in RIS, p.55 in the book "Digital radio systems". Edited Mieczyslawa. M.: Radio and communication. 1990.

Nodes select the number of coherent accumulations 25 and select the number of non-coherent accumulations 26 can be implemented on the basis of the standard ROM (as in the previous paragraph) or a specialized microprocessor.

Evaluation of the detuning of the frequency signals of the beams relative to the frequency of the reference signal in the proposed method is as follows:

- form the real and imaginary components of the in-phase component of the additional reference signal, computing the product of samples of the real and imaginary parts of the pseudorandom sequence, the delay corresponds to the delay of the signal of the beam on the samples in-phase component of the additional reference signal,

- form the real and imaginary components of the quadrature component of the additional reference signal, computing the product of samples of the real and imaginary parts of the pseudorandom sequence, the delay corresponds to the delay of the signal of the beam on the samples of the quadrature component of the additional reference signal,

form a first sum and the first differential reference signals, calculating the sum and the difference the school who enoy components in-phase component of the additional reference signal and the imaginary components of the quadrature component of the additional reference signal,

- form the second sum and second differential reference signals, calculating the sum and the difference of the imaginary components of the in-phase component of the additional reference signal and the actual components of the quadrature component of the additional reference signal,

- create initial total in-phase and quadrature components, calculating the product of samples of the first total reference signal, respectively, at the timing phase and quadrature filtered digital in-phase and quadrature components of the received signal,

form a first differential in-phase and quadrature components, calculating the product of samples of the first differential reference signal, respectively, at the timing phase and quadrature filtered digital in-phase and quadrature components of the received signal,

form a second total in-phase and quadrature components, calculating the product of samples of the second total reference signal, respectively, at the timing phase and quadrature filtered digital in-phase and quadrature components of the received signal,

form a second differential in-phase and quadrature components, calculating the product of samples of the second differential reference signal, respectively, at the timing phase and quadrature filter, avannah digital in-phase and quadrature components of the received signal,

- form an in-phase component corresponding to the increased frequency of the reference signal, summing the counts first overall in-phase component and the timing of the second differential quadrature component,

- form a quadrature component corresponding to the increased frequency of the reference signal by subtracting from the reading first total quadrature component samples of the second differential in-phase component,

- form an in-phase component corresponding to a reduced frequency of the reference signal, summing the counts of the first differential in-phase component and the second counts the total quadrature component,

- form a quadrature component, the corresponding reduced frequency of the reference signal by subtracting from the second counts the total in-phase component samples of the first differential quadrature component,

- accumulate N samples in-phase components corresponding to the increased frequency of the reference signal by N samples of the quadrature components corresponding to the increased frequency of the reference signal by N samples in-phase components corresponding to the reduced frequency of the reference signal by N samples of the quadrature components corresponding to the reduced frequency of the reference signal, where N is the number of coherent accumulations,

- calculate the squares of the results of the NAC is the intervention phase and quadrature component, the corresponding enlarged and reduced the frequency of the reference signal,

- form the coherent accumulation corresponding to the increased frequency of the reference signal, summing the squares of the results of the accumulation phase and quadrature components corresponding to the increased frequency of the reference signal,

- form the coherent accumulation corresponding to the reduced frequency of the reference signal, summing the squares of the results of the accumulation phase and quadrature components corresponding to the reduced frequency of the reference signal,

- form the estimate of the power of the signal beam corresponding to the increased frequency of the reference signal, accumulating the results of the coherent accumulation corresponding to the increased frequency of the reference signal, where K is the number of non-coherent accumulations,

- form the estimate of the power of the signal beam corresponding to a reduced frequency of the reference signal, accumulating the results of the coherent accumulation corresponding to the reduced frequency of the reference signal,

- find the estimate of the power of the signal beam, determining the maximum value of the evaluation signal power of the beam corresponding to the increased frequency of the reference signal, and estimates the signal power of the beam corresponding to the reduced frequency of the reference signal,

- form the ratio of the difference between the estimate m is snasti signal beam, the corresponding increased the frequency of the reference signal, and estimates the signal power of the beam corresponding to the reduced frequency of the reference signal, and estimating the signal power of the beam,

- form the signal detuning frequency of the signal beam relative to the reference signal, multiply formed a relationship with the frequency of the additional reference signal.

To implement the proposed method of assessment of the detuning frequency of the signal beam relative to the frequency of the reference signal can be used to block the General block diagram is shown in Fig.9. The evaluation unit of the detuning frequency of the signal beam 10 includes a phase shifter 30, the generator 31, the first and second multiplier products 32 and 33, the third and fourth multiplier products 34 and 35, the first and second adders 36 and 37, the third and fourth adders 38 and 39, fifth, sixth, seventh and eighth multiplier products 40, 41, 42, 43, ninth, tenth, eleventh and twelfth multiplier products 44, 45, 46, 47, fifth and sixth adders 48 and 49, seventh and eighth adders 50 and 51, the first and second Quad and 52 53, the third and fourth Quad 54, 55, ninth adder 56, the comparator 57, the tenth adder 58, the thirteenth multiplier 59, the divider 60, the eleventh adder 61.

The first inputs of the first and second multiplier products 32, 33 and the input of the phase shifter 30 is connected to the output of the generator 31, the signal of which is sin is aznoe additional component of the reference signal. The input of the generator 31 and the input of the thirteenth multiplier 59 are the inputs of the additional frequency reference signal and connected to the output of the control unit 24. The first inputs of the third and fourth multiplier products 34, 35 connected to the output of the phase shifter 30, the output of which is the quadrature component of the additional reference signal. The second inputs of the first multiplier 32 and the third multiplier 34 are used as inputs of the real part of a pseudo-random sequence signal beam and connected to the output of the gpsa 3. The second inputs of the second multiplier 33 and the fourth multiplier 35 are input imaginary part of the pseudo-random sequence signal beam and connected to the output of the gpsa 3. The second inputs of the multiplier products 32, 33, 34, 35 are first input unit 10.

The output of the first multiplier 32, which is the output signal of the valid components in-phase component of the additional reference signal, connected to the first input of the first adder 36 and to the first input of the third adder 38.

The output of the second multiplier 33, which is the output signal of the imaginary components of the in-phase component of the additional reference signal, is connected to the first input of the second adder 37 and to the first input of the fourth adder 39.

The output of the third multiplier 34, which is the output is ignal valid components of the quadrature component of the additional reference signal, connected to the second input of the second adder 37 and a second input of the fourth adder 39.

The output of the fourth multiplier 35, which is the output signal of the imaginary components of the quadrature component of the additional reference signal, is connected to a second input of the first adder 36 and a second input of the third adder 38.

The total output of the first reference signal of the first adder 36 is connected respectively to the first inputs of the fifth and seventh multiplier products 40 and 42.

The output of the second differential reference signal of the second adder 37 is connected respectively to the first inputs of the sixth and eighth multiplier products 41 and 43.

The output of the first differential reference signal of the third adder 38 is connected respectively to the first inputs of the ninth and twelfth multiplier products 44 and 47.

The output of the second total reference signal of the fourth adder 39 is connected respectively to the first inputs of the tenth and eleventh multiplier products 45 and 46.

The second inputs of the multiplier products 40, 43, 44, 46 are input counts digital filtered in-phase component of the received signal and a third input unit 10.

The second inputs of the multiplier products 41, 42, 45, 47 are input samples filtered quadrature digital component of the received signal and the second input unit 10

The third input of the fifth and sixth adders 48, 49 and third inputs of the seventh and eighth adders 50, 51 are used as inputs number of coherent accumulations and is connected to the output of the control unit 24.

The output of the fifth multiplier 40. which is the output of the first total in-phase component, connected to the first input of the fifth adder 48.

The output of the sixth multiplier 41, which is the output of the second differential quadrature component, is connected to a second input of the fifth adder 48. The output of the fifth adder 48, which is the output common-mode components with increased frequency of the reference signal, is connected to the input of the first Quad 52.

The output of the seventh multiplier 42, which output first overall in-phase component, connected to the first input of the sixth adder 49.

The output of the eighth multiplier 43, which is the output of the second differential quadrature component, is connected to a second input of the sixth adder 49. The output of the sixth adder 49, which is the output of the quadrature components with increased frequency of the reference signal, is connected to the input of the second Quad 53.

The output of the ninth multiplier 44, which is the output of the first differential in-phase component, connected to the first input of the seventh adder 50.

The output of the tenth multiplier 45, which is the output of the second total quadrature component, connected to the second the entrance of the seventh adder 50. The seventh output of the adder 50, which is the output common-mode components with a reduced frequency of the reference signal, is connected to the input of the third Quad 54.

The output of the eleventh multiplier 46, which is the output of the second total in-phase component, connected to the first input of the eighth adder 51.

The output of the twelfth multiplier 47, which is the output of the first differential quadrature component, is connected to a second input of the eighth adder 51. The output of the eighth adder 51, which is the output of the quadrature components with a reduced frequency of the reference signal, is connected to the input of the fourth Quad 55.

The outputs of the first and second Quad 52, 53, which are respectively the outputs of the squares of the inphase and quadrature components with increased frequency of the reference signal, are connected respectively with the first and the second input of the ninth adder 56. The outputs of the third and fourth Quad 54, 55, which are respectively the outputs of the squares of the inphase and quadrature components with a reduced frequency of the reference signal, are connected respectively with the first and the second input of the tenth adder 58. The third inputs of the ninth adder 56 and the tenth adder 58, which are used as inputs in the number of non-coherent accumulations and is connected to the output of the control unit 24. The input of the generator 31, the first input per the multiplier 59, the third inputs of the adders 48, 49, 50, 51, and third inputs of the adders 56 and 58 are the fourth input unit 10.

The output of the ninth adder 56, which is the output cardinality estimation signal beam with an increased frequency of the reference signal, connected to the first input of the comparator 57 and to the first input of the eleventh adder 61. The output of the tenth adder 58, which is the output cardinality estimation signal beam with a reduced frequency of the reference signal, is connected to a second input of the comparator 57 and the second input of the eleventh adder 61. The output of the comparator 57, which is the output cardinality estimation signal beam, connected to the first input of the divider 60 and the second output unit 10. The output of the eleventh adder 61 is connected to the second input of the divider 60, the output of which is connected to a second input of the thirteenth multiplier 59. The output of the thirteenth multiplier 59 is the output signal of the detuning of the frequency of the signal beam relative to the reference signal and the first output unit 10.

Does the evaluation unit of the detuning frequency of the signal beam with respect to the frequency reference signal as follows.

To simplify the description of the General block diagram of the block 10 is conveniently divided into the following groups of nodes that are functionally independent.

The group of nodes forming a common source signal is a phase shifter 30, generate the R 31, first and second multiplier products 32, 33, third and fourth multiplier products 34, 35.

The group of nodes that form the estimate of the power of the signal beam corresponding to the increased frequency of the reference signal is the first and the second adders 36, 37, fifth, sixth, seventh and eighth multiplier products, 40, 41, 42, 43, fifth and sixth adders 48, 49, the first and second Quad 52, 53 and ninth adder 56.

The group of nodes that form the estimate of the power of the signal beam corresponding to the reduced frequency of the reference signal is the third and fourth adders 38, 39, ninth, tenth, eleventh and twelfth multiplier products 44, 45, 46, 47, seventh and eighth adders 50, 51, third and fourth Quad 54, 55 and tenth adder 58.

The group of nodes that form a common output signal is a comparator 57, the thirteenth multiplier 59, the divider 60 and the eleventh adder 61.

The parameters of the unit 10 is installed in accordance with control signals: frequency of additional reference signal Δω, number of coherent accumulations of N and the number of non-coherent accumulations To that form at the output of the control unit 24.

Consider a group of nodes forming a common source signals. The control signal is the frequency of the additional reference signal Δω at the output of the generator 31 is formed samples the in-phase component of the additional reference signal, and the and output of the phase shifter 30 to form the samples of the quadrature component of the additional reference signal. The samples in-phase component of the additional reference signal received at the first inputs of the first and second multiplier products 32, 33. Samples of the quadrature component of the additional reference signal received at the first inputs of the third and fourth multiplier products 34, 35. On the second inputs of the first multiplier 32 and the second input of the third multiplier 34 receives samples of the real part of the pseudorandom sequence signal beam. On the second inputs of the second multiplier 33 and the second input of the fourth multiplier 35 receives samples of the imaginary part of the pseudo-random sequence signal beam. The result of multiplication of the samples at the outputs of the first and second multiplier products 32 and 33 are formed, respectively, the real and imaginary components of the in-phase component of the additional reference signal, and outputs the third and fourth multiplier products 34 and 35 are formed respectively the real and imaginary components of the quadrature component of the additional reference signal. The generated signals are shared with the original signals, which are used to form the estimated power of the signal beam corresponding to the enlarged and reduced the frequency of the reference signal.

The outputs of the first adder 36 and the third adder 38 form respectively the first total and per the first differential reference signals, by summing and subtracting the actual components in-phase component of the additional reference signal and the imaginary components of the quadrature component of the additional reference signal.

The outputs of the fourth adder 39 and the second adder 37 form respectively the second sum and second differential reference signal by summing and subtracting imaginary components of the in-phase component of the additional reference signal and the actual components of the quadrature component of the additional reference signal.

The outputs of the fifth and seventh multiplier products 40, 42 form respectively the first, the total in-phase and quadrature components by multiplying samples of the first total reference signal respectively to the samples of the filtered digital in-phase and quadrature components of the received signal.

The outputs of the sixth and eighth multiplier products 41 and 43 respectively form the second differential quadrature and in-phase components by multiplying samples of the second differential reference signal, respectively, for the samples of the filtered digital quadrature and in-phase components of the received signal.

The outputs of the ninth and twelfth multiplier products 44, 47 respectively form the first differential cinfa the ing and quadrature components, multiply the samples of the first differential reference signal, respectively, for the samples of the filtered digital in-phase and quadrature component of the received signal.

The outputs of the tenth and eleventh multiplier products 45, 46 respectively form the second total quadrature and in-phase components, multiply the samples of the second total reference signal respectively to the samples of the filtered digital quadrature and in-phase component of the received signal.

Adders 48, 49, 50, 51, 56, 58 realize the function of the accumulation of amounts received on their first and second input samples. The number of savings is determined by the control signal to the third inputs of these adders.

In the fifth adder 48 form an in-phase component corresponding to the increased frequency of the additional reference signal, summing the counts first overall in-phase component and the timing of the second differential quadrature component and accumulating N sums, where the number of coherent accumulation of N is determined by the signal control unit 24.

In the sixth adder 49 form a quadrature component corresponding to the increased frequency of the additional reference signal by subtracting from the reading first total quadrature component samples of the second differential in-phase component and accumulating N differences.

All mom the adder 50 is formed in-phase component, the corresponding reduced frequency additional reference signal, summing the counts of the first differential in-phase component and the second counts the total quadrature component and accumulating N amounts.

In the eighth adder 51 form a quadrature component, the corresponding reduced frequency additional reference signal by subtracting from the second counts the total in-phase component samples of the first differential quadrature component and accumulating N differences.

In the first and second Quad 52 and 53 calculates the squares of the results of the accumulations in the fifth and sixth adders 48 and 49 in-phase and quadrature components corresponding to the increased frequency of the additional reference signal.

In the third and fourth Quad 54 and 55 calculates the squares of the results of the savings in the seventh and eighth adders 50 and 51 in-phase and quadrature components corresponding to the reduced frequency of the additional reference signal.

The output of the ninth adder 56 form the estimate of the power of the signal beam corresponding to the increased frequency of the additional reference signal, summing the squares of the results of the accumulation phase and quadrature components corresponding to the increased frequency of the additional reference signal, and accumulating the sum, where is determined by the output signal of the control unit is to be placed 24.

The output of the tenth adder 58 form the estimate of the power of the signal beam corresponding to the reduced frequency of the additional reference signal, summing the squares of the results of the accumulation phase and quadrature components corresponding to the reduced frequency of the additional reference signal, and accumulating the amounts.

In the comparator 57 are estimating the signal power of the beam, determining the maximum value from the estimated power of the signal beam corresponding to the enlarged and reduced the frequency of the additional reference signal.

The output of the eleventh adder 61 to form the difference between the estimate of the signal power of the beam corresponding to the increased frequency of the additional reference signal, and estimates the signal power of the beam, the corresponding reduced frequency additional reference signal. The divider 60 is formed with respect to the difference obtained in the eleventh adder 61, to assess the strength of the signal beam from the output of the comparator 57.

The output of the thirteenth multiplier 59 form the signal detuning frequency of the signal beam relative to the reference signal, multiply formed in the divider 60 ratio with the magnitude of the additional frequency reference signal Δω.

It should be noted that successive cyclic procedure of assessment of detuning and its compensation uses the original Sal is the rhythm of determining the maximum crucial functions for two values of the uncertainty ranges of frequency, that allows to reduce the time of compensation of the frequency detuning. Unlike the prototype, the proposed procedure has a higher noise immunity, because it uses additional digital reference signal. The proposed algorithm can function at different, including significant, the initial values of the frequency detuning. It is effective both in the initial phase (mode) seizure frequency), and the subsequent action.

Presents solution-locked loop combines the ability to fine tune the frequency at moderate cost for its implementation. The proposed embodiment of the automatic frequency control allows fine tuning of the reference oscillator frequency, even at very low signal-to-noise ratio for the received signal.

1. Method-locked loop frequency of the reference signal receiving station, namely, that Peremohy the received signal to in-phase and quadrature components of the reference signal, forming in-phase and quadrature components of the received signal, will filter the in-phase and quadrature components of the received signal, producing an analog-to-digital conversion of the filtered in-phase and quadrature components of the received signal form the real and imaginary part of the pseudo-random the sequence of the pilot signal, temporary position which corresponds to the delay signals of the detected beams, each beam found form the signal detuning frequency of the signal beam relative to the frequency of the reference signal and the estimated power of the signal beam using a digital filtered inphase and quadrature components of the received signal and the real and imaginary part of the pseudo-random sequences of the pilot signal of the beam form the signal average detuning the frequency of the received multipath signal relative to the frequency of the reference signal, which summarize the estimates of the signal power of all rays, for each beam form for assessing the strength of the signal beam to the sum of the power ratings of all signals of beams, each beam Peremohy formed a relationship with the signal detuning frequency signal beam relative to the frequency of the reference signal, form the average detuning the frequency of the received multipath signal relative to the reference signal, obtained by summing works on all rays, adjust the frequency of the reference signal at the average detuning the frequency of the received multipath signal relative to the reference signal for each beam of the average detuning the frequency of the received multipath signal relative to the reference signal and the signal detuning frequency of this beam is otnositelno the frequency of the reference signal to generate the relative pitch difference of the signal frequency of the beam.

2. The way of estimating the detuning of the frequency signals of the beams relative to the frequency of the reference signal, namely, that form the real and imaginary components of the in-phase component of the additional reference signal, computing the product of samples of the real and imaginary parts of the pseudorandom sequence, the delay corresponds to the delay of the signal of the beam on the samples in-phase component of the additional reference signal, form the real and imaginary components of the quadrature component of the additional reference signal, computing the product of samples of the real and imaginary parts of the pseudorandom sequence, the delay corresponds to the delay of the signal of the beam on the samples of the quadrature component of the additional reference signal, generate the first sum and the first differential reference signals, calculating the sum and the difference of valid components in-phase component of the additional reference signal and the imaginary components of the quadrature component of the additional reference signal, generate a second sum and a second differential reference signals, calculating the sum and the difference of the imaginary components of the in-phase component of the additional reference signal and the actual components of the quadrature component of the additional supports the wow signal, form a first total in-phase and quadrature components, calculating the product of samples of the first total reference signal, respectively, at the timing phase and quadrature filtered digital in-phase and quadrature components of the received signal, generate the first differential in-phase and quadrature components, calculating the product of samples of the first differential reference signal, respectively, at the timing phase and quadrature filtered digital in-phase and quadrature components of the received signal form the second total in-phase and quadrature components, calculating the product of samples of the second total reference signal, respectively, at the timing phase and quadrature filtered digital in-phase and quadrature components of the received signal form the second differential in-phase and quadrature components, computing works samples of the second differential reference signal, respectively, at the timing phase and quadrature filtered digital in-phase and quadrature components of the received signal form the in-phase component corresponding to the increased frequency of the reference signal, summing the counts first overall in-phase component and the timing of the second differential quadrature component, f is rerout quadrature component, the corresponding increased the frequency of the reference signal by subtracting from the reading first total quadrature component samples of the second differential in-phase component, form the in-phase component corresponding to a reduced frequency of the reference signal, summing the counts of the first differential in-phase component and the second counts the total quadrature component, form a quadrature component, the corresponding reduced frequency of the reference signal by subtracting from the second counts the total in-phase component samples of the first differential quadrature component, accumulate N samples in-phase components corresponding to the increased frequency of the reference signal by N samples of the quadrature components corresponding to the increased frequency of the reference signal by N samples in-phase components corresponding to the reduced frequency of the reference signal of N samples of the quadrature components corresponding to the reduced frequency of the reference signal, where N is the number of coherent accumulations, compute the squares of the results of the accumulation phase and quadrature components corresponding to the enlarged and reduced the frequency of the reference signal, to form the coherent accumulation corresponding to the increased frequency of the reference signal, summing the squares of the results of the accumulation phase quadrature component, the corresponding increased the frequency of the reference signal, to form the coherent accumulation corresponding to the reduced frequency of the reference signal, summing the squares of the results of the accumulation phase and quadrature components corresponding to the reduced frequency of the reference signal to form an estimate of the power of the signal beam corresponding to the increased frequency of the reference signal, accumulating the results of the coherent accumulation corresponding to the increased frequency of the reference signal, where K is the number of non-coherent accumulations, form the estimate of the power of the signal beam corresponding to a reduced frequency of the reference signal, accumulating the results of the coherent accumulation corresponding to the reduced frequency of the reference signal, find the estimate of the power of the signal beam, determining the maximum value of the evaluation signal power beam corresponding to the increased frequency of the reference signal, and estimates the signal power of the beam corresponding to the reduced frequency of the reference signal, form the ratio between the cardinality estimation of a signal beam corresponding to the increased frequency of the reference signal, and estimates the signal power of the beam corresponding to the reduced frequency of the reference signal, and estimating the signal power of the beam formed signal detuning frequency of the signal beam relative to the reference signal, the AC is able formed a relationship with the frequency of the additional reference signal.

3. Device-locked loop frequency of the reference signal receiving station, containing the first and second multiplier products, Phaser, the pseudo-random sequence generator, the first and second analog-to-digital converters, the first and second filters, the N blocks of the evaluation of the detuning frequency of the signal beam, a first adder, N second adders, a voltage controlled oscillator, and the first signal, the inputs of the first and second multiplier products are combined and input device, the first outputs of blocks evaluation of the detuning frequency of the signal beam are output signals of the detuning frequency signals rays relative to the frequency of the reference signal and connected to the first inputs of the respective second adders, the outputs of the adders are the outputs of the relative detuning of the frequency of the signal beam, and outputs, wherein the inputs of the N multipliers, N divider, the third adder, the control unit, the second input of the first multiplier connected to the output of the quadrature component of the reference signal of the phase shifter, a second input of the second multiplier connected to the output of the in-phase component of the reference signal generator, voltage-controlled output reference signal generator, voltage controlled, is connected also to the input futuredate what I the output of the first multiplier, which is the output of the quadrature component of the received signal through the first filter and the first analog-to-digital Converter connected to the second inputs of the N blocks of the evaluation of the detuning frequency of the signal beam, the output of the second multiplier, which is the output of the inphase component of the received signal through a second filter and a second analog-to-digital Converter connected to the third inputs of the N blocks of the evaluation of the detuning frequency of the signal beam, the first inputs units estimates of the detuning frequency of the signal beam are connected to the outputs of the pseudorandom sequence generator that generates real and imaginary part of the pseudo-random sequences pilot signal beams, the input of the pseudo-random sequence generator is the input control signal search results fourth inputs units estimates of the detuning frequency of the signal beam is connected to the control outputs of the control unit, the input of which is the input set the operation mode, the first outputs of blocks evaluation of the detuning frequency of the signal beam, which are the output signals of the detuning frequency signals rays relative to the frequency of the reference signal is connected to first inputs of respective multipliers, the second outputs of blocks evaluation of the detuning frequency of the signal beam, kotoryaaya outputs estimates of the signal power of the rays, connected with the first inputs of the respective dividers and to the corresponding inputs of the first adder, the output of the first adder being the output of the sum of the estimates of the signal power of all rays, is connected with the second inputs of the dividers, the outputs of the dividers, which are the outputs of relationship cardinality estimation signal beam to the sum of the estimates of the signal power of all rays connected with the second inputs of respective multipliers, the outputs of the multipliers are connected to the corresponding inputs of the third adder, the output of the third adder, the output of which is signal average detuning the frequency of the received multipath signal relative to the reference signal, is connected to the second inputs of the second adders and the generator input, voltage-controlled the outputs of the second adders are the output signals of the relative detuning of the frequency of the signal beam, and outputs of the device.



 

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3 cl, 2 dwg

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