Method and device for receiving pseudorandom operating frequency tuning signals

FIELD: radio engineering.

SUBSTANCE: device implementing proposed method designed for use in pseudorandom operating frequency tuning radio communication systems and in monitoring systems of the latter has first and second band filers 1 and 3, respectively, first and second multipliers 2 and 16, respectively, demodulator 4, first, second, third, and fourth delay lines 4, 5, 7, and 9, respectively, adjustable frequency synthesizer 6, first, second, third, and fourth spectrum analyzers 10, 11, 12, and 13, respectively, first and second subtracters 14 and 15, respectively, comparator 17, and maximal higher-than-threshold component searching unit 18.

EFFECT: ability of signal reception and demodulation in case of a priori uncertain pseudorandom operating frequency tuning program.

2 cl, 8 dwg

 

The proposed method and device relate to the field of radio engineering and can be used in radio systems with pseudorandom change the operating frequency (frequency hopping) and in the control systems of radio communication systems with frequency hopping.

Known methods and devices for receiving signals from a pseudo-random operating frequency tuning (AVT. mon. The USSR№№403084, 1291984, 1381721, 1742741, 1760471; RF patents №№2161863, 2215370, 2219656; U.S. patent No. 5077538, 5379046; patents WO No. 96/10309, 96/19877. "Foreign Radioelectronics", 1979, No. 3, pp.42-51; Chistyakov NI a Receiving device. - M.: Owls. radio, 1978, p.29-30; Borisov, V.I. and other Immunity of radio communication systems with expansion of the range of signals, the method of pseudo-random adjustment of the operating frequency. - M.: Radio and communication, 2000, p. 24, figure 1.7, b and others).

Known methods closest to the present invention is a method for receiving signals with pseudorandom change the operating frequency, which is implemented in the device described in the monograph Vierimaa and other "noise Immunity of radio communication systems with expansion of the range of signals, the method of pseudo-random adjustment of the operating frequency" - M.: Radio and communication, 2000, p.24, figure 1.7, b, is selected as the base.

The structural scheme of the device, which implements the prototype method is presented in figure 1, where we have introduced the following notation:

1, 3 - first and second Polozov the nd filters;

2 is a multiplier (mixer);

4 - demodulator;

5 is a generator of pseudo-random code;

6 - tunable frequency synthesizer.

The device prototype includes serially connected first band-pass filter 1, a signal input which is the input of the multiplier 2, the second band-pass filter 3 and the demodulator 4, the output of which is the output of the device, and the generator 5 pseudo-random code, the n outputs of which are connected with the control n inputs tunable frequency synthesizer 6, the output of which is connected to a second reference input of the multiplier 2.

A device that implements the basic method is as follows.

The input device receives an input mixture signal with pseudorandom change the operating frequency, which is a sequence of N radio pulses duration τ0modulated information whose carrier frequencies are changed by a given pseudo-random code (program pseudorandom realignment), and narrowband interference frequencies which coincide with the frequencies of the signal.

The input mixture is fed to the input of unit 1, where it is filtered in the frequency band occupied by the signal with pseudorandom change the operating frequency. From the output of block 1 input mixture flows to the input unit 2, the second is porny input of which receives the reference signal with pseudorandom change the operating frequency, forming unit 6 for controlling the n inputs of which a pseudo-random code with n outputs of the block 5, which defines the law of frequency tuning unit 6. In the result of multiplying the input signal with synchronous with him a reference signal is convolution of the input signal with pseudorandom change the operating frequency to an intermediate frequency that is filtered by block 3 in bandwidth ΔF, consistent with the duration of τ0and is demodulated in block 4, the output of which is fed to the output device.

Narrow-band interference due to the multiplication with a tunable frequency reference signal into the output of block 2 in the radio pulses duration τ0that may be different from the radio signal only amplitude. The impulses formed in the block 2 are filtered by unit 3 and demodulate unit 4, while their influence is reduced to the distortion of the received information.

The basic method implemented in the device represented in figure 1, is based on filtering the input mixtures containing signal with pseudorandom change the operating frequency and interference in the band ΔF equal to the frequency band occupied by the signal with pseudorandom change the operating frequency, and then filter the result of the multiplication is the band Δ F(ΔF≪Δƒ), consistent with a spectral width of vnutripolostnoe information modulation signal on each of its N frequencies and demodulation.

The basic method consists of the following sequence of actions on the input mixture.

The input mixture signal with pseudorandom change the operating frequency, which is a sequence of N radio pulses duration τ0, whose carrier frequencies are changed at random program (code), and the interference filter in the band Δƒoccupied by the signal with pseudorandom change the operating frequency. The result of filtering Peremohy synchronous reference oscillation representing a signal with pseudorandom change the operating frequency, the frequency of which ƒopdifferent from the frequency of the input signal ƒwithon a constant ƒCRequal to the intermediate frequency:

The result of the multiplication, which represents the convolution of the input signal with pseudorandom change the operating frequency to an intermediate frequency equal to ƒCR, is filtered in the band ΔF, consistent with a spectral width of vnutripolostnoe information modulation. When this interference at frequencies differing from ƒcin the bandwidth of the second bands of the first filter does not fall and do not pass on the demodulator. Filtered in the frequency band of the signal on the intermediate frequency demodulator.

However, the basic method does not provide opportunities for reception and demodulation of the signal under conditions of a priori uncertainty of the program pseudorandom realignment of its operating frequency.

An object of the invention is the provision of reception and demodulation of the signal under conditions of a priori uncertainty of the program pseudorandom realignment of its operating frequency.

The problem is solved because, according to the method of receiving signals with pseudorandom change the operating frequency based on the filter input mixture in the band Δƒoccupied by the signal with pseudorandom change the operating frequency, the multiplication of the filter with synchronous reference signal and then filter the result of the multiplication in the frequency range ΔF, consistent with the duration of the radiation signal with a pseudorandom operating frequency tuning τ0on each of the N frequencies of perestroika, and its demodulation, choose the measuring time interval τACthe result of filtering the input mixture in the band Δƒ sequentially delayed for the time intervals τACτ0ACand τAC, thus forming four measurement intervals in the well, duration τACeach are determined by measuring the intervals sliding amplitude spectra of S1(ƒ),S2(ƒ),S3(ƒ) and S4(ƒ), respectively, and the difference between the amplitude of the sliding spectra of S21(ƒ)=S2(ƒ)-S1(ƒ) and S34(ƒ)=S3(ƒ)-S4(ƒ), Peremohy received the difference between the amplitude of the sliding spectra between each other

S2134(ƒ)=S21(ƒ)×S34(ƒ),

the spectral function S2134(ƒ) is compared with the threshold level STHENchosen in such a way as to eliminate its excess due to fluctuations of only noise components of the spectral function S2134(ƒin case of exceeding the threshold level STHENdecide that the frequency spectral component of the spectral function S2134(ƒ), exceeded the threshold STHENequal to the carrier frequency of the received pulse signal ƒwithreceived the value of the carrier frequency ƒcthe current pulse signal is used for forming the reference signal with frequency ƒopcCRand the result of filtering the input mixture in the band Δƒ before multiplication with the synchronous reference signal delayed in time by the value of

τ30AC2134 ,

where S2134(f) the time spent on the formation and processing of the spectral function S2134(f).

The problem is solved in that the device for receiving signals with pseudorandom change the operating frequency, containing the first band-pass filter, the input of which is the input of the cascaded tunable frequency synthesizer, the first multiplier, the second bandpass filter and demodulator whose output is the output of the device, supplied with four delay lines, four spectrum analyzers, two vycitalem, a second multiplier, a comparator, and a device search maximum spectral component exceeding the threshold, and the output of the first bandpass filter through the first delay line connected to the second input of the first multiplier, the output of the first bandpass filter connected in series, a second delay line the second spectrum analyzer, the first myCitadel, the second input is through the first spectrum analyzer connected to the output of the first bandpass filter, a second multiplier, a comparator, and a device search maximum spectral component exceeding the threshold, the output of which is connected with the control input of the tunable frequency synthesizer, the output of the second delay line connected in series, the third l is of delays, the fourth delay line, the fourth spectrum analyzer and the second myCitadel, the second input is through the third spectrum analyzer connected to the output of the third delay line and the output is connected to the second input of the second multiplier.

Due to the fact that with increasing duration of the measuring interval τACthe measurement accuracy of the carrier frequency increases, and as the selection of the input pulse duration decreases, the value of τACare chosen to provide a compromise between the specified parameters.

Value τACis selected on the one hand based on the required accuracy of the estimation of the carrier frequency of the pulse signal with frequency hopping due to the fact that the duration of the measurement interval is proportional to the realized accuracy of frequency measurement, and on the other hand, based on the desired quality selection of the input pulse signals in duration due to the fact that the quality of selection is higher, the shorter the interval of analysis.

Under the current amplitude spectrum of the input mixture is understood to mean the amplitude spectrum generated to the current time tTECHthe fragment of the input mixture in the interval from tTECHACto tTECH.

As spectrum analyzers, forming the sliding amplitude range of the input mixture in the range analysis τAU can be used device, comprising serially connected analog-to-digital Converter and calculator fast Fourier transform on the interval τAC. In this case, the operation of differencing amplitude spectra, calculating multiplication of the obtained difference, the comparison with the threshold level and selecting the maximum spectral component, exceeded the threshold, can be implemented using arithmetical-logical unit.

The structural scheme of the device that implements the proposed method is presented in figure 2. Time and frequency diagrams explaining the principle of operation of the device shown in figure 3, 4, 5, 6, 7 and 8.

The device comprises series-connected first band-pass filter 1, the inlet of which is the input of the first delay line 5, the first multiplier 2, the second band-pass filter 3 and the demodulator 4, the output of which is an output device. The output of the first bandpass filter 1 serially connected second delay line 7, the second spectrum analyzer 11, the first myCitadel 14, the second input is through the first spectrum analyzer 10 is connected to the output of the band pass filter 1, the second multiplier 16, a comparator 17, the device 18 searching for the maximum spectral component, exceeded the threshold, tunable synthesizer 6 h is the frequency, the output of which is connected with the second input of the first multiplier 2. The output of the second delay line 7 connected in series, the third delay line 8, the fourth delay line 9, the fourth analyzer 13 of the spectrum and the second myCitadel 15, the second input is through a third analyzer 12 of the spectrum is connected to the output of the third delay line 8, and the output connected to the second input of the second multiplier 16.

The proposed method is implemented as follows.

The input mixture signal with pseudorandom change the operating frequency, which is a sequence of N radio pulses duration τ0with vnutripolostnoe information modulation and spectrum width Δƒ, whose carrier frequencies are changed in accordance with a given program pseudorandom adjustment of the operating frequency and narrow-band interference and interfering radio pulses with a duration other than τ0arrive at the input of the first bandpass filter 1, where it is filtered in the frequency band occupied by the signal with pseudorandom change the operating frequency.

From the output of the first bandpass filter 1 input mixture is fed to the input of the first delay line 5, which provides a delay signal to the range τACat the entrance of the first analyzer 10 of the spectrum, calculates the amplitude sliding the spectrum of the input mixture on the time interval τ ACand to the input of the second delay line 7, which provides a delay time interval τAC. From the output of the second delay line 7 input mixture is fed to the input of the second analyzer 11 of the spectrum, calculates the amplitude sliding range of the input mixture on the time interval τACand to the input of the third delay line 8, which provides a delay signal to the range τ0AC(figure 3).

With the release of the third delay line 8 input mixture is fed to the input of the third analyzer 12 of the spectrum, evaluates the sliding range of the input mixture on the time interval τACand to the input of the fourth delay line providing a delay signal to the range τAC, from which it is fed to the input of the fourth analyzer 13 of the spectrum, evaluates the sliding range of the input mixture on the time interval τAC. At the time the diagram presented on figure 3, shows the basic timing when the processing of the signal with pseudo-random rearrangement of the operating frequency, consisting of radio pulses duration τ0. This chart intervals on which the first, second, third and fourth spectrum analyzers are formed corresponding sliding spectra, labeled 1, 2, 3, and 4, respectively.

Formed in the current point in time per the om 10 and second 11 spectrum analyzers sliding amplitude spectra of S 1(ƒ) and S2(ƒ), respectively, is fed to two input vicites 14, which defines their difference

S2l(ƒ)=S2(ƒ)-S1(ƒ).

Formed in the current time in the third 12 and fourth 13 spectrum analyzers sliding amplitude spectra of S3(ƒ) and S4(ƒ), respectively, is fed to two input vicites 15, which defines their difference

S34(ƒ)=S3(ƒ)-S4(ƒ).

The difference of the amplitude spectrum S21(ƒ) and S34(ƒ) with outputs vychitala 14 and 15 is fed to two inputs of the multiplier 16, which calculates the spectral function in the form of a work

S2134(ƒ)=S21(ƒ)×S34(ƒ).

The comparator 17 compares the spectral function S2134(ƒ) with the threshold level STHEN.

The principle of formation of the spectral function S2134(ƒ) for the relative position of the intervals forming the amplitude spectra and pulse signal with pseudorandom change the operating frequency, is shown in figure 3, is illustrated in figure 4.

Exceeding the threshold level Sthenit is possible only in the case when the mutual position of the current pulse signal with pseudorandom change the operating frequency and intervals of the formation of the sliding spectra of the first 10, second 11, 12 and the third the fourth the 13 th spectrum analyzers corresponds to the situation shown in figure 3. In this case, the value of the spectral component of the spectral function S2134(ƒ), exceeded the threshold STHENis the carrier frequency ƒwiththe received pulse signal with pseudorandom change the operating frequency. The resulting value of the carrier frequency ƒwiththe current pulse signal is used to set the synthesizer 6 frequencies so as to ensure conditions:

ƒOPwithCR

When the amount of delay τ3the first delay line 5 is selected on the basis of the pulse duration τ0constituting the signal with pseudorandom change the operating frequency, interval analysis τACrequired for the formation of the current running spectrum of the fourth-13 spectrum analyzer and time τ2134used to determine the spectral function S2134(ƒ), comparing it with the threshold level STHENand the evaluation values of the carrier frequency of the current pulse

τ30+AC2134.

The threshold value STHENselected in such a way as to eliminate its excess due to the fluctuation of the noise spectral components of the function S2134(ƒ).

When the mutual position of the current signal with pseudorandom change of working often the s and intervals of the formation of the sliding spectra of the first 10, the second 11 and third 12 and fourth 13 spectrum analyzers are not relevant to the position shown in figure 3, for example, as shown in figure 5, the threshold value STHENnot happening, which is illustrated by the charts in figure 5 and 6.

If the input mixture contains a narrowband signal with a fixed carrier frequency, it is not detected through the use of the algorithm for determining the spectral function S2134(ƒand, therefore, does not affect the operation of the device. If the input mixture contains a pulse signal with a duration other than τ0he also is not detected due to the use of the algorithm for determining the spectral function S2134(ƒand does not affect the operation of the device. These provisions are illustrated by charts 7 and 8.

Thus, the proposed method and the device in comparison with a base and other technical solutions for a similar purpose to provide reception and demodulation of the signal with pseudo-random rearrangement of the operating frequency with a given duration of radiation, equal to τ0on each of the N frequencies without a priori knowledge of the program pseudorandom adjustment of the operating frequency on the background of interfering signals in the form of narrowband and impulsive noise, possibly a member of the other signal with the pseudorandom pirastro is some of the operating frequency. This provides a measurement of the carrier frequencies of the pulses of the received signal with pseudorandom change the operating frequency, which may be used additionally for opening programs pseudorandom realignment.

1. The method of receiving signals with pseudorandom change the operating frequency based on the filter input mixture in the band Δƒoccupied by the signal with pseudorandom change the operating frequency, the multiplication result to the synchronous reference signal and then filter the result of the multiplication in the frequency range Δƒconsistent with the duration of the radiation signal with a pseudorandom operating frequency tuning τ0on each of his N frequency restructuring program, and its demodulation, characterized in that it calculates on the measuring intervalsamplitude sliding spectrathe result of filtering the input mixture, wherespectrum calculated in the first measuring intervalspectra of the filter input mixture, detained onrespectively, and the difference between the amplitude of the sliding spectra of S21(ƒ)=S2(ƒ)-S1(ƒ) and S34(ƒ)=S3(ƒ)-S4(&402; ), Peremohy received the difference between the amplitude of the sliding spectra between each other

S2134(ƒ)=S21(ƒ)·S34(ƒ),

the spectral function S2134(ƒ) is compared with the threshold level STHENchosen in such a way as to eliminate its excess due to fluctuations of only noise components of the spectral function S2134(ƒin case of exceeding the threshold level STHENdecide that the frequency spectral component of the spectral function S2134(ƒ), exceeded the threshold STHENequal to the carrier frequency of the received pulse signal ƒcreceived the value of the carrier frequency ƒcthe current pulse signal is used for forming the reference signal with frequency ƒOPWithCRwhere- intermediate frequency, and the result of filtering the input mixture in the band Δƒ before multiplication with the synchronous reference signal delayed in time by the amount τ30AC2134where τ2134(ƒ) - the time required for the formation and processing of the spectral function S2134(ƒ).

2. A device for receiving signals with pseudorandom change the operating frequency, containing the first band-pass filter, I is d which is the input device, cascaded tunable frequency synthesizer, the first multiplier, the second bandpass filter and demodulator whose output is the output of the device, characterized in that it is provided with four delay lines, four spectrum analyzers, two vycitalem, a second multiplier, a comparator, and a device search maximum spectral component, exceeded the threshold, and the output of the first bandpass filter through the first delay line connected to the second input of the first multiplier, the output of the first bandpass filter connected in series, a second delay line, the second spectrum analyzer, the first myCitadel, the second input is through the first spectrum analyzer connected to the output of the first bandpass filter, a second multiplier, a comparator, and a device search maximum spectral component exceeding the threshold, the output of which is connected with the control input of the tunable frequency synthesizer, the output of the second delay line connected in series, the third delay line, the fourth delay line, the fourth spectrum analyzer and the second myCitadel, the second input is through the third spectrum analyzer connected to the output of the third delay line and the output is connected to the second input of the second multiplier.



 

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EFFECT: increased receiving device operation stability and decreased probability of error during receipt of discontinuous message symbols.

3 dwg

FIELD: information transfer with spectrum expansion, realized by means of chaotic signals.

SUBSTANCE: in accordance to method, at transmitting side information carrier is formed within given frequency range by means of chaotic dynamic system, structure of which is preliminarily synthesized in accordance to given characteristics of information carrier with required spectrum, complete chaotic information carrier is modulated by appropriate information signal and then its transferred along communication channel to receiving side, where receipt and demodulation is performed on received chaotic information carrier by means of dynamic system, synchronized by behavior with chaotic dynamic system of transferring side, while spectral power density of modulated chaotic information carrier satisfies given spectral mask.

EFFECT: information transfer between two or more users with consideration of limits on spectrum density of power of signal transmitted through communication channel.

2 cl, 20 dwg

FIELD: radio engineering; construction of radio communication, radio navigation, and control systems using broadband signals.

SUBSTANCE: proposed device depends for its operation on comparison of read-out signal with two thresholds, probability of exceeding these thresholds being enhanced during search interval with the result that search is continued. This broadband signal search device has linear part 1, matched filter 2, clock generator 19, channel selection control unit 13, inverter 12, fourth adder 15, two detectors 8, 17, two threshold comparison units 9, 18, NOT gates 16, as well as AND gate 14. Matched filter has pre-filter 3, delay line 4, n attenuators, n phase shifters, and three adders 7, 10, 11.

EFFECT: enhanced noise immunity under structural noise impact.

1 cl, 3 dwg

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