Device for suppressing narrow-band interferences

FIELD: radio communications.

SUBSTANCE: device has broadband amplifier of intermediate frequency, narrowband interferences suppressor, adder, synchronized filter, intermediate frequency amplifier, narrowband interferences suppression elements, multiplier, integrator, support signal generator, spectrum analyzer 10, decimation index 11, clock pulse generator 12, first 13 and second 14 decimators.

EFFECT: higher trustworthiness, higher resistance to interference.

7 dwg

 

The proposed device relates to the field of radio engineering and can be used mainly in full-duplex radio control and packet radio networks, operational command positional relationship in areas under influence of narrowband interference.

It is known device for suppressing narrowband interference (A.S. USSR №754681, CL N 04 1/10)containing n connected in series, a self-tuning notch filter. However, this device together with the interference is suppressed and the spectrum of the useful signal.

It is also known a device in which to suppress narrowband interference is used comb switched filters (A.S. USSR №720730, CL N 04 1/10).

The disadvantage of this device is its complexity due to the presence of combs narrowband dial-up filters and additional electrical losses caused by eidetically and instability over time of the amplitude and phase characteristics of the individual filters.

The closest to the technical nature of the claimed object is the suppression of narrowband interference", found in the book "the Immunity of systems with complex signals," edited by Tuzova GI, Moscow, "R. and C." 1985, str, Risa adopted for the prototype.

Figure 1 shows the structural diagram of the device of the prototype, which marked is:

1 - broadband intermediate frequency amplifier (if amplifier);

2 - the suppression of narrowband interference (block protection);

3 - adder;

4 - consistent filter;

51-5nthe intermediate frequency amplifier (if amplifier);

61-6nelements of suppressing narrowband interference;

7 - multiplier;

8 - integrator;

9 generator reference signal.

The device prototype contains connected in series broadband amplifier 1 and the protection block 2, the n outputs of which are connected to the corresponding inputs of the adder 3, the output of which is connected to the input of the matched filter 4 whose output is the output device. Moreover, the protection block 2 consists of n parallel channels, each of which consists of series-connected amplifier 5 and the n elements of suppressing narrowband interference 6, the outputs of which are the respective outputs of the block 2.

In addition, the inputs of the amplifier 6 of each of the n channels are connected and are input unit 2. Consistent filter 4 includes sequentially connected to the multiplier 7 and the integrator 8, the output of which is the output of the filter 4, and the reference signal generator 9, the output of which is connected with the second input of the multiplier 7, the inlet of which is the input of the matched filter 4.

Function prototype as follows.

Adopted broadband signal (W is C) after frequency conversion is fed to a broadband amplifier 1, where is amplified to the required size and then fed to the narrowband noise suppressor 2 (protection unit), consisting of n narrow-band if amplifier 51-5nand n elements of suppressing narrowband interference 61-6n.

Using filters narrow-band if amplifier 51-5nall band PSS is divided into n partial channels

where Δƒ - width of one partial channel;

ΔF - band width of the received PSS;

n is the number of partial channels.

The width of bands of all n partial channels must be the same and, in addition, the bandwidth of the partial channels must not overlap and therefore the amplitude-frequency characteristic (AFC) and phase characteristic (PFC) suppressor represented as the sum of AFC and PFC individual channels

Each partial channel in addition to the notch filter includes an amplifier, which compensates the attenuation in the filter its partial channel.

The choice of the bandwidth of each partial channel is made so that each partial channel was not more than one narrowband interference.

If any of the partial channels more than one narrowband interference suppression is in her elements suppression 61-6n. Elements under the effect of narrowband interference 6 1-6nare nonlinear elements, working in either restrict the input mixture, either in the mode key (the channel is open at low levels of interference and closed at high levels of interference).

From the output of the narrowband noise suppressor 2 signal n outputs is supplied to the adder 3, where the summed across frequency band ΔF=n·Δƒ. From the output of the adder 3 broadband signal at a consistent filter 4.

Your prototype as a matched filter can be used as passive coherent filter based on a multi-tap delay line, active and consistent filter correlator.

Using the matched filter 4 is merging broadband modulation, i.e. collapsing.

The disadvantage of the prototype is registrovana plots of the frequency spectrum, that is, when the elements of suppressing narrowband interference in a mode key and in the presence of narrowband interference levels are locking these keys; a great loss of energy of the received signal, encased in rejection the plot, and the more narrowband interference in the spectrum of the received signal, the greater part of the energy is lost, greatly reducing the reliability of the received signal.

To eliminate this drawback in the device, teramae broadband amplifier and block protection n outputs of which are connected to respective inputs of the adder, the output of which is connected to the input of the matched filter whose output is the output of the device, and protection block contains n parallel channels, each of which consists of series-connected narrowband if amplifier and element suppression of narrowband interference, the output of each of which is the corresponding output block protection, additionally, the input narrow-band amplifier of each of the n channels are connected and are the input of block protection, consistent filter contains connected in series multiplier and integrator whose output is the output of the matched filter, and the reference signal generator, with the input of the multiplier is input the matched filter according to the invention, introduced a spectrum analyzer, shaper index decimation, the generator of clock pulses, and first and second Decimator, and the spectrum analyzer input connected to the output of the broadband amplifier and the first input of the first Decimator and n outputs a spectrum analyzer connected respectively with n inputs shaper index decimation controlled input of which is connected to one of the outputs of the oscillator reference signal, the output of the shaper index decimation is connected by bus with the second inputs of the first and second Decimator is in, the third inputs of which are connected with the output clock and the input of the oscillator reference signal, the other output of which is connected to the first input of the second Decimator, the output of which is connected with the second input of the multiplier, and the output of the first Decimator connected to the input of the protection block.

Figure 2 shows a functional diagram of the proposed device, where indicated:

1 - broadband intermediate frequency amplifier (if amplifier);

2 - protection block (narrowband noise suppressor);

3 - adder;

4 - consistent filter;

51-5n- narrowband intermediate frequency amplifiers;

61-6n- suppressors of narrowband interference;

7 - multiplier;

8 - integrator;

9 - the reference signal generator;

10 is a spectrum analyzer;

11 - shaper index decimation;

12 is a generator of clock pulses;

13, 14, the first and second Decimator.

The proposed device has connected in series broadband amplifier 1, the first Decimator 13, the protection block 2 consisting of n parallel channels, each of which consists of series-connected amplifier 5 and the elements of suppressing narrowband interference 61-6nthe outputs are the corresponding outputs of the protection unit 2 and connected to respective inputs of the adder 3, you are the od which is the input of the matched filter 4, consisting of series-connected multiplier 7 and integrator 8, the output of which is the output of the device and of the series-connected reference signal generator 9 and the second Decimator 14, the output of which is connected with the second input of the multiplier 7.

The output of amplifier 1 is connected to the input of the spectrum analyzer 10, the n outputs of which are connected respectively to the n inputs of the former (index decimation 11, controlled input connected to the second output of the reference signal generator 9. The shaper's output index decimation 11 bus is connected with the second inputs of the first Decimator 13 and the second Decimator 14, the third inputs of which are connected with the input of the reference signal generator 9 and the generator output clock pulses 12.

The proposed device is as follows. Photomanipulation signals (FM) represent a sequence of impulses, the initial phase of which is changed by law, pseudo-random sequence (SRP). In most cases, the FM signal consists of a radio with two values of the initial phases (0, π). Such signals are formed modulation binary SRP, and their complex envelope is a sequence of positive and negative videokursov.

The spectrum of the complex envelope of the FM signal shall meet the following form:

where τ - the duration of the elementary pulse FM signal;

N is the length of the SRP (base FM signal);

So(W) spectrum of the elementary pulse FM signal;

anelements of the SRP (11-1).

For a rectangular pulse

The sum in the right part of expression (1) is spectrum code sequence (range SRP).

The spectrum of the FM signal can be represented as a product in discrete form

In the expression (2) left factor depends only on the shape of the elementary pulse, and the right only on the structure of the SRP. This representation is very convenient for further descriptions.

Call decimate the operation cycle of each q-th element of the SRP. A positive number q will be called the index of the collection. In the expression (1) it is shown that the decimation of the SRP its spectrum code sequence H(K) is changed according to the law

where N(K) is the spectrum of the original SRP;

Hq(K) - spectrum of the SRP after its collection.

From the expression (5) shows that the spectrum as well as the SRP is changed according to the law of decimation. But if the SRP to deciminate index q, the spectrum is converted by the decimate by index 1/q. Thus, when the decimation is possible to rearrange spectral the major components of the law, defined by the decimate. Here, note that H(K) for the M-sequences have the same valuefor all K>0. Therefore, the expression (5) holds for truncated M-sequences, sequences GOLA, Kasami and their truncations, which are currently widely used in modern communication systems with PSS for different purposes.

Knowing the spectral position of the narrow-band interference, it is possible to adjust the spectrum of the signal under noise.

The above was taken into account only the second component of expression (4) by decimation. Considering the first component can not only rearrange the spectral components, but also to increase the "gap" in the spectrum.

It should also be noted that with the decimation of the SRP her auto - and cross correlation functions (the values of their emissions) are not changed, the expression (2), that is, when the noise at the output of the optimal filter is not reduced. Moreover, when the decimation received FM signal together with noise will decorrelation separate counts of noise (see Bessarabova A.A., Davydov IV, Stepkin V.M. "Correlation and spectral properties of pseudorandom sequences with the decimation", "radio", 1987, CH, No. 7).

Adopted by the FM signal after frequency conversion is fed to a broadband amplifier 1, which is amplified to the necessary the th value. And the same signal at the first input of the first Decimator 13. The signal has a frequency range of the expression (1), which is fed to the spectrum analyzer 10, where with the help of narrow-band filters, the entire band PSS is divided into n narrow strips so that each strip could not get more than one narrowband interference. N first output of the spectrum analyzer 10 signal in the form of a binary code of length (0 - indicates that there is no interference; 1 corresponds to the presence of interference in the channel above the level of the signal) is supplied to the driver index decimation 11.

To the input reference signal shaper index decimation 11 signal of videotopia with generator reference signal 9. The former index decimation 11 code modulating SRP coming from the reference signal generator 9 and the binary code received from the spectrum analyzer 10 and the corresponding interference in the frequency channel is determined by the decimation index q required for the decimation in Decimator 13 and 14, which are connected with the shaper index decimation 11.

In the first Decimator 13 is shifting in time of the spectral components in accordance with the index collection. Output Decimator 13 adjusted FM signal having a spectrum code sequence, the expression (5), comes to the protection block 2.

Similar de is imaze is in the second Decimator 14 with a reference signal generator 9.

The former index decimation 11 in binary code SRP j, j=1...N, are sent from the reference signal generator 9 in accordance with the expression (3) is determined spectrum code sequence N(K). Defines the number of Ki for L lowest value (L is the number of dips in the spectrum), i=1...L).

Code is generated "spectrum holes" Gj, j=1...N

With the spectrum analyzer 10 receives the binary code of the presence of interference in the frequency channel aj; j=1...n

Consistently define the index of decimation qijfor spectral components: i=1...L; j=1...M,

where M is the number of single-character code in ai.

where minumbers of single characters in code ai.

After the decimation of the spectral components of N(K) in accordance with the decimation index qijdefines the number of matching single elements W codes aiand bi. Select qijmaxfor which W has the maximum value.

The index of the collection for the SRP determined in accordance with expression (5).

On figa shows the spectrum code sequence H(K), for a sequence of Gould length N=31, figb shows the spectrum of the SRP, the resulting decimation index q=3.

From figb seen that the spectral comp is engaged when it was transformed in accordance with the decimate index

On figa and 5B shows the spectra of FM signals with narrowband interference to the decimation and after, respectively.

In this example, the components of the SRP rearranged in accordance with the decimate by index q=3 and then the elements of this SRP will be in the following sequence:

0, 3, 6, 9, 12, 15, 18, 21, 24...,

and components spectrum code sequence in accordance with

will 0, 6, 12, 18, 24, 30, 5, 11, 17...

In the narrowband noise suppressor 2 (block protection), the entire band PSS is divided into n partial channels with filters narrow-band if amplifier 51-5n. The width of bands of all n partial channels must be the same and, in addition, the bandwidth of the partial channels must not overlap. Therefore, the amplitude-frequency characteristic (AFC) and phase characteristic (PFC) suppressor 2 are represented as the sum of the frequency response and phase characteristics of the individual channels.

The choice of the bandwidth of each partial channel is made so that each partial channel was not more than one narrowband interference. If any of the partial channels narrowband interference suppression is in her elements suppression 61-6n. Elements of suppressing narrowband interference 61-6nprovide the make of yourself nonlinear elements, working either in the mode key (the channel is open in the absence or low levels of interference and closed at high levels of interference), or in the restriction mode of the input mixture.

From the output of the narrowband noise suppressor 2 signal n outputs is supplied to the adder 3, where the summed across frequency band and the output of the adder 3 broadband signal at a consistent filter 4. As the matched filter can be used as passive coherent filter based on a multi-tap delay line, active and consistent filter correlator.

In the proposed device uses a correlator consisting of a multiplier 7, the integrator 8, the reference signal generator 9 and Decimator 14.

One possible implementation of decimation 13 and 14 shown in figa and 6b, respectively. Decimator 13, a functional diagram of which is shown in figa, works as follows. Elements taken M-sequence come to an analog-to-digital Converter (ADC) 13.15, where analog is converted to digital and through the first switch 13,1 alternately at time intervals N/ƒtequal to the period M-sequence are recorded alternately in the first RAM 13.2 and second RAM 13.3. During recording in the first RAM 13.2 read from the second RAM 13.3 and Vice versa. Scity aema information via a second switch 13.4 fed to the input of digital to analogue Converter (DAC) 13.6, where is converted to analog form and then output Decimator. Phase switching switches 13.1 and 13.4 mode control read and write RAM 13.2 and 13.3 is determined by the state of flip-flop outputs 13.5, the input of which receives pulses with frequency ƒt/N frequency divider 13.8, the input of which receives the clock pulse frequency clock pulse. The clock pulses are also fed to the input of the first counter 13.9, the output of which is parallel binary code is supplied to the first input of the third switch 13.6. On the second counter 13.12 received pulses with a frequency N·ƒtwith frequency multiplier 13.11, the input of which receives the pulses of the clock frequency. Parallel binary code output of the second counter 13.2 arrives at the inputs of schema matching 13.13 and register latch 13.10, the output of which is parallel binary code is supplied to the first input of the fourth switch 13.7. To the second input of schema matching is decimation index q in the form of binary code. With the output of the circuit matches 13.13 signal of the logic unit is supplied to the second input of the register - latch 13.10 and to the first input circuit And 13.14, to the second input of which receives the clock pulses and the output signal is fed to the input reset to the zero state of the second counter 13.12. On the state clock inputs of the third switch 13.6 and fourth 13.17 whitefish is al comes from the direct and inverted outputs of the trigger 13.5 respectively. The outputs of these switches are the address inputs of RAM 13.3 and 13.2, respectively.

Put blocks 13.10, 13.11, 13,12, 13.3, 13.4 allow to generate the address for the RAM in accordance with the decimation of the input signal at the specified index of the collection q.

Functional diagram of the second Decimator 14 shown in figb, which is different from the first Decimator 13 lack AD and DAC. The principle of operation it is similar to the principle of operation of the first Decimator 13.

Figure 3 shows a functional diagram of one possible implementation of spectrum analyzer 10. Block spectrum analyzer with one entrance and two pairs of n outputs can be implemented as shown in figure 3, which works as follows. The signal at the inputs of bandpass filters 10.11-10.1nwith which band width of the received signal is divided into n bands. The outputs of bandpass filters 10.11-10.1nare the inputs of the n devices comparison 10.21-10.2non the second input of which is supplied a constant voltage n threshold. The outputs of circuits compare 10.21-10.2nare the outputs of the spectrum analyzer 10.

Shaper index decimation unit 11 may be implemented as software on the microprocessor. The block diagram of algorithm of calculation of index q decimation is shown in figa and 7b.

In blocks 1-5 of the algorithm code is generated "on the rock spectrum" Cj and binary SRP bj and calculated the number of gaps in the spectrum of L.

In blocks 6-9 formed non frequency channels with interference mtoand the number M

In blocks 10-19 calculated indexes collection qijfor different "spectrum holes" and select qmaxproviding the maximum number of matches and gaps of the spectrum of the FM signal to noise in the channel protection unit (KB).

Input: binary code interference in the frequency channel

ai, i=1...N with block 10;

- binary code SRP bi, i=1...N with unit 9;

- the minimum value of the spectral component of Hminis specified by the developer.

Output: - the index of the collection q.

Device for suppressing narrowband interference, containing a broadband intermediate frequency amplifier (if amplifier), the block sewn, n outputs which are connected to the corresponding inputs of the adder, the output of which is connected to the input of the matched filter whose output is the output of the device, and protection block contains n parallel channels, each of which consists of series-connected narrowband if amplifier and element suppression of narrowband interference, the output of each of which is the corresponding output block protection, additionally, the input narrow-band amplifier of each of the n channels are connected and are the input of block protection, consistent filter contains connected in series multiplier and in erator, the output which is the output of the matched filter, and the reference signal generator, the input of the multiplier is the input of the matched filter, characterized in that the input spectrum analyzer, shaper index decimation, clock generator pulses, the first and second Decimator, and the spectrum analyzer input connected to the output of the broadband amplifier and the first input of the first Decimator and n outputs a spectrum analyzer connected respectively with n inputs shaper index decimation controlled input of which is connected to one of the outputs of the oscillator reference signal, the output of the shaper index decimation is connected by bus with the second inputs of the first and second decimators, the third inputs of which are connected between a, with the output clock and the input of the oscillator reference signal, the other output of which is connected to the first input of the second Decimator, the output of which is connected with the second input of the multiplier, the output of the first Decimator connected to the input of the protection block.



 

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