Method and device for controlling transmission power in mobile communications system

FIELD: mobile communications.

SUBSTANCE: power controller, placed between filters, generating common-mode and quadratic channels pulses, and frequency transformer, during each selection period calculates compensation signals for pulses of signals, which increase relation of top power to average power; by means of said pulse generating filters among compensation signals it filters out compensation signals having higher level and combines compensation signals having passed filtering stage with source signals. In such a way, spectrum expansion beyond limits of signals frequencies band is suppressed. In case of a system, supporting numerous assigned frequencies, adjustment of relation of top power to average power is performed for each assigned frequency according to its maintenance category.

EFFECT: higher efficiency.

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The present invention relates in General to the mobile communications system and, in particular, to a device and method designed to reduce peak power to average power of the signal (OPSM) at the base station (BS) from the mobile communication system.

As is known, the gain-frequency (RF) signal, including those intended for the mobile station (MS) speech and data, the BS uses an RF power amplifier. RF amplifier is the most expensive device in the entire system and, thus, an important component to be considered in the context of reducing the cost of the system. This RF amplifier should be designed so that it satisfies two requirements: one is to give power RF signal at a level sufficient to cover all MS located in the service area of a cellular cell; and the other is to keep interference adjacent channel (DB) output signal of the RF amplifier at an acceptable level or below it.

If the value of the input power, which provides sufficient output power RF signal is outside the scope of the linear gain of the power amplifier, because of the nonlinear amplification of the output signal of the power amplifier has a distortion component of the signal outside the bandwidth of this signal is La. In other words, in the frequency plane expansion of the range outside the frequency band of the signal causes the UCS. Is very difficult to design a power amplifier that meets these requirements, because the first one requires high power input, and the second requires a low input power.

The feature is that the system with high OPSM, such as multiple access, code-division multiplexing (mdcr), should control the input power to ensure the power amplifier to function in the field of linear amplification, or to use an expensive power amplifier with linearity at maximum input power. In this context, the system mdcr requires expensive power amplifier, which can adapt the maximum input power, 10 dB above the average power input to suppress distortion of the signal. However, as stated earlier, such a power amplifier reduces the efficiency of use of power and increases the power consumption, the size of the system and its cost. Moreover, the BS at the same time transmits signals with multiple assigned frequency (LF), using a power amp for each WOOFER, which imposes economic constraints. Therefore, effective layout and design is ukcia power amplifiers are very important for the design of BS.

One approach to stable operation of the power amplifier in the system with high OPSM is to use correction circuits pre-emphasis for the maximum input power. The correction pattern distortion measures the signal distortion introduced by the power amplifier, and controls the input signal of the power amplifier based on the measurement results. The power amplifier generates an amplified signal from the original input signal by attenuation distortion.

In the process of measuring distortion included very complex processes, such as modulation and demodulation, taking samples, sampling, synchronization and comparison between input and output signals. The correction pattern distortion uses its input and output signals in order to match the standards of the power of the adjacent channel (MSC), governing the implementation of the system. However, using this scheme, the correction of distortion cannot achieve the optimal distortion compensation due to the inherent disadvantages associated with efficiency, speed and complexity.

Another approach is to reduce OPSM input signal in the power amplifier by reducing the signal level with a predetermined speed using the maximum input power and linear characteristics of the gain of the amplifier. All the output signals are converted into signals of low power by multiplying them by the scale factors, based on the linear characteristics of the gain, for the purpose of operating the power amplifier within the range of linear amplification. Or OPSM can be reduced by reducing the power of the input signal, the value of which is equal to a certain threshold value or exceeds it, up to the desired level. The result of a decrease of the signal level with a predetermined speed or decrease the level of the signal exceeds a certain threshold value, to a predetermined level are intensive changes of the signal level and the higher power outside the frequency band of the signal. As a consequence, decreases the performance of the entire system.

The third approach consists in calculation of the intensity and power of the input signal in-phase (I) channel and the intensity and power of the input signal of the quadrature (Q) channel and in the formation of the signal compensation signals, the intensity of which is equal to the threshold value or higher. The signal intensity is reduced to the desired level by summing the source signals and the compensation signals at the same time. Signal transmission using this scheme, the gain is illustrated in figure 1.

According to Figure 1, in the communication system mdcr each channel device or channel element 1-2 from the group 1-1 channel device generates a signal p is band of modulating frequencies by applying to the data input of the corresponding channel coding, modulation and forming channels. The signals of the baseband in-phase and quadrature channels are summed separately. The processor 1-5 measures the intensity of the signals in-phase (I) and quadrature (Q) channels, calculates their power levels, decides on the intensity value of the signal that should be deleted, for each channel in accordance with the desired power level and sends signals to the compensation. Unit 1-3 combining baseband related to in-phase channel, and the block 1-4 combining baseband related to the quadrature channel, delay the signals in-phase and quadrature channels on the time required by the processor 1-5 to perform their operations, and summarize the delayed signals in-phase and quadrature channel signals of compensation in order to obtain signals from the intended power level. Filters-shapers 1-6 and 1-7 pulses limit the width of the frequency bands of the output signals of blocks 1-3 and 1-4 combining baseband related to in-phase and quadrature channels, respectively. The output signals of filters-shapers 1-6 and 1-7 pulses are transmitted to the antenna through the transducer 1-8 frequency and amplifier 1-9 power. The antenna emits signals with the required transmit power BS on station MS located within the maintenance is shrink her cell cell.

Despite the fact that the blocks 1-3 and 1-4 combining baseband related to in-phase and quadrature channels, adjust the value of OPSM signals to desired values, these values increase filter shapers 1-6 and 1-7 pulses. As a result, the amplifier 1-9 power is expanding the range outside the frequency band of the signal, thereby causing the UCS.

Thus, the present invention is the implementation of the method and device, designed to improve the efficiency of RF power amplifier to implement a stable and workable system for mobile communications.

Another objective of the present invention is the provision in a system with high OPSM method and device designed for stable operation of the power amplifier in the linear region of amplification.

Another objective of the present invention is the provision of a method and device designed to reduce OPSM input of the amplifier, without impact on the performance of the entire system.

Another objective of the present invention is the implementation of the method and device designed to reduce OPSM power amplifier and to maximize the suppression of the expansion of the range outside the frequency band C is Nala, to maximize the efficiency of the power amplifier in the context of transmission in the mobile communication system.

Another objective of the present invention is the provision of a method and device intended for simultaneous transmission of signals using multiple woofers, effectively using the power amplifiers.

Another objective of the present invention is the provision of a method and device for controlling an input signal of the power amplifier, using the controller power is placed between the filter pulse shapers in-phase and quadrature channels, and a frequency Converter.

To solve the foregoing and other objectives of the present invention, the control device transmit power from the mobile communication system supporting a single WOOFER, group channel device generates a signal to baseband in-phase channel and the signal of the baseband quadrature channel by performing coding and modulation for each data channel; filter shaper pulse filters the signals to baseband; a controller regulates power values OPSM filtered signals in accordance with the threshold power required for a linear power amplifier; a frequency Converter converts the signal is s, have been managing power with increasing frequency in the RF signals; and a power amplifier amplifies the RF signals.

The above and other objectives, features and advantages of the present invention become more apparent from the detailed description below with reference to the accompanying drawings, in which:

Figure 1 is a block diagram of the transmitter of the composition of the relevant prior art of a typical mobile communication system;

Figure 2 is a block diagram corresponding to a variant of implementation of the present invention the transmitter part of a mobile communication system using a single LF;

Figure 3 is a detailed block diagram of the controller power on Figure 2;

Figure 4 illustrates the principle of operation of the unit for computing the compensation signals from the controller power by 3;

Figure 5 illustrates the structure of the filter-forming pulses in Figure 3;

6 is a block diagram of an algorithm illustrating the corresponding variant of implementation of the present invention the operation of power control;

Fig.7 illustrates the original signal applied to the unit definition scale in Figure 3;

Fig illustrates the signals generated by the unit definition scale in Figure 3;

Fig.9 illustrer is no resultant signals, calculated by the computing unit signal compensation on Figure 3;

Figure 10 illustrates the compensation signals generated by the computing unit signal compensation on Figure 3;

11 illustrates the signal compensation with a maximum signal levels, the selected blocks determine the maximum level in Figure 3;

Fig illustrates the compensation signals with the maximum levels of the signal after processing by the filter pulse shapers and their power levels;

Fig is a block diagram corresponding to another variant implementation of the present invention the transmitter part of a mobile communication system that uses multiple LF;

Fig is a detailed block diagram of the controller power that supports a variety of bass, Fig;

Fig illustrates the power characteristics of each signal LF controller power that supports a variety of bass, when the LF signals have the same priority;

Fig is a block diagram of an algorithm illustrating a method of calculating by the computing unit scale Fig scale factors for a variety of bass with the same priority;

Fig is a block diagram of an algorithm illustrating a method of calculating by the computing unit scale Fig scale factors for many NP featuring the Misia priorities;

Fig illustrates the power characteristics of each signal LF controller power that supports a variety of bass, when the LF signals have different priorities;

Fig is a block diagram of the algorithm, illustrating another method of calculating unit calculating a scale Fig scale factors for a variety of LF with different priorities.

The following describes the preferred implementation of the present invention with reference to the accompanying drawings. In the following description, detailed descriptions of well-known functions or constructions are omitted, as too much detail can obscure the invention itself.

The description of the present invention is preceded by a definition of terms used here. OPSM or the ratio of the amplitude (KA) denotes the ratio of peak power to average power. This performance characteristic is an important factor for designing a power amplifier system mdcr in which many users share a common frequency resources. The algorithm reduce the coefficient amplitude (UCU) is an algorithm that performs the controller power to reduce OPSM in accordance with the present invention. Power loss is measured as the ratio of the maximum power required to achieve l is Nanoha gain to average power. Loss of power is used to specify the region of linear gain of the power amplifier.

2 to 12 illustrate a variant implementation of the present invention, which uses one bass, and Fig-19 illustrate another variant of implementation of the present invention, which uses a lot of bass.

The first option exercise

Figure 2 is a block diagram corresponding to a variant of implementation of the present invention the transmitter BS from the mobile communication system using a single WOOFER.

According to Figure 2, the transmitter includes a group 2-1-channel device, having at least one channel element 2-2, filters, conditioners 2-3 and 2-4 pulses are in-phase and quadrature channels, the Converter 2-5 frequency and amplifier 2-6 power. The feature is that the controller 2-8 power placed between the filter shapers 2-3 and 2-4 pulses and transducer 2-5 frequency in order to perform the algorithm INDICATED in accordance with the present invention.

When functioning group 2-1 channel device generates signals to baseband in-phase and quadrature channels by performing encoding, modulation and forming channels for each data channel. In particular, in the system mdcr signals in-phase and quadrature to the signals represent the sum total of the control signals and user data, designed for multiple users, and the summation is performed at the level of chips (symbols psevdochumoy sequence) in-phase and quadrature channels.

Due to the fact that in the system that transmits the sum of the signals of multiple channels, such as the system mdcr, there are significant variations in the output power, filters, conditioners 2-3 and 2-4 pulses limit the frequency of the signal of each channel in order to reduce the UCS. Converter 2-5 frequency located before the input of the amplifier 2-6 power, after digital to analog conversion converts the signals to an intermediate frequency (if)received from filter-shapers 2-3 and 2-4 pulses with increasing frequency in the RF signals.

The amplifier 2-6 power placed before the input of the antenna and increases the power of its input signal for the transmission of this signal with the output power required for all users within a cell of a cell of the considered BS. The antenna transmits the amplified signal at the station MILLISECONDS.

The controller 2-8 power performs the function of reducing OPSM input signal to reduce imposed on the amplifier cost constraints and prevent decrease of system performance by suppressing the expansion of the range outside the frequency band of the signal. The controller 2-8 power races is ologen for the outputs of filters-shapers 2-3 and 2-4 pulses to prevent the increase OPSM during the operation of the filter-shapers 2-3 and 2-4 pulses.

Figure 3 is a corresponding variant of implementation of the present invention, a detailed block diagram of the controller 2-8 power. According to Figure 3, the controller 2-8 assembled from a box 3-1 definitions of scale, unit 3-2 calculation of compensation signals, blocks 3-10 and 3-11 determining the maximum signal in-phase (I) and quadrature (Q) channels, filters-shapers 3-12 and 3-13 of the pulses of the maximum signal in-phase and quadrature channels, blocks 3-14 and 3-15 signal delay in-phase and quadrature channels and adders 3-16 and 3-17 in-phase and quadrature channels.

The output signals of filters-shapers 2-3 and 2-4 pulses fed to the inputs of the block 3-1 definitions of scale, blocks 3-14 and 3-15 signal delay and block 3-2 calculation of the compensation signals. The output signal I2 of the filter-driver 3-12 pulse maximum signal in-phase (I) channel and the output signal I3 of the block 3-14 delayed in-phase signal channel are summed in the adder 3-16 in-phase channel, resulting in a signal I’. Similarly, the output signal Q2 of the filter-driver 3-13 pulse maximum signal level quadrature (Q) channel and the output signal Q3 of the block 3-15 delay signal of the quadrature channel are summed in the adder 3-17 quadrature channel, resulting in a signal Q’.

To whom troller 2-8 power processes the output signals I and Q filters-shapers 2-3 and 2-4 pulses to achieve values OPSM, required for the linearity of the amplifier 2-6 power and, thus, to suppress the expansion of the range outside the frequency band of the signal.

Next, with reference to Figure 3 describes the principle of operation of the controller 2-8 power control.

Unit 3-1 determine the scale receives the signal in-phase channel, coming from the output of the filter shaper 2-3 pulses are in-phase channel (hereinafter, this signal will be called the source signal in-phase channel and the quadrature signal of the channel received from the output of the filter shaper 2-4 pulses of the quadrature channel (hereinafter, this signal will be called the source signal quadrature (Q) channel), through blocks 3-3 and 3-4 erection level signal in-phase and quadrature channels in the square, periodically makes sampling the original signal in-phase (I) and quadrature (Q) channels with a preset period and measures the levels samples of signals. Instantaneous power at each sampling period is calculated by summing the output signals of blocks 3-3 and 3-4 erection level signal in-phase (I) and quadrature (Q) channels in the square, that is, P=I2+Q2. Unit 3-5 calculation of scaling factors calculates the instantaneous power P and the predefined power threshold Pthresholdas follows.

Instant power is here P is compared with the threshold power P thresholdwhich is defined as follows:

If the instantaneous power P is less than or equal to the threshold power Pthresholdthen the scale factors to be multiplied by the signals in-phase and quadrature channels, determines is equal to 1. This means that the output signals I1 and Q1 of the unit 3-2 calculation of signal compensation equal to 0 and, as a result, the control power source signals is not performed. On the other hand, if the instantaneous power P is greater threshold power Pthreshold, the scale factors determined equal to the values which adjust the power of the source signals in order to reduce OPSM, in accordance with the following equation:

Alternatively, the scale factors can be extracted from the table of scales stored in a storage device (not shown). These scale factors are served on the block 3-2 calculation of the compensation signals.

Blocks 3-6 and 3-7 multiplication of the unit 3-2 calculation of compensation signals multiply the scale factors on the source signals in-phase and quadrature channels. The output signals of blocks 3-6 and 3-7 multiplication are the resulting signals are in-phase and quadrature channels required for linear operation in which elites 2-6 power. That is, if the instantaneous power P is greater threshold power Pthresholdthen the resulting signal of each channel, which has a threshold power Pthresholdand the same phase as the original signal of this channel, can be obtained by multiplying. Blocks 3-8 and 3-9 subtraction subtract the original signals in-phase and quadrature channels of the respective output signals and generate signals I1 and Q1 compensation.

Figure 4 illustrates the principle of operation of the unit 3-2 calculation of the compensation signals. According to Figure 4, the vector 4-1 initial signal is the vector of source signals in-phase and quadrature channels generated by the filter shapers 2-3 and 2-4 pulses. Vector 4-2 resulting signal represents the vector of the resulting signal having the same phase as the vector 4-1 initial signal, and the above-mentioned threshold power. Vector 4-3 signal compensation represents the vector of the signals I1 and Q1 of compensation issued by the unit 3-2 calculation of compensation signals in Figure 3. The outer solid circle denotes the threshold power and the inner dashed circle denotes the average power of the source signals. In this case, the vector of 4-3 receive compensation signal by subtracting the vector 4-1 initial signal from the vector 4-2 of the resulting signal.

Detect the crystals compensation produced using the above process of defining the phases of output signals equal to the phases of the source signals have the least power among all compensation signals that reduce OPSM source signals.

The signals I1 and Q1 served on the compensation blocks 3-10 and 3-11 determining the maximum signal in-phase and quadrature channels.

If the pulses applied to the inputs of filters-shapers 3-12 and 3-13 of the pulses of the maximum signal in-phase and quadrature channels, have the same polarity and consecutive non-zero values at each sampling period, the result of the processing performed by the filter shapers 3-12 and 3-13 pulses, these pulses are superimposed and have signal levels, higher compared to the signal levels of compensation. Output signals I2 and Q2 filters-shapers 3-12 and 3-13 of the pulses of the maximum signal in-phase and quadrature channels is summed with the output signals I3 and Q3 units 3-14 and 3-15 delay signal adders 3-16 and 3-17, which can cause additional distortion of the signal.

To solve this problem blocks 3-10 and 3-11 determine the maximum signal level retain the pulses of the compensation signals having the same polarity and maximum levels relative to the pulses urovnem signal among signals of compensation, taken at each sampling period, while setting the remaining signals of compensation equal to 0.

That is, blocks 3-10 and 3-11 determining the maximum signal in-phase and quadrature channel select signals compensation, with the highest levels of the sequentially received signals of compensation for each sampling period. Then the filters-shapers 3-12 and 3-13 of the pulses of the maximum signal in-phase and quadrature channels limit the compensation signals with the highest level of the desired bandwidth.

As described earlier, filters, conditioners 3-12 and 3-13 pulses the maximum level of the signal performs the function of suppressing the increase of the UCS and out-of-band distortion by limiting the bandwidth of the input signals of the desired bandwidth. Therefore, they can represent filters with finite impulse response (FIR filters or filters with infinite impulse response (IIR filters)designed to restrict the input signals, the bandwidth of the output signals I3 and Q3 units 3-14 and 3-15 signal delay.

Figure 5 illustrates the structure of the filter-driver 3-12 (or 3-13) pulses the maximum signal level, which is the FIR filter. According to Figure 5, the signal coming from the block, 3-10 definition poppy is kalinago level signal, delayed by delay blocks with 5-1 through 5-4. The signals at the inputs and outputs of the delay blocks with 5-1 through 5-4 are multiplied by the coefficients c0withnin blocks multiplication with 5-5 through 5-8. The adder 5-9 summarizes the output signals of multiplier units with 5-5 5-8 and outputs the sum Century For receiving the input signal from filter-driver 3-12 (or 3-13) pulse maximum signal level controller 2-8 power generates signal I2 (or Q2) within the desired frequency band.

Returning to Figure 3, the blocks 3-14 and 3-15 delay delay of the source signals in-phase and quadrature channels at a predetermined time. This time delay is the time required for the passage of the original signal in-phase and quadrature channels from block 3-1 definitions of scale through filters-shapers 3-12 and 3-13 of the pulses of the maximum signal level.

Adders 3-16 and 3-17 summarize the output signal I3 of the block 3-14 delay output signal I2filter-driver 3-12 pulse maximum signal level and the output signal Q3 of the block 3-15 delayed output signal Q2filter-driver 3-13 pulse maximum signal level. The signals I2 and Q2 is the compensation signals with the highest levels after treatment in the filters-shapers 3-12 and 3-13 of the pulses of the maximum signal level. Therefore, the output signals of the sum is atarov 3-16 and 3-17 compensated so they have the power required for the linearity of the amplifier 2-6 power.

6 is a corresponding variant of implementation of the present invention a block diagram of an algorithm illustrating the operation of the controller 2-8 power in General. According to Fig.6, the block 3-1 determine the scale at the stage 6-1 measures the levels of the source signals in-phase and quadrature channels received from the filters-shapers 2-3 and 2-4 pulses are in-phase and quadrature channels, and calculates the instantaneous power P(=I2+Q2), and on the stage 6-2 compares the instantaneous power P with the threshold power Pthreshold. If the instantaneous power P is less than or equal to the threshold power Pthresholdon stage 6-9 determine the scale factor equal to 1. If the instantaneous power P is greater threshold power Pthresholdthen at step 6-3, the scale factor determined according to a previously saved table scale or equation (2).

Unit 3-2 calculation of compensation signals on the stage 6-4 receives output signals having the same phase as the original signal in-phase and quadrature channels, and above the threshold power, by multiplying the original signal in-phase and quadrature channels on the scale factor and phase 6-5 calculates the signals I1 and Q1 compensation by the subtraction of the source signals in-phase and quadrature channels of the result signals. The signals I1 and Q1 compensation is used to achieve the desired OPSM.

At step 6-6 blocks 3-10 and 3-11 determine the maximum signal level to determine the compensation signal with the highest level through repetition of steps 6-1 through 6-5 on each sampling period. At stage 6-7 filters-shapers 3-12 and 3-13 of the pulses of the maximum signal level is designed to limit the transmission bandwidth of the compensation signal with the highest level.

At the stage of 6-8 adders 3-16 and 3-17 summarize the output signals of filters-shapers 3-12 and 3-13 of the pulses from the source signals in-phase and quadrature channels, detainees blocks 3-14 and 3-15 delay. In the result, the values OPSM mentioned amounts offset to the desired level.

7 to 12 illustrate the power produced by the controller 2-8 power. Fig.7 illustrates the levels of the signals in-phase and quadrature channels, measured after processing filters-shaper pulse in-phase and quadrature channels at each sampling period, and Fig illustrates the instantaneous levels of R (=I2+Q2) the capacity of the selected signals in Fig.7.

Fig.9 illustrates the pulse output signals of the inphase and quadrature channels, obtained by multiplying the original signal in-phase and quadrature channels, the region is giving instant power higher threshold power, the scale factors calculated at each sampling period, and Figure 10 illustrates the pulse signals to compensate for phase and quadrature channels, obtained by subtracting the pulse source signals in 7 pulse output signals in figure 9 at each sampling period. It should be noted that the pulses of the compensation signals have a phase opposite to the phase of the source signals and output signals.

11 illustrates the pulse signals to compensate for phase and quadrature channels with the highest levels relative to the pulse level 0 signal among the pulse signals of compensation on Figure 10. Fig illustrates signals to compensate for phase and quadrature channels with the highest levels of the processed filters-shaper pulses, and the power levels of these signals. The compensation signals in-phase and quadrature channels Fig are summed with the original signal in-phase and quadrature channels 7 in the adders 3-16 and 3-17. In the output signals of the adders 3-16 and 3-17 are values OPSM required for amplifier 2-6 power.

The second option exercise

The second variant implementation of the present invention is applied to the aircraft from the system Moby who enoy communication supports lots of bass.

Fig is a block diagram corresponding to the second variant of implementation of the present invention the transmitter BS from the mobile communication system that uses a lot of bass.

According Pig, the transmitter includes a block 13-1 channel devices, the unit 13-2 filters-pulse shapers and power 13-4 power. The feature is that the controller 13-3 power that supports a variety of bass, which is placed between the block 13-2 filters-pulse shapers and amplifier 13-4 power to regulate values OPSM source signals LF.

When the operation unit 13-1 channel devices contains many groups of channel elements corresponding to the bass frequencies, and each group of channel elements includes a channel device, similar in configuration to the device group 2-1 channel elements of figure 2, and performs coding, modulation and the formation of channels for each signal LF baseband. Unit 13-1 channel device controls each WOOFER independently. Unit 13-2 filters-shapers pulse contains many filters-shapers pulse in-phase and quadrature channels and limits the bandwidth of the signals in-phase and quadrature channels, issued by the unit 13-1 channel device the TV for each WOOFER. The output signals of the unit 13-2 filters-shapers of pulses fed to the input of the controller 13-3 power that supports a variety of bass.

The transmission path of signals with lots of bass like the signal path with one WOOFER in Figure 2. Namely, the controller 13-3 power that supports a variety of bass, outputs a signal that has been the power control input signal high OPSM to ensure stable operation of the amplifier 13-4 power. The amplifier 13-4 power amplifies the output signal of the controller 13-3 power that supports a variety of bass, to a level sufficient for transmission of this signal to all MS in the zone of coverage of the considered cell cell.

Fig is a detailed block diagram corresponding to the second variant of implementation of the present invention controller 13-3 power that supports a variety of bass. According Pig, the controller 13-3 power that supports a variety of bass, composed of unit 14-1 definitions of scale, multiple controllers 14-3 and 14-10 - 14-11 power adder 14-12. Controllers 14-3 and 14-10 - 14-11 power to regulate OPSM signal each WOOFER in a manner analogous to the method according to 6, except that the scale factor for each LF is calculated in correlation with scale factors of signals from other bass.

<> Unit 14-1 determine the scale takes the original signals I1, Q1, I1, Q1,...,IN, QNwith many bass through the respective blocks squaring and calculates the levels of these signals at each sampling period. Unit 14-2 calculate the scale of the unit 14-1 determine the scale calculates scale factors for a variety of bass, using the levels of the respective signals. The scale factors are determined according to a previously saved table size is calculated by equation (2).

Controllers 14-3 and 14-10 - 14-11 power to perform the corresponding LF the same operations as the controller 2-8 power on 6. The following is a description of the controller 14-3 capacity as the representative of all the considered controllers power.

Block 14-4 calculation of compensation signals from the controller 14-3 power receives output signals of the inphase and quadrature channels by multiplying the original signal I1and Q1in-phase and quadrature channels on the scale factor S1LF(1)obtained from block 14-1 definitions of scale, and calculates the compensation signals by subtracting the original signal I1and Q1in-phase and quadrature channels of the above-mentioned output signals. Block 14-5 defining m is ximango signal selects the signal compensation with the highest levels of relative signal level 0 signal among signals of compensation, taken from block 14-4 calculation of compensation signals at each sampling period, while asking other signals compensation equal to 0. The selected signals served on the compensation filter driver 14-6 impulses.

At the same time block 14-7 delay delays the original signal I1and Q1in-phase and quadrature channels, and the adder 14-8 summarizes these delayed signals with the output signals of the filter-driver 14-6 pulses, thereby forming the signals that have been power control. Converter 14-9 frequency increases the frequency of the signal for which was performed capacity management, to the frequency of the RF signal corresponding to LF(1), using for each bass is different from other high frequency.

Controllers 14-10 - 14-11 power function similarly and give signals with LF(2) LF(N). The adder 14-12 sums the output signals of the controllers 14-3 and 14-10 - 14-11 power and outputs the sum to the amplifier 13-4 power.

Fig illustrates the output signal of the adder 14-12 from the system that supports three bass. According Pig, position 15-1, 15-2 and 15-3 denote the circle, the radii of which are the levels of the source signals LF(1), LF(2) LF(3). Position 15-5 denotes a circle, the radius of which is the level of the reference signal, which obviously satisfies the requirement OPSM, ele is " on the amplifier 13-4 power. Frequency source signals are related by the following relation: LF(1)<LF(2)<LF(3). Due to the different frequency bands are combined signal LF(1) LF signal(2) gives the circumference of 15-2 with the center belonging to the circle 15-1, and the combination of low signal(2) signal LF(3) - circumference 15-3 with the center belonging to the circle 15-2.

Changes in the level of low signal(1) is faster than the signal strength of the LF(2), and the change of signal level LF(2) faster than LF(3). Therefore, the instantaneous level of the signal for each WOOFER is not constant, and varies periodically with the appropriate circle. Consequently, the maximum output signal of the adder 14-12 can be represented by a point 15-4. The maximum value represents the sum of the signal levels of all bass. To satisfy the condition that the sum of the instantaneous level of the signal must be less than the threshold level signal, it is necessary to determine the scaling factors so that the output signal of the adder 14-12 lay within the circle 15-5.

Thus, if the sum of the instantaneous levels of the source signals for each LF is less than or equal to the threshold signal level, the controller 13-3 power that supports a variety of bass, sets the scale factors for all of NP is equal to 1. On the other hand, if this sum is greater than the threshold level C is Nala, then calculate the appropriate scale factor. Here for all HF apply the same scale factor, or for each WOOFER is used different from the other scale factor.

If for each WOOFER features different from other scale factor, then this means that LF have different priorities or classes of service), that is, the priority levels. Thus, the BS can assign each LF a different priority level. For example, the CDMA2000 EV-DO (data exchange) features the LF related to the service mdcr first generation, from the LF related to the high-speed data services. As LF, supporting high-speed data services that are sensitive to the quality of the transmitted signal due to the characteristics of this service, it should have a higher priority compared to LF, support mdcr first generation.

Fig is a block diagram of an algorithm illustrating the process of computing unit 14-2 calculate the scale single scale factor for N bass, with the same priority level. According Pig, the instantaneous level of the signal LF(1) is equal to the square root of the sum of the square of the level of the original signal I1in-phase channel LF(1) and the square of the level of the original signal Q1quadrature channel LF(1) . After all LF calculated instantaneous levelssignal phase 16-1 their sum to obtain the maximum output signal of the adder 14-12.

On stage 16-2 valuecompared with predetermined or calculated thresholdsignal. Ifless than or equal toon stage 16-3 scale factors for all bass set equal to 1. Ifmoreon stage 16-2 calculate the scale factor S according to the following formula:

The scale factors S served on blocks 14-4 calculation of compensation signals, where they are used to signal suppression in the case when the source signals have the maximum possible signal levels.

Scale factors for N LF can be calculated using the weighting factors and threshold signal levels in accordance with classes of service.

In the previous method, the signal of each WOOFER has appointed different from other weight coefficient in order to calculate the scale factor for this bass.

According Pig, the instantaneous level of the signal LF(1) is equal to the RMS is Tomo root of the sum of the square of the level of the original signal I 1in-phase channel LF(1) and the square of the level of the original signal Q1quadrature channel LF(1). After all LF calculated instantaneous levelssignal phase 17-1 their sum to obtain the maximum output signal of the adder 14-12

On stage 17-2 valuecompared with predetermined or calculated thresholdsignal. Ifless than or equal toon stage 17-3 scale factors for all bass set equal to 1. Ifmore,on stage 17-4 in accordance with the service class LF(1) calculate a weighting factor αiLF(1). Weighting factor αiis the weighting factor for the i-th LF. The source signals for all bass with assigned weights written asGreater weight should be assigned to the LF with a higher priority. The weight of the bass can be defined as an indicator of the priority of this bass. If all LF divided by categories such as class 1 service or class 2 service, and if class 1 service and eat higher priority than class 2 service, all LF relating to class 1 service, assign a weighting factor of 2, and all LF relating to class 2 service - weighting factor 1.

Then at step 17-5 calculates the overall scale factor Stotalaccording to the following formula:

On stage 17-6 scale factor Sicalculated by multiplying the total scale factor Stotalthe corresponding weighting factor αi.

Corresponding to the frequencies of the bass scale factors served on blocks 14-4 calculation of the compensation signals. Weighting factors affect the determination of scaling factors for bass frequencies, and transmit power low signal with a higher priority is limited to a lesser extent. Therefore, maximized the efficient use of available transmission capacity.

Now with reference to Fig and 19 describes the method of calculating the scaling factors in accordance with classes of service. According to this method, the unit 14-2 calculate the scale sets for each bass is different from the other threshold level signal.

Namely, at first many bass in descending order are divided by categories such as classes of service from 1st to k-th, and for each WOOFER is ustanavlivaut threshold signal.is the threshold level for the i-th LF corresponding to its class of service and a high threshold signal set to a higher class of service. Sumthreshold signal levels less than or equal to the total thresholdsignal required in this system.

In the CDMA2000 EV-DO high-pass, low support high-speed data transmission, and bass, support mdcr first generation, share by categories such as class 1 service class 2 service, respectively.

According Pig, the threshold signal levels belonging to the class 1 service class 2 service, represented by circles 18-1 and 18-2, respectively. Consequently, the outer circumference on Fig represents the total thresholdsignal.

According Pig, the instantaneous level of the signal LF(1) is equal to the square root of the sum of the square of the level of the original signal I1in-phase channel LF(1) and the square of the level of the original signal Q1quadrature channel LF(1). After all LF calculated instantaneous levelssignal phase 19-1 their sum is irout to obtain the maximum output signal of the adder 14-12

On stage 19-2 valuecompared with a preset (or calculated) thresholdsignal. Ifless than or equal toat step 19-3 scale factors for all bass set equal to 1. Ifmorethescale factors for each LF is calculated in accordance with its priority level.

First on stage 19-4 averageinstantaneous level of the signal frequency WOOFER with class 1 service is compared with the threshold levelsignal for class 1 service. Ifmoreon stage 19-5 scale factor for frequency WOOFER with class 1 service is calculated as. On the other hand, ifless than or equal tothen the scale factor is set to 1 and the new value of the threshold level signal for frequency WOOFER with class 2 service is calculated on the stage as 19-6with thein order to assign the remaining frequencies from LF to class 1 service capacity the bass frequencies with class 2 service and thereby improve the efficiency of power use.

Similarly, at step 19-7 averageinstantaneous level of the signal frequency WOOFER with class 2 service compare with the new thresholdsignal for class 2 service. Ifmore new values ofon stage 19-8 scale factor for frequency WOOFER with class 2 service is calculated as. On the other hand, ifless than or equal to the new valuescale factors are set equal to 1 and the new value of the threshold level signal for frequency WOOFER with class 3 service is calculated on the stage 19-9 as

When 19 within 10 stages, 19-11 and 19-12 defined scale factor for frequency WOOFER with the lower class k service, scale factors served on blocks 14-4 calculation of the compensation signals. The described control threshold signal levels guarantees a minimum performance in accordance with the characteristics of each signal LF.

In accordance with the present invention described above, (1) without the Tr is Yes, the implement controller power for a variety of systems, including mdcr a broader spectrum direct sequence (mdcr-PP), broadband mdcr (SMDR) and mdcr with many carriers (mdcr-MN), and use it in conjunction with the correction pattern distortion; (2) in systems such as mdcr, you can change the inefficient operation of the power amplifier due to the high value OPSM resulting from the sum of the control signals and user data to multiple users; (3) the performance degradation is minimized without the use of expensive power amplifiers, which lowers overall system cost; (4) in mobile communication systems, especially those that support a lot of bass, you can guarantee a minimum performance in accordance with the characteristics of each signal LF during transmission of signals with lots of bass, and to maximize the efficient use of capacity through the regulatory process scale factor for each signal LF.

Despite the fact that the present invention has been presented and described with reference to certain preferred ways of its implementation, an expert in this field technicians will agree that various changes in form and details may be made without departure from the essence and about the EMA claims of the present invention, which is defined by the following claims.

1. Device for control of transmit power in a mobile communication system supporting a single assigned frequency (LF), containing:

group channel device designed to signal the baseband in-phase (I) channel and a signal of a baseband quadrature (Q) channel data from each channel;

two filter-driver pulses intended for filtering and pulse shaping signals to baseband;

the controller power, designed to regulate the ratio between peak-to-average power (OPSM) signals passed filtering and shaping of the pulses, in accordance with the threshold power required for linear power amplification;

the frequency Converter is designed to convert signals that have been managing power with increasing frequency in the high frequency (HF) signals and outputting these RF signals.

2. The control device for power transmission according to claim 1, in which the controller power block contains the scale is intended for receiving the source signal in-phase and quadrature channels of the filter-shaper pulses, calculate the instantaneous power and the outcome of the output signals of the inphase and quadrature channels at each sampling period, comparison of instantaneous power threshold power and determination of scaling factors in accordance with the comparison results;

the computing unit signal compensation designed to calculate the resulting signals by multiplying the original signal in-phase and quadrature channels on the scale factors and the calculation of compensation signals by subtracting the original signal in-phase and quadrature channels of the result signals;

two unit delay signal, intended to delay the original signal in-phase and quadrature channels on the time required by the computing unit signal compensation and unit definition scale of their operations;

two blocks determine the maximum signal level for the intended signal receiving compensation from the computing unit signals the compensation for each sampling period and the signal selection compensation with maximum levels;

two filter-driver pulses the maximum signal level is designed for filtering and pulse shaping of the selected signal compensation with maximum levels; and

two adder designed for summing the delayed signals with the signals of compensation, which passed the filtering and shaping and the heartbeats.

3. The control device for power transmission according to claim 2, in which the blocks determine the maximum signal level select signal compensation with maximum levels among consecutive non-zero signal compensation.

4. The control device for power transmission according to claim 2, in which the scale factors determined by the following equation:

if the instantaneous power ≤ power threshold, then the scale factor = 1;

if the instantaneous power > threshold power,the scale factor =

5. The control device for power transmission according to claim 2, in which the threshold power is determined by the following equation:

where Rthreshold- power threshold, PAVG- average power in a mobile communication system, and the power losses represent the ratio of the maximum power required to achieve linear amplification, medium power.

6. The method of controlling the transmit power in a mobile communication system supporting a single assigned frequency (LF), which includes the following steps:

form the signal to baseband in-phase (I) channel and a signal of a baseband quadrature (Q) channel data from each channel;

perform the filtering and shaping of the pulse signals to baseband;

adjust the peak-to-average power (OPSM) signals passed filtering and shaping of the pulses, in accordance with the threshold power required for linear power amplification; translate signals that have been managing power with increasing frequency in the high frequency (HF) signals and generates these RF signals.

7. The method according to claim 6, in which the phase regulation OPSM includes the steps consisting in the fact that

take the original signals, the filtered and shaping of the pulses, at each sampling period to calculate the instantaneous power of the source signals passed filtering and shaping of the pulses and determine the scale factors by comparing the instantaneous power with a threshold power;

calculate the resulting signals by multiplying the original signal by the scale factors, and calculates the compensation signals by subtracting the original signal from the output signals; and

combine the compensation signals from the source signals, which passed the filtering and shaping of the pulses.

8. The method according to claim 7, which further includes the steps consisting in the fact that

at each sampling period p is inimum compensation signals and select signals compensation with maximum levels;

perform the filtering and shaping of the pulses of the selected signal compensation with maximum levels before combining.

9. The method according to claim 8, in which the compensation signals with the maximum levels choose among consecutive non-zero signal compensation.

10. The method according to claim 7, which further includes the step consisting in the fact that the source signals are delayed for a predetermined time so that by the time they can be combined with the selected compensation signals these signals coincide in phase.

11. The method according to claim 7, in which the scale factors determined by the following equation:

if the instantaneous power ≤ power threshold, then the scale factor = 1,

if the instantaneous power > power threshold, then the scale factor =

12. The method according to claim 8, in which the threshold power is determined by the following equation:

where Rthreshold- power threshold, PAVG- average power in a mobile communication system, and the power losses represent the ratio of the maximum power required to achieve linear amplification, medium power.

13. Device for control of transmit power in a mobile communication system that supports a variety called uchennyh frequency (LF), contains:

many groups channel devices belonging to each of the LF and designed for generating signals of the baseband in-phase (I) channel signal and the baseband quadrature (Q) channel data from each channel;

many filters-shapers pulse in-phase and quadrature channels intended to limit the bandwidth of the signals in-phase and quadrature channels, given by the channel groups of devices for each bass; and

controller power WOOFER, designed to regulate the ratio between peak-to-average power (OPSM) signals passed filtering and shaping of the pulses, in accordance with the threshold power required for linear power amplification.

14. The control device transmit power indicated in paragraph 13, in which the controller power LF contains:

unit definition scale, designed to receive the source signals in-phase and quadrature channels corresponding to the bass frequencies, the filters-shapers pulses, calculate the instantaneous power of the source signals in-phase and quadrature channels at each sampling period, comparing the instantaneous power with the threshold power and the determination of scaling factors in accordance with the result of the Atami comparison;

many controllers power corresponding to the frequency WOOFER and intended to adjust the value OPSM source of LF signals using scale factors; and

the adder designed for summing the output signals of the controllers power.

15. The device power control of the transmission 14, in which each of the controllers of power contains:

the computing unit signal compensation designed to calculate the resulting signals by multiplying the original signal in-phase and quadrature channels on the scale factors and the calculation of compensation signals by subtracting the original signal in-phase and quadrature channels of the result signals;

the unit delay signal that is designed to delay the original signal in-phase and quadrature channels on the time required by the computing unit signal compensation and unit definition scale of their operations;

the adder designed for summing the delayed signals with the signals of compensation.

16. The control device transmit power indicated in paragraph 15, in which each of the controllers of power further includes:

the block determining the maximum level of the signal intended for reception of signals to compensate for the emission at each sampling period and the signal selection compensation with maximum levels;

filter driver pulses the maximum signal level is designed for filtering and pulse shaping of the selected compensation signals with the maximum levels.

17. Device for control of transmit power in clause 16, in which determining the maximum level of signal selects the signal compensation with maximum levels among consecutive non-zero signal compensation.

18. The device power control of the transmission 14, in which if the set LF is the same class of service, each of the scale factors are determined according to the following equation:

where Ri(i=1, 2,..., N) is the instantaneous power of the signal of the i-th LF, Rthreshold- power threshold, and Si- the scale factor for the i-th LF.

19. The device power control of the transmission 14, in which if many bass has different classes of service, each of the scale factors are determined according to the following equation:

where Si- the scale factor of the i-th LF (i=1, 2,..., N), αI- weighting factor assigned to the i-th LF, Rthreshold- power threshold, a Pi- instantaneous power signal of the i-th LF.

20. The device power control of the transmission 14, in which the ω if the set LF has different classes of service, each of the scale factors are determined according to the following equation:

where Ri- instantaneous power (i=1, 2,...,N),- power threshold corresponding to the service class of the i-th N4 and Si- the scale factor for the i-th LF.

21. The control device transmit power by claim 20, in which if the signal is some bass with a higher class of service than the signal of the i-th LF has a scale factor equal to 1, then the new value of the threshold signal power of the i-th LF is calculated by summing the i-th threshold powerwith the amount of power remaining from the threshold power of the bass, which has a higher class of service.

22. Device for control of transmit power in item 21, in which the remaining amount of power is the difference between the threshold power and the instantaneous signal power WOOFER with a higher class of service.

23. The device power control of the transmission 14, in which the threshold power is determined by the following equation:

,

where Rthreshold- power threshold, PAVG- average power in a mobile communication system, and the power losses represent the ratio of the maximum of the power, required to achieve linear amplification, medium power.

24. The method of controlling the transmit power in a mobile communication system that supports a variety of assigned frequency (LF), comprising the following steps:

for each form LF signal to baseband in-phase (I) channel and a signal of a baseband quadrature (Q) channel data from each channel;

perform the filtering and shaping of the pulse signals to baseband frequencies corresponding to the frequencies LF;

adjust the peak-to-average power (OPSM) signals passed filtering and shaping of the pulses, in accordance with the threshold power required for linear power amplification, and give signals that have been regulation OPSM, in the HF range.

25. The method according to paragraph 24, in which the phase regulation OPSM includes the following steps:

take the original signals each LF, past the filtering and shaping of the pulses, at each sampling period, calculate the instantaneous power of the source signals passed filtering and shaping of the pulses, and through a comparison of the instantaneous power with a threshold power determine the scale factors for a given LF;

regulate OPSM source signals LF the BL is using a scaling factor;

combine the signals LF, have been regulation OPSM.

26. The method according A.25, by which stage regulation OPSM includes the following steps:

calculate the resulting signals by multiplying the original signal LF on scale factors, and calculates the compensation signals by subtracting the original signal LF of the result signals; and

summarize the compensation signals with the original signal.

27. The method according to p, which further includes the following steps:

at each sampling period accept the compensation signals and select signals compensation with maximum levels;

perform the filtering and shaping of the pulses of the selected signal compensation with maximum levels before summation.

28. The method according to item 27, on which the compensation signals with the maximum levels choose among consecutive non-zero signal compensation.

29. The method according to p, which further includes a stage on which the original signal delayed for a predetermined time so that by the time their summation with the selected compensation signals these signals coincide in phase.

30. The method according A.25, according to which if the set LF is the same class of service, each of the scale factors are determined according to the trail is the overarching equation:

where Ri(i=1, 2,..., N) is the instantaneous power of the signal of the i-th LF, Rthreshold- power threshold, and Si- the scale factor for the i-th LF.

31. The method according A.25, which if many bass has different classes of service, each of the scale factors are determined according to the following equation:

where Si- the scale factor of the i-th LF (1=1, 2,..., N), αI- weighting factor assigned to the i-th LF, Rthreshold- power threshold, a Pi- instantaneous power signal of the i-th LF.

32. The method according A.25, which if many bass has different classes of service, each of the scale factors are determined according to the following equation:

where Ri- instantaneous power (i = 1, 2,..., N) the i-th NP- power threshold corresponding to the service class of the i-th N4 and Si- the scale factor for the signal of the i-th LF.

33. The method according to p, whereby if the signal is some bass with a higher class of service than the signal of the i-th LF has a scale factor equal to 1, then the new value of the threshold signal power of the i-th LF is calculated by summing the i-th threshold power ( with the amount of power remaining from the threshold power of the bass, which has a higher class of service.

34. The method according to p, in which the remaining amount of power is the difference between the threshold power and the instantaneous signal power WOOFER with a higher class of service.

35. The method according A.25 on which the threshold power is determined by the following equation:

,

where Rthreshold- power threshold, PAVG- average power in a mobile communication system, and the power losses represent the ratio of the maximum power required to achieve linear amplification, medium power.



 

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