Station interference to radio communications

 

The invention relates to the field of radio and can be used in the development of new and modernization of existing plants interference to radio communications. The technical result of the invention is to provide opportunities for continuous maintenance of radio reconnaissance and suppression of radio communications the proposed station interference due to the correlation convolution and signal attenuation noise coming from the transmitting antenna (reflected from the underlying surface). The use of the proposed station interference linear frequency-modulated signal as a sighting interference and lo signal for further converting the frequency of the received signals allows for continuous reconnaissance of radio communications and minimizes noise. The weakening of the chirp interference is achieved by suppression in the stopband the filter and expansion of the amplitude-frequency spectrum at the output of the second mixer. Station interference to radio communications includes receiving antenna 1, faucets 2.1, 2.2, bandpass filters 3.1, 3.2, notch filter 4, the keys 9.1, 9.2, the receiver 5, the analyzer 6, the amplifier-limiter 7, a detector 8, the modulator 14, the amplifier 15, the transmitting antenna 16, the reference generator 10, d is le=" page-break-before:always;">

The invention relates to the field of radio and can be used in the development of new and modernization of existing plants interference to radio communications.

It is known device for the formation of interference for radio stations [U.S. patent No. 3953851, CL N 04 To 3/00, 1976], containing connected in series receiving antenna, mixer, parallel connected first receiving channel and the second receiving channel with unit delay block And the indicator, modulator, power amplifier and transmitting antenna, while the second input of the mixer is connected to the output of the amplifier.

To detect suppressed radio communications input to the mixer from the output of the power amplifier receives the signal of the local oscillator. This known device requires continuous power amplifier for radiation in the conduct of intelligence suppressed wireless links. Constant work on radiation reduces electromagnetic compatibility of the device forming interference to radio interference with radio-electronic means other purposes, the frequencies of which are within the swath.

The drawback of the device forming the interference signals for radio stations is low electromagnetic of kotoryj are within the swath.

Known station suppress radiotelegraph signals [U.S. patent No. 4214208, CL N 04 To 3/00, 1980], which contains a receive / transmit antenna, the output of which is connected in series through switch "round-trip", the receiver is connected to a regulated pulse generator, the output of which is connected with the second inputs of the switch "transfer" and the key, the second input is through the exciter is connected to the second output of the receiver, and the output of the key through the amplifier connected to the transmitting antenna.

To detect the emitted radiotelegraph signal transmitting-receiving antenna through the switch "transfer" is connected to the input of the receiver. The output of the controlled pulse generator is formed by a pulse corresponding to the end of a received high-frequency pulse Telegraph signal, which is used to control the switch "transfer" and key. The switch "transfer" disables the input of the receiver from the transmitting-receiving antenna, and the switch connects the output of the exciter to the input of the amplifier.

The disadvantage of this station interference is the inability reconnaissance radiotelegraph signals during radiation transmitter high-frequency UEMOA effect is station interference to radio communications [see Paly A. I. Electronic warfare. Means and methods of suppression and protection of electronic systems. - M. 1981, S. 56], consisting of series-connected two-way radio antenna, antenna switch, receiver, analyzer, generator noise voltage, modulator, power amplifier, the output of which is connected to the second input of the antenna switch.

For detection of the emitted radio signal transmitting-receiving antenna through the antenna switch is connected to the input of the receiver. Received radio signals from the output of the receiver is fed to the input of the analyzer. The analyzer determines the type of modulation, spectrum width, and other parameters of received signals. Upon detection of the suppressed signal from the output of the analyzer to the input of the device forming the interference signal, allowing the formation of a noise voltage. At the same time the antenna switch disables the input of the receiver from the transmitting antenna and connects it to the output of the amplifier.

The shortcoming is the inability continuity suppression and intelligence suppressed radio communications.

The technical result of the invention is the provision of opportunities for continuous vtci and signal attenuation, interference, coming from the transmitting antenna (reflected from the underlying surface).

This result is achieved in that in the known station interference to radio communications containing the receiving antenna, receiver, analyzer and connected in series modulator, a power amplifier and transmitting antenna between the receiving antenna and receiver connected in series introduced the first mixer, the first band-pass filter, connected in parallel notch filter with the first key, the second mixer and the second band-pass filter, between the first output of the analyzer and a second input of the first key typed connected in series amplifier-limiter and detector, and entered serially connected reference oscillator, frequency divider, the frequency setting unit, to the second input of which is connected to the second output of the analyzer, a linear frequency-modulated oscillator and a second key, a second input connected to the output of the detector, and the output of the second key is connected to the input of the modulator, and the second and third inputs of the linear frequency modulated generator connected to respective outputs of the frequency divider and the reference oscillator, and a fourth input linear frequency-modulated GE who are satisfied with the first input of the second key.

As interference is necessary to use a linear frequency modulated (chirp) signal. The width of the amplitude-frequency spectrum (frequency deviation), the chirp-signal interference (FP. chirp) is selected [see paly A. I. Electronic warfare. M: Voenizdat, 1974, 272 S., see S. 110, first paragraph above]:

FP. chirp=(2-3)FCR, (1)

whereFCRthe receiver bandwidth. The receiver bandwidthFCRconsistent with the width of the spectrum of the useful signalFWith.

Correlation convolution of the interference signal S1P. chirpat the input of the receiving antenna from the transmitting antenna (reflected from the underlying surface), occurs at the first mixer. The width of the amplitude-frequency spectrum minimized interferenceF1Pis determined from the vertical section of the body(, F) plane zero temporary mismatch=0, whereF - temporary and frequency mismatch, respectively, [Electronic systems is edited J. D. Shirman. - M.: ZAO MAQUIS, 1998. 828, see S. 428, the expression (18.10) and S. 437, Fig.18.7,b] by the formula

F1P=1/TThe chirp, (2)

where TThe chirpduration is minimized, the chirp-signal interference at the output of the first mixer.

So, for the duration of the chirp signal-interference TThe chirp=0,1 with the width of the amplitude-frequency spectrum interferenceF1Pthe output of the first mixer is 10 Hz.

The width of the amplitude-frequency spectrum of the useful signalFC. the chirpthe output of the first mixer expands on the value ofFThe chirp:

FC. the chirp=FThe chirp+FC. (3)

Amplitude-frequency characteristics of the first bandpass filter and a notch filter consistent with the amplitude-frequency spectrum of the useful signal |SWith(f)| and interference |S1P(f)|, respectively.

The bandwidth suppression notch filterFRFis selected from the condition

FRF=(23)FP.(4)

For LC notch filter attenuation shall be the and effective signal ToThe SWEAT.Within percent with the passage of the notch filter is determined by the formula

ToThe SWEAT.With=[FRF/(FThe chirp+FC)]100%, (5)

whereFRF- band width suppression notch filter. For example, for band suppression notch filter from (4) -FRF=30 Hz, a frequency deviation signal loFThe chirp=2104Hz and bandwidth of the useful signal -FC=104Hz loss ToSWEATfrom (5) will be approximately 0.1 percent of the input useful signal level.

In the second mixer demodulation (recovery) amplitude-frequency spectrum of the useful signal |SWith(f)| and the expansion of the amplitude-frequency spectra of the transformed spectrum residual signal interference |S11P. chirp(f)|.

The interference power P11P. chirpthe output of the second bandpass filter is attenuated ToDonkeytime:

PO.CM2=PREF.CM2/KDonkey, (6)

where KDonkey=F11P. chirp/F1Ala interference at the output of the second mixer;

F1P- the width of the amplitude-frequency spectrum of the residual noise signal at the input of the second mixer.

For example, for the width of the spectrum of the residue interference at the input of the second mixerF1P=50 Hz, and after their conversion in the second mixer spectrum width residues interferenceF11P. chirpapproximately 2104Hz, weakening To aDonkeyfrom (6) will be about 400 times, or 26 dB.

Then taking into account signal attenuation interference rejection filter on the value of over 30 dB and reducing the spectral power density of the interference due to the expansion of its spectrum |S11P. chirp(f)| second conversionDonkey=26 dB total attenuation interference is 56 dB.

The converted spectrum signals S11P. chirp(f) and SWith(f) is fed to the input of the second bandpass filter. Amplitude-frequency characteristics of the second bandpass filter only agreed with the spectrum of the useful signal |SWith(f)|.

The power of the useful signal RO.PPthe output of the second bandpass filter, without taking into account losses in the stopband of the filter exceeds the power of the useful signal ub>SG
PREF.CM1, (7)

where KSG=1+FC. the chirp/FC.

So, for the frequency deviationFThe chirp=2104Hz and the width of the amplitude-frequency spectrum of the useful signal at the output of the second bandpass filterFWith=104Hz coefficient of compression ToSGfrom (7) will be 3 times.

The power of the useful signal RO.PPtaking into account losses in the notch filter at the output of the second bandpass filter 4.2 is from the expression

PO.PP=|KSG-KSWEAT|PBX.CM1.(8)

For the obtained compression ratios on the spectrum ToSG=3 and losses ToSWEAT=0.001 modulus of the difference of the coefficients of (8) will be $ 2,999 times.

Thus, the proposed station with additional transformation on the frequency useful signals SWith(f) and interference SP. chirp(f) little or no loss ensures that the passage to the analyzer input signal is achieved by weakening collapsed on the spectrum of the chirp interference 56 dB or more, which allows for continuous reconnaissance and suppression lines radiosvjaz-frequency spectrum of the useful signal and the chirp interference at the receiver input, the output of the first and second bandpass filters and amplitude-frequency characteristics of the first bandpass filter, notch filter and the second bandpass filter.

Station radio interference (Fig.1) contains a receiving antenna 1, faucets 2.1 and 2.2, bandpass filters 3.1 and 3.2, the notch filter 4, a receiver 5, the analyzer 6, the amplifier-limiter 7, a detector 8, the keys 9.1 and 9.2, the reference oscillator 10, the frequency divider 11, the frequency setting unit 12, a linear frequency-modulated oscillator 13, a modulator 14, the amplifier 15 and the transmitting antenna 16.

And receiving antenna 1 through the first mixer 2.1, the first band-pass filter 3.1, connected in parallel notch filter 4 with the first key 9.1, the second mixer 2.2, the second band-pass filter 3.2, the receiver 5, the analyzer 6, the amplifier-limiter 7, a detector 8, the second key 9.2, modulator 14 and the amplifier 15 is connected to a transmitting antenna 16, with reference oscillator 10 connected in series through the frequency divider 11, the frequency setting unit 12, the second input is connected to the second output of the analyzer 6, and linear frequency-modulated oscillator 13 is connected to the first input of the second key 9.2 and second inputs of the first and second mixers 2.1 and 2.2, Voronenko frequency modulated generator 13 is connected to the output of the reference oscillator 10, the fourth input of the linear frequency-modulated oscillator 13 is a control input station interference, and the output of the detector 8 is connected with the second input of the first key 9.1.

To implement technical solutions can be used with standard commercial equipment. So, for example, mixers 2.1 and 2.2 represent the diode frequency Converter, made by balancing scheme [M. S. Shumilin, C. B. Kozyrev, V. A. Vlasov. Designing transistor cascades transmitters. Textbook for technical schools. - M.: Radio and communication, 1987. - 320 S., S. 178, Fig. 2.77].

Bandpass filters 3.1 and 3.2 can be made for the three band-pass filter [radio Transmitting devices. M. C. Balakirev, Y. C. of Vakhmyakov, A. C. Surikov and others/edited by O. A. pH. - M.: Radio and communication, 1982. - 256 S., S. 94, Fig. 4.12].

The notch filter 4 may be performed, for example, by the circuit LC notch filter of the sixth order [Aaal R. Reference calculation filters: TRANS. with it. - M.: Radio and communication, 1983, - 752 S., see S. 75, Fig.8.21].

The amplifier-limiter 7 is a double-sided limiter, made by the scheme [Galperin M. C. Practical circuitry in industrial automation. - Energoatomizdat, 1987. - 132 C., S. 131, Fig.3.20, in, EV Century. And. Domestic chip and foreign counterparts. Reference "SEC Microtech", 2000 - 375 C., S. 182, 211].

The detector 8 when converting a frequency-modulated signals can be performed, for example, on-chip series HP, and in the case of amplitude-modulated signals on chip series DA or CD [Perelman B. L., Shevelev Century. And. Domestic chip and foreign counterparts. Reference "SEC Microtech", 2000 - 375 C., S. 49, 204].

Keys 9.1 and 9.2 can be performed, for example, on the chip series CT (CCT) [Perelman B. L., Shevelev Century. And. Domestic chip and foreign counterparts. Reference "SEC Microtech", 2000 - 375 C., S. 193, 222].

Reference generator 10 is a pulse generator with quartz stabilization performed, for example, on-chip series KLN (C. N. Veniaminov, O. N. Lebedev, A. I. Miroshnichenko. Chips and their application: Ref. The allowance. - 3rd ed., revised and enlarged extra - M.: Radio and communication, 1989, 240 S., S. 210, Fig. 7.10, d].

The frequency divider 11 may be performed, for example, on-chip series CMIE [Perelman B. L., Shevelev Century. And. Domestic chip and foreign counterparts. Reference "SEC Microtech", 2000 - 375 C., S. 129, 81].

The frequency setting unit 12 can be performed by multiplex CX is alogi. Reference "SEC Microtech", 2000 - 375 C., S. 44, 89].

The chirp generator 13 is, for example, the circuit consisting of the generator phase-locked loop (PLL) [Design of radar receivers: Textbook. Manual for radio specialists of universities, A. P. Golubkov, A. P. Lukoshkin and others/edited by M. A. Sokolov. M: The High. HQ., 1984. - 335 S., S. 176, Fig. 6.28] and digital synthesizer, the chirp signal [Kochemasov C. N., Belov, L. A., Okoneshnikovo Century C. the Formation of signals with linear frequency modulation. - M.: Radio and communication, 1983. - 192 S., S. 55, Fig. 4.12]. The PLL provides accurate tuning frequency controlled generator under frequency reference chirp signal generated by the digital synthesizer, and reducing the level of noise in the signal, the chirp generator 13.

The inventive station radio interference (Fig.1) works as follows.

In the initial state, the notch filter 4 shorted shorted key 9.1. Reference generator 10 generates highly stable sequence of clock pulses with a repetition periodT. These pulses arrive at the corresponding inputs of the chirp generator 13 and the frequency divider 11. The frequency divider 11 is designed to generate pulses start the chirp signal. The repetition period impulse run the chirp signal received at the first input of the frequency setting unit 12 and the second input of the chirp generator 13. To the second input of the frequency setting unit 12 from the second output of the analyzer 6 is fed parallel binary code frequency setting. Write code to set the frequency at the first input of the chirp generator 13 is carried out upon receipt of each video impulse to the first input unit 12.

To reduce the power level, penetrating to the input of the receiving antenna 1, the transmitting antenna 16 with deployed 90 degrees by the polarization vector.

The exploration begins with receipt of the control signal at the fourth input chirp generator 13. The chirp output signal from the chirp generator 13 is supplied to the second input of the second key 9.2 and as a lo signal to the second inputs of the first and second mixers 2.1 and 2.2.

Amplitude-frequency spectrum of the chirp signal |SThe chirp(f)| at the output of the chirp generator 13 shown in Fig.2B.

From the output of the receiving antenna 1 of the useful signal SWith(f) is fed to the input of the first mixer 2.1. The amplitude-frequency spectrum of the useful signal |SC(f)| at the input of the first mixer 2.1 shown in Fig.2A. In the first mixer 2.1 SC(f) is converted by the frequency and extends along the spectrum on the value ofFThe chirp. The amplitude-frequency spectrum of the signal |SC. the chirp filter 3.1 and the first key 9.1 is fed to the input of the second mixer 2.2. The amplitude-frequency characteristic of the bandpass filter 3.1, is shown in Fig.2D. In the second mixer 2.2 there is a restoration of the original signal spectrum |SWith(f)| (Fig.2H). The recovered signal SWith(f) from the output of the second mixer 2.2 through the second band-pass filter 3.2 to the input of the receiver 5. The amplitude-frequency spectrum of the useful signal |SWith(f)| at the output of the second bandpass filter 2.2 shown in Fig.2K. 5 receiver amplifies and converts the frequency of the received signal. From the output of the receiver 5, the signal SWith(f) to the input of the analyzer 6. The analyzer 6 determines the type of modulation (manipulation), spectrum width, and other parameters of received signals [see paly A. I. Electronic warfare. Means and methods of suppression and protection of electronic systems. - M. 1981, S. 56].

The signal SWith(f) from the first output of the analyzer 6 through the amplifier-limiter 7 is fed to the input of the detector 8. A positive level from the output of the detector 8 is supplied to the inputs of the keys 9.1 and 9.2.

At the same time to adjust the average frequency chirp generator 13 from the second output of the analyzer 6 to the second input of the frequency setting unit 12 receives information about the frequency of a measured signal in the form of parallel dojchmajster 14. The modulator 14 generates the chirp interference on the frequency of a measured signal SWith(f). From the output of the modulator 14, the chirp interference through the power amplifier 15 is fed to the input of the transmitting antenna 16. The transmitting antenna 16 provides radiation in the space-frequency energy supplied by the feeder [see paly A. I. Electronic warfare. Means and methods of suppression and protection of electronic systems. - M. 1981, S. 57].

The input of the receiving antenna 1 along with the useful signal SWith(f) begins to act the part of the power of the chirp interference SlP. chirp(f) emitted by the transmitting antenna 16 (reflected from the underlying surface). The appearance of the spectra of the useful signal SWith(f) (solid line) and chirp interference SlP. chirp(f) (dotted line) shown in Fig.2B.

Useful signal SWith(f) and the chirp interference SlP. chirp(f) is fed to the input of the first mixer 2.1. In the first mixer 2.1 is the correlation convolution chirp interferencelP. chirp(f) the expansion of the spectrum of the useful signal SWith(f) (cm. Fig.2G). From the output of the first mixer 2.1 the converted signals through the first band-pass filter 3.1 arrive at the inputs connected in parallel notch filter 4 and the first key 9.1. A positive level and 3.1 and the input of the second mixer 2.2. The amplitude-frequency characteristic of the notch filter 4 shown in Fig.2E. From this time begins the suppression of the correlation collapsed on the spectrum of the chirp signal interference.

The width of the spectrum of the useful signalFC. the chirpthe output of the first bandpass filter 3.1 exceeds the bandwidth of rejectioFRFnotch filter 4 (see Fig.2D, e). From the analysis of expression (5) it follows that the useful signal SC. the chirp(f) little or no loss passes the notch filter 4. The appearance of the spectra of the useful signal |SC. the chirp(f)| and balances the chirp interference |SlP(f)| at the output of notch filter 4 shown in Fig.2ZH.

Useful signal SC. the chirp(f) and the remains of the chirp interference SlP. chirp(f) is fed to the input of the second mixer 2.2. In the second mixer 2.2 is the correlation convolution signal (restore the original spectrum of the signal |SC(f)|) and the extension of the residue spectrum chirp interference |S11P. chirp(f)|. The appearance of the spectra of the useful signal |SC(f)| (solid line) and residues chirp interference |S11P. chirp(f)| (dotted line) at the output of the second mixer 2.2 shown in Fig.2H. Useful signal SC(f) and the remains of the chirp stick bandpass filter 3.2 is shown in Fig.2i. The amplitude-frequency characteristic of the bandpass filter 3.2 consistent with the amplitude-frequency spectrum of the useful signal |SC(f)|.

To the input of the analyzer 6 receives the useful signal SC(f) and part of the remains of the chirp interference |S11P. chirp(f)|, which have passed through the second band-pass filter 3.2 (see Fig.2K).

Thus, the proposed station interference allows continuous logging of radio reconnaissance and suppression of radio communications.

Claims

Station interference to radio communications containing the receiving antenna, receiver, analyzer and connected in series modulator, a power amplifier and transmitting antenna, characterized in that between the receiving antenna and receiver connected in series introduced the first mixer, the first band-pass filter, connected in parallel notch filter with the first key, the second mixer and the second band-pass filter, between the first output of the analyzer and a second input of the first key typed connected in series amplifier-limiter and detector, and entered serially connected reference oscillator, frequency divider, the frequency setting unit, to the second input of which is connected the second is the output of the detector, and the output of the second key is connected to the input of the modulator, and the second and third inputs of the linear frequency modulated generator connected to respective outputs of the frequency divider and the reference oscillator, and the fourth input of the linear frequency modulated generator is managing entrance station interference, while the second inputs of the first and second mixers connected to the first input of the second key.

 

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