The correction method is complementary bearing in the system broadcast digital audio signal that is compatible with the amplitude - modulated signal

 

The invention relates to radio broadcasting and can be used for correction of the demodulated signal at the receiver is designed to work in the system broadcast a digital signal that is compatible with the amplitude-modulated signal. The method consists in including in that the update of correction coefficients used for the complementary signals is carried out by interpolation using the coefficients vector for complementary signals. The technical result - the loss prevention information transferred signals, unbalanced amplitude and neenteeimmicy phase. 4 C. and 23 C.p. f-crystals, 5 Il.

The present invention relates to radio broadcasting and, in particular, to methods and devices for correcting the demodulated signal at the receiver is designed for operation in the system of broadcasting a digital signal that is compatible with the amplitude-modulated signal.

The prior art broadcast of digital audio coding, allowing to achieve a higher quality reproduction of the transmitted signal is of high interest. In this direction proposed several approaches. One of the digital signals on a standard channel, AM broadcast. Broadcasting amplitude-modulated radio-frequency signal produced in the first frequency spectrum. Amplitude-modulated radio frequency signal includes the first carrier, the modulated analog signal program. Simultaneously broadcast on the totality of bearing signals using digital modulation in the frequency band that encompasses the first frequency spectrum. Each of the signals carrying pending digital modulation modulate digital signal program. The signals carrying the first group subject to digital modulation, placed in the first frequency spectrum, modulate the quadrature relative to the first carrier signal. The signals carrying the second and third groups, subject to digital modulation, outside of the first frequency spectrum, modulate both in phase and in quadrature with respect to the first carrier signal.

In relation to the broadcast of digital audio signal that is compatible with the AM signal, described in U.S. patent 5588022 (WO 95/24781), was derived waveform to achieve a sufficiently high speed data transmission through a digital signal and, at the same time, to avoid crosstalk in analog AM signal. Dialnum frequency division (MOCR).

Mono detectors household AM radios only respond to the envelope, but not on the phase of the received signal. Using digital modulation numerous bearing eliminates the need for a means of reducing the distortion envelope arising from the transfer of a group of signal. In U.S. patent 5859876 disclosed a method of reducing distortion of the envelope in the system broadcast digital audio signal that is compatible with the AM signal. Certain carrying a digital signal whose frequency above the carrier frequency of the analog AM signal, correspond to the bearing of the digital signal with frequency below the carrier frequency of the analog AM signal with the same frequency shift. Data and method of modulating their upper carrier digital signal and corresponding to the bottom of the carrier are such that the addition of bearing does not give the components, in-phase with the carrier, the analog AM signal. Arranged in such a way a pair of bearing of the digital signal are called complementary. This configuration provides substantial improvement in the quality of playback in analog AM receiver, cifrovoy broadcast signals compatible with AM signals.

In the receiver digital signal demodulated through quick conversions is the disclosed method, demodulation, when a broadcast digital audio signal that is compatible with the AM-signal (ACV AM), and for the modulation format for multiplexing orthogonal frequency division (MOCR), thanks to the use of dual processes fast Fourier transform to split the respective in-phase and quadrature components of a received digital signal format MOCR, undesirable crosstalk between analog signal and digital signals are minimized. To recover the data transmitted through the complementary bearing, use the output signal of the quadrature channel, and for recovering data transmitted through complementary bearing, use the sum of the signals obtained by processing components.

In the presence of dynamic changes in the characteristics of the channel received signal with multiple carriers need to adjust. Without such a correction detection signal would lead to significant distortions that impede the recovery information of the digital broadcast signal. Corrector increases the possibility of data recovery digital audio broadcasting. One such corrector disclosed in U.S. patent Hal, compatible with the AM signal, and the preservation of this form of the signal as a vector waveform. Then the checker processes the waveform by multiplying the vector form of the signal adjustment vector. This correction vector is formed by a set of correction coefficients, each of which initially assigns the specified value. Then the corrector compares each position of the processed vector waveform with the stored vector waveform. Corrector selects the signal quality is the position vector that is closest to the saved vector waveform. Preferably, the corrector contains the update tool of correction coefficients, which, using the vector form of the processed signal vector waveform and the stored vector waveform, provides protection from noise.

Corrector, presented in the patent 5633896 and patent 5559830 (WO 96/23374), the offset information is coming in the frequency domain in the form of a vector of the frequency domain. Each block of frequency domain information is stored as a data array. This vector data array is multiplied by a set of correction coefficients. The resulting work is Ivate each orientation vector of the adjusted signal. As the actual value signal choose the ideal value nearest to a given orientation of the vector. Vector solutions remain in the array of solutions. Using the received signal, the adjusted signal and the array of solutions, the evaluation unit calculates correction coefficients estimated values of the coefficients. Update frequency coefficients determines the security of the offset from the noise and the degree of convergence. The coefficients on different parts of the range can be updated with varying frequency, depending on the information about the mechanism of distortion.

Although the dual FFT allows to improve the performance of the system on the channel, which in the frequency range of complementary bearing has symmetry in the amplitude and symmetry in phase relative to the carrier frequency of the AM signal, but on the channels, unbalanced amplitude or neenteeimmicy phase, the information contained in the signals, unbalanced amplitude and neenteeimmicy phase, in the process of combining the output signals of the FFT complementary bearing is destroyed, which leads to the formation of incorrect control signal corrector. For this reason, you need a way demodulation, that, in such ostatecznie phase.

The present invention is to create an improved correction method and receivers that operate in this way.

Summary of the invention the Present invention provides the evaluation method of correction coefficients for complementary bearing and, at the same time, allows you to use the benefits of combining information of the output signals from FFT complementary bearing. The method involves the use of information transmitted through complementary bearing, to estimate, by interpolation, the correction coefficients for the complementary carriers.

The correction method that meets the present invention is used for processing a digital broadcast signal that is compatible with the amplitude-modulated signal containing amplitude-modulated radio-frequency signal characterized by the first frequency spectrum, and the amplitude-modulated RF signal has a first carrier modulated analog signal program, a set of signals carrying subjected to digital modulation posted in the frequency band covering the first frequency spectrum, and the first group of signals carrying, EE, and the second and third group of signals carrying subjected to digital modulation, contain complimentary bearing and are positioned outside of the first frequency spectrum. How is that form a first signal representing the in-phase components of the digital broadcast signal that is compatible with the amplitude-modulated signal, generate a second signal representing the quadrature components of the digital broadcast signal modulation compatible with the amplitude-modulated signal, using the first and second signals as the real and imaginary input signals to a fast Fourier transform performed on the first and second signals, for providing a set of converted signals representing data in the frequency domain, and process the converted signals by multiplying the converted signals to the correction vector and the adjustment vector is formed by a set of correction coefficients, and differs in that the upgrading of correction coefficients used for the complementary signals by interpolating the coefficients vector for complementary signals.

The invention also ohvatyvajushee the above described way, and radios that contains this device.

Brief description of drawings in order that the specialists in this field of technology was more understandable to the invention, the following description provided with reference to the accompanying drawings, in which: Fig. 1 is a diagram representing a composite signal consisting of a digital broadcast signal and an analog DM signal, corresponding to the prior art, having a bearing placed in accordance with the present invention; Fig.2 is a block diagram of the receiver, which can include concealer, acting in accordance with the present invention; Fig. 3 is a functional block diagram that illustrates the action of the demodulator and adaptive corrector in accordance with the present invention; Fig.4 and 5 are diagrams illustrating the amplitude-frequency characteristic corrector.

Detailed description of preferred embodiments the Present invention provides a correction method bearing in the broadcast signal, which contains the analog amplitude-modulated signal and a digital signal for transmission which uses the same scheme, channel assignment, and that the existing broadcasting analog AM signal. Method broadcast cifrovogo frequency of the main channel (ITOOK). This broadcast is carried out by passing the digital signal through the aggregate carrying modulated format MOCR, and some of them are modulated in quadrature with respect to the analog AM signal and placed in the spectral region in which the standard AM broadcast signal has significant energy. The remaining carrying a digital signal modulated in phase and in quadrature with respect to analog AM signal and are placed on the same channel as the analog AM signal, but in the spectral regions in which the analog AM signal has no significant energy. In the United States, as prescribed by the Federal communications Commission (FCC), the radiation of radio stations broadcasting in the AM band, subject to the mask signal, which is specified as follows: the level of radiation in the frequency bands located on either side of the carrier analog signal in the range from 10.2 kHz to 20 kHz, must be at least 25 dB below the unmodulated analog carrier signal, the level of radiation in the frequency bands located on either side of the carrier analog signal in the range from 20 kHz to 30 kHz, should be at least 35 dB below Samodurov is it an analog signal in the range from 30 kHz to 60 kHz, must be at least [35 dB+1 dB/kHz] below the level of the unmodulated analog carrier signal.

In Fig.1 presents the range of the broadcast signal of the digital audio signal and the amplitude-modulated signal, similar to what is used in accordance with the present invention. Curve 10 represents the spectral characteristic of the amplitude of the standard broadcast signal with amplitude modulation, the carrier which has a frequency f0. Mask radiation prescribed by the FCC, represented by position 12. Waveform format MOCR formed near the supporting data are posted to the f1= 59,535106/(131072) Hz or approximately 454 Hz. The first group of twenty-four bearing subjected to digital modulation, is in the frequency range (f0-12f1) to (f0+12f1) that illustrates the envelope, indicated in Fig.1 position 14. The level of most of these signals are reduced by 39.4 dB relative to the signal level of the unmodulated carrier DM signal in order to minimize crosstalk analog DM signal. To further reduce crosstalk apply this encoding digital information, which ensures orthogonality on Rel. omplimentary DFMN (binary phase shift keying), complementary CPMN (quadrature phase shift keying) or a complementary 32-Noah BM (quadrature amplitude modulation) and described in more detail in the previously discussed thoroughly review the application 08/671252. Modulation format complementary DFMN used for the inner pair of bearing a digital signal, f0f1to facilitate the recovery of the synchronization. The levels of these bearing set equal to -28 DBs. All other carriers belonging to this first group have a level -39,8 DBs and modulated using complementary 32-Noah BM for velocity encoding 48 and 32 kbit/s 8-e complementary FMN is used to modulate the carrier in the range of (f0-11f1) to (f0-2f1) and from (f0+2f1) to (f0+11f1for the coding rate 16 kbit/s Bearing (f0-12f1) and (f0+12f1) are used to transfer assistance data and can be modulated using complementary 32-KAM Noi for all three velocity encoding.

Additional groups carrying digital signals are placed outside of the first group. The need in quadrature the frequency of the analog DM signal. Bearing the second and third groups covered envelopes, respectively, 16 and 18, can be modulated using, for example, a 32-Noah CAM for speeds of 48 and 32 kbit/s and 8-s QPSK for speed 16 kbit/s For all speeds of coding levels bearing set equal to -30 DBs.

In Fig. 2 depicts a block diagram of a receiver intended to receive the composite analog and digital signals, shown in Fig.1. The antenna 110 takes the form of a composite signal containing digital and analog signals, and sends the signal to the normal input of the cascades 112, which may include RF preselector, amplifier, mixer and local oscillator. The inputs generates an intermediate frequency signal in line 114. The intermediate frequency signal passes through the circuit 116 automatic gain control to the generator 118 I/Q signals. The generator I/Q signals generates a common-mode signal in line 120 and the quadrature signal in line 122. In-phase channel output in line 120, is fed to an analog-to-digital Converter 124. Similarly, the quadrature channel output line 122, is supplied to another analog-to-digital Converter 126. The feedback signals on lines 120 and 122 are used to control circuit 116 automatic adjustment reinforced is highlighted in the output stage 142 and, then, on the loudspeaker 144 or other output unit.

An auxiliary filter 146 of the upper frequencies can be used to filter the in-phase components on line 128, in order to exclude the energy of the analog AM signal and provide a filtered signal on line 148. If the high-pass filter is not used, the signal on line 148 is the same as on line 128. The demodulator 150 receives digital signals on lines 148 and 130, and generates output signals on lines 154. These output signals are sent to the corrector 156, and then in block 158 of the filter data rate and data decoder. To obtain a higher signal to noise ratio (SNR) for the complementary bearing, output signals of the FFT for pairs of complementary bearing unite. The output signal of the decoder data serves to block 164 circuit reversed alternation and decoder for forward error correction for enhanced data integrity. Output the converted signal of the interleaver/schemas forward error correction is supplied to the decoder 166 of the original signal. The output signal of the decoder of the source signal subjected to the delay circuit 168 to compensate for the delay of the analog signal in the transmitter and to coordinate on-time analog and digital signals in the receiver. VIH, to generate a signal on line 162, which enters the output stage 142.

In Fig.3 depicts a functional block diagram that illustrates the operation of the demodulator 150 and adaptive corrector 156 in accordance with the present invention. In-phase (I) and quadrature (Q) signals on lines 148 and 130 to the inputs of the weighting scheme compactly supported function and removal of the guard interval. These signals can be obtained using the conversion items with decreasing frequency, similar to those shown in Fig. 2. You should use this finite weighing function to carry the digital signal remained orthogonal or at least the degree of reorthogonalize between the bearing digital signal was small enough not to degrade the system parameters. Was developed the method of using finite weighing function, which preserves the orthogonality between the carriers. According to a particular implementation variant of the method, the transmitter and receiver are used finite weighing function that has a view of the square root of the cosine. This finite weighing function provides the downturn in the first and the last seven samples of 135 samples that make up the sampling period. After the application is eating 129-th sample is added to the first sample, 130 sample stack with the second sample and continue to operate under this scheme until you add 135-th sample to the seventh sample. Received 128 points come in the FFT block. In some cases it may be useful to perform the operation of weighing using compactly supported functions and remove guard interval before processing by the filter 146 of the upper frequencies. The output signals of the circuits 151 weighing using compactly supported functions and remove guard interval enter the FFT block 153. The output signals of the FFT block are received on lines 154 to the coefficient multiplier 157. Coefficient multiplier operates with data in the frequency domain and regulates the amplitude and phase of each carrier subjected to modulation format MOCR to compensate for the effects of channel disturbances filters in the transmitter and the receiver, the transmit and receive antennas, and other factors and process that affect the amplitude and phase of the signal. Block 178 unites, as shown in Fig.3, the information moving pairs of complementary bearing, output on lines 174 and 176 of the coefficient multiplier. In the specific case, this Association can be done by averaging the data of the frequency region for each pair to totoy area. Carried out, thus, combining information transferred complementary bearing, increases the signal to noise ratio for the complementary carriers. This combined information for complementary bearing, as well as the output signals of the coefficient multipliers on lines 180 and 182 to complementary bearing shall be received by the processor 184, which determines which of the points of the frequency diversity was passed. These decisions, together with the previously adjusted points of diversity and the previous values of correction coefficients, are used to update the correction coefficients at block 186. To update the correction coefficients block 186 may use a known algorithm such as the method of least medium squares (MSC) or recursive method medium squares (RMS). The output signal of the offset 156, shown in Fig.2, may consist of a combination of the output signals on lines 174, 176, 180 and 182, or may consist of output signals on lines 185 and line 185 contain decisions about complementary and complementary bearing. Depending on the type of data needed for further processing, use the p>

In the patent 5559830, issued September 24, 1996, describes one mode of operation of the corrector, which implements the algorithm updates the correction coefficients. The present invention allows to improve the performance of the corrector and the update algorithm of correction coefficients by taking into account the effects that may occur when the correction coefficients are provided by the symmetry of the module or the symmetry of phase with respect to the Central frequency of the FFT.

If, for removal of the analog signal is in phase with the input signal FFT is passed through the high-pass filter, the output signal of the FFT, to which is applied the update algorithm of correction coefficients, acquires a certain symmetry properties. In particular, because of the complementary bearing, in-phase component of the input signal FFT has energy close to zero, then the output signal FFT for complementary bearing has a symmetry close to internetowej. The same property is true for the output signal of the decision on the symbols for the complementary carriers. Since the input signals of the update procedure correction coefficients are these two internetowych detect erotica - antisymmetric with respect to the Central frequency of the FFT. Therefore, the adjustment factors will not converge to the correct values when the adjustment factors should be asymmetric module or antisymmetric phase with respect to the Central frequency of the FFT. Fig. 4 illustrates an example of such a situation. For the case shown in Fig. 4, it is assumed that the amplitude-frequency response of the channel is asymmetric with respect to the Central frequency of the FFT. In fact, in Fig.4 shows the inverse of the amplitude-frequency characteristic 188 channel, because it should look like amplitude-frequency characteristic corrector. In Fig. 4 shows also feature 190, which can be obtained on the basis of the amplitude of the output signal of the offset. For clarity, the illustrated characteristic corrector shifted slightly upwards, so that it can be distinguished from the reverse characteristics of the channel. Note that in regions 192 and 194, corresponding complementary bearing, this characteristic coincides with the inverse characteristic of the channel. However, in the field 196, a corresponding complementary bearing, characteristic corrector turns out to be incorrect, because in this spectral, to resolve the analog signal prior to submission to the FFT block, the output signal of the FFT block for complementary bearing sachusetts due to leakage of the analog signal in the region complementary bearing closest to the carrier frequency of the analog AM signal. In addition, when the adjustment factors must possess symmetry module and symmetry in phase relative to the carrier of the analog AM signal, in the absence of a high-pass filter estimation of correction coefficients for complementary bearing are subjected to more noise than when using the high-pass filter. In addition, if the adjustment factors should not possess the symmetry module and symmetry in phase relative to the carrier frequency of the analog AM signal, the estimation of correction coefficients for complementary bearing is difficult due to the fact that the analog signal and the complementary bearing is not already separated, respectively, in-phase and quadrature components. To obtain the correct adjustment of the coefficients in static conditions, when you want the adjustment factors were asymmetric module and not antisymmetric phase Aulnay disturbances, often asymmetric module and neenteeimmicy phase with respect to the Central frequency FFT, occur at random and fleeting that it is not possible to adjust them by long-term averaging.

Therefore, regardless of whether you use a high-pass filter to eliminate the analog signal, adjustment factors for complementary bearing will be useless when the ideal adjustment factors for complementary bearing must be asymmetric module or participtation phase with respect to the Central frequency of the FFT.

To remedy this drawback it is possible to use interpolation of correction coefficients in the field of complementary bearing. When properly configured the control circuits of the receiver, such as schemes of automatic gain control (AGC) circuit carrier detect circuit and the detection of symbols, the center frequency of the FFT must comply with known constant amplitude and phase. Therefore, the information contained in the spectral regions 192 and 194 that are outside the area of 196 complementary bearing, can be used for prediction and evaluation of the correct adjustment coefficientmore. Coefficient multiplier 157 outputs the adjusted signals to complementary bearing on lines 180 and 182 and the adjusted signals for the complementary bearing on lines 174 and 176. The processor 184 solutions displays characters on line 187 decisions concerning only complementary bearing, unlike the case when the interpolation is not used and line 187 contain decisions on complementary bearing. The circuit 186 update correction coefficients updates the coefficients for complementary bearing. Then the coefficients for complementary bearing updated by interpolation using the known values for the center frequency of the channel and the values of the coefficients for complementary bearing. In Fig.5 shows an example when for determining corrective coefficients in the vicinity of the Central frequency of the channel used linear interpolation. From the graph you can see that, if the amplitude-frequency characteristic of the channel 198 is relatively smooth, the interpolated correction coefficients close to the ideal values, and the amplitude-frequency response 200 corrector practically coincides with the inverse frequency response of the channel.

o bearing, subject MOOR lying outside the area of complementary bearing, can be used for linear interpolation of their values to the value at the center of the channel. It was found that linear interpolation gives acceptable results in most cases, when the spectrum of the signal corresponds to the strip commercial AM broadcast (from 530 kHz to 1710 kHz), and the width of the region complementary bearing is less than 10 kHz. Alternatively, it may be useful to use complementary bearing, lying farther from the center frequency of the channel, if one or more complementary bearing, lying near the area of complementary bearing, are filtered, for example through high-pass filters that can be used to eliminate the analog signal of the inphase component of the received signal. In addition, the interpolation process can use the information moving numerous complementary bearing. You can use interpolation algorithms, non-linear. As examples of well-known interpolation algorithms can lead to interpolation using cubic spline, polynomial interpolation, interpolation based on ementary bearing, used for interpolation, and adjustment factors for complementary bearing, obtained by interpolation, can be averaged over time to reduce noise impacts. To reduce the impact of noise can also use the aliasing frequency. Instead of interpolation modules of the coefficients in the linear scale may be preferable to interpolate the amplitude in logarithmic scale. Alternatively, instead of interpolate the modulus and phase correction coefficients, it may be useful to interpolate the corresponding real and imaginary components of the coefficients (Cartesian coordinates), which can also be used to represent correction coefficients.

The invention proposes a system for adaptive correction signal broadcast digital audio compatible with amplitude-modulated signal. In the above description set forth certain preferred options for implementation and enforcement of this invention, however, it should be understood that other embodiments of the invention within the scope of the invention defined in the claims.

the private signal, containing amplitude-modulated radio-frequency signal characterized by the first frequency spectrum, and amplitude-modulated radio-frequency signal (10) has a first carrier modulated analog signal program, a set of signals carrying subjected to digital modulation posted in the frequency band covering the first frequency spectrum, and the first group of signals carrying subjected to digital modulation, contains complementary signals, and is located in the first frequency spectrum (14), and the second and third group of carrier signals are subjected to digital modulation, contain complementary signals and are positioned outside of the first frequency spectrum, namely, forming a first signal representing the in-phase components of the digital broadcast signal that is compatible with the amplitude-modulated signal, generate a second signal representing the quadrature components of the digital broadcast signal that is compatible with the amplitude-modulated signal, using the first and second signals as the real and imaginary input signals to a fast Fourier transform performed on the first and second signals, for forming sovoobraznyh signals by multiplying together the converted signals to the correction vector, moreover, the correction vector is formed by a set of correction coefficients, characterized in that the upgrading of correction coefficients used for the complementary signals by interpolation using the coefficients vector for complementary signals.

2. The method according to p. 1, characterized in that the coefficients vector for complementary signals interpolate using linear interpolation, interpolation using a cubic spline, polynomial interpolation, interpolation based on the fast Fourier transform or approximation of a logarithmic curve.

3. The method according to p. 1, characterized in that the interpolation produce averaged over time.

4. The method according to p. 1, characterized in that the interpolation results are linear changes in the magnitude and phase coefficients as a function of frequency.

5. The method according to p. 1, characterized in that the interpolation results are logarithmic changes of the module of coefficients.

6. The method according to p. 1, characterized in that the interpolation carried out on the module and phase of the coefficients.

7. The method according to p. 1, characterized in that the interpolation carried out on the real and imaginary part of bestimage with amplitude-modulated signal, containing amplitude-modulated radio-frequency signal (10), characterized by the first frequency spectrum, and the amplitude-modulated RF signal has a first carrier modulated analog signal to the broadcasting program, a set of signals carrying subjected to digital modulation, placed in the band (14), which encompasses the first frequency spectrum, and the first group of signals carrying subjected to digital modulation, contains complementary signals, and is located in the first frequency spectrum, and the second and third group of signals carrying subjected to digital modulation, contain complementary signals and are positioned outside of the first frequency spectrum, namely, receiving a digital broadcast signal that is compatible with the amplitude-modulated signal, generate a first signal representing the in-phase components of the digital broadcast signal that is compatible with the amplitude-modulated signal, generate a second signal representing the quadrature components of the digital broadcast signal that is compatible with the amplitude-modulated signal, using the first and second signals as the real and imaginary input signals dlti converted signals, representing data in the frequency domain, and process the set of transformed signals by multiplying together the converted signals to the correction vector and the adjustment vector is formed by a set of correction coefficients, characterized in that the upgrading of correction coefficients used for the complementary signals by interpolating the coefficients vector for complementary signals to form an output signal in accordance with the adjusted signals generated during machining operations.

9. The method according to p. 8, characterized in that the coefficients vector for complementary signals interpolate using linear interpolation, interpolation using a cubic spline, polynomial interpolation, interpolation based on the fast Fourier transform or approximation of a logarithmic curve.

10. The method according to p. 8, characterized in that the interpolation produce averaged over time.

11. The method according to p. 8, characterized in that the interpolation carried out on the module and phase of the coefficients.

12. The method according to p. 8, characterized in that the interpolation results are logarithmic change is part and imaginary components of the coefficients.

14. Device (156) for the correction of a digital broadcast signal that is compatible with the amplitude-modulated signal containing amplitude-modulated radio-frequency signal (10), characterized by the first frequency spectrum, and the amplitude-modulated RF signal has a first carrier modulated analog signal program, a set of signals carrying subjected to digital modulation, placed in the band (14), which encompasses the first frequency spectrum, and the first group of signals carrying subjected to digital modulation, contains complementary signals, and is located in the first frequency spectrum, and the second and third group of signals carrying subjected to digital modulation, contain complementary signals and are positioned outside of the first frequency spectrum containing means (118) forming a first signal representing the in-phase components of the digital broadcast signal that is compatible with the amplitude-modulated signal, means (118) forming a second signal representing the quadrature components of the digital broadcast signal that is compatible with the amplitude-modulated signal, means (150) using the first and second signals in ka is pout and second signals for providing a set of converted signals, representing data in the frequency domain, and means (156) processing the totality of the converted signals by multiplying together the converted signals to the correction vector and the adjustment vector is formed by a set of correction coefficients, characterized in that it contains means (186) update of correction coefficients used for the complementary signals by interpolation using the coefficients vector for complementary signals.

15. The device according to p. 14, characterized in that the interpolation coefficients vector for complementary signals is a linear interpolation, interpolation using a cubic spline, polynomial interpolation, interpolation based on the fast Fourier transform or approximation of a logarithmic curve.

16. The device according to p. 14, characterized in that the interpolation is accompanied by averaging over time.

17. The device according to p. 14, characterized in that the interpolation results are linear changes in the magnitude and phase coefficients as a function of frequency.

18. The device according to p. 14, characterized in that the interpolation results are logarithmic change module is Oh coefficients.

20. The device according to p. 14, characterized in that the interpolation is performed on the real and imaginary parts of the coefficients.

21. A radio receiver for receiving digital broadcast signal that is compatible with the amplitude-modulated signal containing amplitude-modulated radio-frequency signal (10), characterized by the first frequency spectrum, and the amplitude-modulated RF signal has a first carrier modulated analog signal program, a set of signals carrying subjected to digital modulation posted in the frequency band covering the first frequency range (14), with the first group of signals carrying subjected to digital modulation, contains complementary signals, and is located in the first frequency spectrum, and the second and third group of signals carrying subjected to digital modulation, contain complementary signals and are positioned outside of the first frequency spectrum containing means (110) for receiving a digital broadcast signal that is compatible with the amplitude-modulated signal, means (118) forming a first signal representing the in-phase components of the digital broadcast signal that is compatible with amplitude-modulated si is Ala broadcast, compatible with amplitude-modulated signal, means (150) using the first and second signals as the real and imaginary input signals to a fast Fourier transform performed on the first and second signals for providing a set of converted signals representing data in the frequency domain, and means (156) processing the totality of the converted signals by multiplying together the converted signals to the correction vector and the adjustment vector is formed by a set of correction coefficients, characterized in that it contains means (186) update of correction coefficients used for the complementary signals, by interpolation using the coefficients vector for complementary signals and means (144) generate an output signal in accordance with the adjusted signals generated in the processor.

22. Radio on p. 21, characterized in that the interpolation coefficients vector for complementary signals is a linear interpolation, interpolation using a cubic spline, polynomial interpolation, interpolation-based would be the of the action scene, what interpolation is accompanied by averaging over time.

24. Radio on p. 21, characterized in that the interpolation results are linear changes in the magnitude and phase coefficients as a function of frequency.

25. Radio on p. 21, characterized in that the interpolation results are logarithmic changes of the module of coefficients.

26. Radio on p. 21, wherein the interpolation is performed on the module and phase of the coefficients.

27. Radio on p. 21, wherein the interpolation is performed on the real and imaginary parts of the coefficients.

 

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