Line radio

 

The invention relates relates to the field of radio communications and can be used in space and terrestrial communication systems using spatial modulation. The technical result is that when using two orthogonal channels, the proposed device is transmitted in addition to the basic information is still three more, which can be used as a utility that does not require increasing the number of radio channels. The device was introduced on the transmission side frequency synthesizer, two electronic key, the inverter, and the second block addition, at the receiving side of the first and second mixers, fifth and sixth multipliers, first and second low pass filters (LPF), the first, second and third delay lines, the first band-pass filter of the carrier frequency f1 (PF f1), the second PF f2, the block select maximum, the unit of comparison, the amplifier-limiter, synchronous phase filter and the third band-pass filter. 2 Il.

The proposed device relates to the field of radio communications and can be used in space and terrestrial communication systems using spatial modulation.

Known devices for wireless communication with a reuse frequency (see U.S. Pat. USA 4987818 and changes the relative position of the antennas is achieved by ensuring the orthogonality of polarization of two simultaneously transmitted signals with circular or linear polarization. However, these devices because of the high accuracy requirements ensure the orthogonality of polarization of the transmitted signals have a complex system-locked loop, using a special pilot signals. In addition, the use of pilot signals requires the allocation of additional frequency channels, which does not coincide with the spectrum of transmitted signals, which significantly complicates the design of the device and degrade its performance.

It is also known device.with. 1141978 containing two channels, one of which information is transmitted using angular modulation, and the second channel using the additional modulation signals according to the polarization of the waves, making it possible to pass additional information (reuse frequency).

However, in the case of wideband signals, which is typical for modern communication systems, low immunity receiving information on the second channel due to the low noise reference signal for the synchronous detector.

Closest to the technical nature of the proposed facility is "Apparatus for transmission of discrete information".with. 300946 adopted for the prototype.

Functional diagrams the deposits of the carrier and clock frequencies (GNTC); 2 - shaper orthogonal pseudo-random sequences (FOPP); 3 - pseudo-random sequence generator (HPG); 4 - device phasing; 5, 6 - the first and the second multipliers; 7 - Phaser 90o; 8 - phase arm; 9 - scheme of addition;
The receiving device
10, 11 the third and fourth multipliers;
12 - shaper orthogonal pseudo-random sequences (FOPP);
13 - reference generator pseudo-random sequence (GOP);
14 - device phasing;
15 - device synchronization;
16, 17, the first and second bandpass filters;
18 is a phase detector.

The device prototype contains on the transmission side GNTC 1, the first output of which is connected with the first inputs FOPP 2 and 3 GPP, the second inputs of which are connected respectively to the first and second outputs of the device phasing 4, exit POP 2 connected to the first input of the first multiplier 5, a second input connected to the output of the phase shifter 90o7, and the input of the phase shifter connected to one of inputs of the phase arm 8 and a second output GNTC 1, the GPP output 3 is connected to one of inputs of the second multiplier 6, the second input is connected to the output of the phase manipulator 8, and the output W of the multiplier 5, the output of the adder 9 is the transmitter output, the first input of the phase manipulator 8 is an information input; at the receiving side input synchronization device 15 is connected with the first inputs of the first 10 and second 11 multipliers, the outputs of which are connected respectively to the inputs of the first 16 and second 17 of bandpass filters whose outputs are connected respectively with the first and second inputs of the phase detector 18, the output of which is the output device, the output of the synchronization device 15 is connected with the first inputs FOPP 12 and GAP 13, the second inputs of which are connected respectively to the first and second outputs of the device phasing 14, output FOP 12 is connected with the second input of the first multiplier 10, and the output GAP 13 is connected with the second input of the second multiplier 11.

The device prototype works as follows.

In the transmitter GNTC 1 generates two frequencies clock frequency for POP 2 and 3 GPP and the carrier frequency signal. Clocked output GNTC 1 is fed to the input FOPP 2 and 3 GPP, which produce a binary pseudo-random sequence. These sequences represent sets of bipolar pulses of direct current of the same magnitude and duration, which is about the same to ensure low cross-correlation between the pseudo-random sequences FOPP 2 and 3 GPP at any phase shift between them (quasiorthogonal binary pseudo-random sequence). This condition is necessary for their effective separation and suppression of the echo signal in the receiver.

The device phasing 4 sets shift registers POP 2 and 3 GPP in the same initial state, so that the communication phase of their pseudorandom sequences. The device fairaway 4 consists of decoders initial States FOPP 2 and 3 GPP and pulse phasing scheme, which provides a combination of initial conditions in phase. Binary pseudo-random sequence output FOPP 2 is supplied to the multiplier 6. To the second input of the multiplier 5 through the phase shifter 90o7 output GNTC 1 receives the oscillation of the carrier frequency, which in the multiplier 5 is multiplied by a binary pseudo-random sequence. As a result, the output of the multiplier 5 is formed a signal representing the oscillation of the carrier frequency with a constant amplitude shift keyed phase by 180oby law, a binary pseudo-random sequence. Binary pseudorandom on the output GNTC 1 receives the oscillation of the carrier frequency. At the output of the multiplier 6 is formed a signal representing the oscillation of the carrier frequency with a constant amplitude shift keyed phase by 180oby law, a binary pseudo-random sequence. Depending on the sign of peredavalas information, phase arm 8 carries out the rotation phase of the carrier frequency signal at the output of the multiplier 6 relative to the carrier frequency of the signal at the output of the multiplier 5 to 0 or 180o. Thus, depending on the sign of information transmitted carrier frequencies of these signals are shifted from each other in phase. From the outputs of the multipliers 5 and 6, the signals are sent to the scheme of adding 9, which forms an output signal representing the oscillation of the carrier frequency with a constant amplitude shift keyed phase at 0o, 90o, 180oand 270oand moments of manipulation and the order of these values of the phases is determined by the ratio of the signs of the elements of the binary pseudo-random sequences FOPP 2 and 3 GPP and transmitted phase difference. With schema adding 9 signal enters the high-frequency transmitter and radiated in the air.

The received signal output from the high frequency receiver is fed to the multipliers 10 and 11, similar to the sequence, which produces POP 12, similar POP 2 transmitter. The output signal from the multiplier 10 is supplied to the bandpass filter 16, which allocates the oscillation of the carrier frequency signal. In the multiplier 11 and the received signal is multiplied by a binary pseudo-random sequence, which forms the BPU 13, similar to the 3 GPP transmitter. The output signal from the multiplier 11 is supplied to band-pass filter 17, which allocates manipulated by phase fluctuations of the carrier frequency signal.

The device phasing 14, similar to the device phasing 4 transmitter provides connection phase output sequences FOPP 12 and GAP 13 corresponding to the communication phase sequences HOP 2 and 3 GPP transmitter.

Binary pseudo-random sequence produced by the generator in the receiver is synchronized with the binary pseudo-random sequences of the received signal using the synchronization device 15. As a synchronization device 15 can be used the known device synchronization, ensuring the synchronism of the local signal of the receiver with one of the strongest rays of the received multipath signal on the basis of the analysis of the cross-correlation function accept is echino effective suppression of interfering rays, either the addition of several selected the strongest rays, and the suppression of concentrated interference.

Fluctuations of the carrier frequency from the outputs of bandpass filters 16 and 17 are received by a phase detector 18, which measures the information of the phase difference between them.

But this device prototype inherent drawback: to transfer an increasing amount of information necessary to increase the transmission rate or the number of radio channels, which in both cases leads to the expansion of radio frequency bands. As you know, currently, the range of frequencies, from the lowest - VLF to the highest microwave, very congested. Therefore, the task of allocating any part of the radio spectrum is becoming increasingly problematic.

The proposed device allows you to transfer in addition to the basic INFO.1, another three for more DETAILS.2, INF.3 and INF.4.

To eliminate this drawback in the device containing connected in series generator carrier and clock frequencies (GNCC), the first shaper orthogonal pseudo-random sequences (FOPP), the first multiplier, the output of which is connected to the first input of the first block of the addition, the output of which I have goluzinoi sequence (GPP) and the second multiplier, the output of which is connected with the second input of the first block of addition, the second inputs of the first FOP and GPP connected to respective outputs of the block phasing, the first input of GPP is connected to the input of the first POP, the first input of the phase manipulator is connected to the input of the phase shifter, a second input of the phase manipulator is input information INF.1" and its output connected to the second input of the second multiplier, at the receiving side includes a synchronization unit, an input connected to the first inputs of the third and fourth multipliers and an entrance of the receiving part radio communication lines, the output of the synchronization unit is connected with the first inputs of the second FOPP and second GPP, the output of which is connected to a second input of the fourth multiplier, a second input of the second FOP and GPP connected to respective outputs of the block phasing, as well as band-pass filter of the lower sideband, band-pass filter of the upper sideband and the phase detector, introduced on the transmission side frequency synthesizer, the first and second electronic switches, the inverter, the second block addition and two-channel single-sideband modulator, at the receiving side connected in series with the first delay line and the first mixer, sequentially connect the Tr low pass (LPF), connected in series to the sixth multiplier and the second low-pass filter, and the first and second bandpass filters of the carrier frequency f1and f2(PF f1and PF f2), connected in series block select maximum, the amplifier-limiter and synchronously-basic demodulator, connected in series, the third band-pass filter and a third delay line, and the unit of comparison. On the transmitting side input of the frequency synthesizer is connected with the second output GNTI, and the outputs of the frequency synthesizer connected to the first inputs of the first and second electronic switches whose outputs are connected to respective inputs of the second block of addition, the output of which is connected to the input of the phase shifter. The input of the inverter connected to the second input of the second electronic key and an entry information "INF.4". The output of the inverter is connected to a second input of the first electronic switch, the Output of the phase shifter connected to the first input channel single-sideband modulator, the output of which is connected with the second input of the first multiplier, a second input of the dual-channel single-sideband modulator is the input information of IFN.2, and its third input of the input information INF.3". At the receiving side inputs of the first and second whether the mixer is connected to the input of bandpass filter lower sideband, the output of which is connected to the first input of the fifth multiplier. The output of the second mixer is connected to the input of bandpass filter upper sideband, the output of which is connected to the first input of the sixth multiplier.

The output of the first LPF is a data output "INF.3". The output of the second LPF is the output information of the ANF.2". The output of the first PF f1connected with the first inputs of the block select maximum and block comparison, the output of which is a data output "INF.4". The output of the second PF f2connected with the second inputs of the block select maximum and Comparer. The output of the fourth multiplier is connected to the third input of the PF. The output of the third delay line connected to the first input of the phase detector, a second input connected to the second output of the synchronous phase demodulator, the first output of which is connected with the second inputs of the first and second mixers, fifth and sixth multipliers. The output of the phase detector is a data output "INF.1".

In Fig. 2 shows a functional diagram of the proposed device, where we have introduced the following notation:
1 - generator carrier and clock frequencies (GNTC);
2 - shaper orthogonal pseudo-random sequences (FOPP);
3 - generator is 7 - Phaser 90o;
8 - phase manipulator;
9 - the first block of addition;
10, 11 the third and fourth multipliers;
12 - second shaper orthogonal pseudo-random sequences (FOPP);
13 - the second reference generator pseudo-random sequence (GOP),
14 - unit phasing;
15 is a block synchronization;
16 - band-pass filter lower sideband;
17 - bandpass filter upper sideband;
18 phase detector;
19 - vented;
20 - frequency synthesizer;
21, 22, the first and second electronic switches;
23 - second unit of addition;
24 - channel single-sideband modulator;
25, 26, the first and second delay lines;
27 - the first band-pass filter of the carrier frequency f1(PF f1);
28 - the second band-pass filter of the carrier frequency f2(PF f2);
29, 30, the first and second mixers;
31, 32 fifth and sixth multipliers;
33, 34, the first and second low pass filter (LPF);
35 is a block select max;
36 - amplifier-limiter;
the 37 - unit comparisons;
38 - the third band-pass filter (PF);
39 - the third delay line;
40 - synchronous phase demodulator.

The proposed device contains on the transmission side connected in series Gogo is the output of the radio link. In addition, the output GNTC 1 connected in series through ppgs 3 and the second multiplier 6 is connected with the second input of the first block of addition 9. Second input FOPP 2 and 3 GPP connected to respective outputs of the block phasing 4. The second output GNGC 1 is connected to the input of the frequency synthesizer 20, two exits through which the first 21 and second 22 electronic switches connected to inputs of the second block of addition and 23, respectively, the output of which is connected to the inputs of the phase shifter 7 and the phase of the manipulator 8, the output of which is connected with the second input of the second multiplier 6. The output of the phase shifter 7 through a two-channel single-sideband modulator 24 is connected to a second input of the first multiplier 5. The second and third inputs of the dual-channel single-sideband modulator 24 are used as inputs for further information 2 (INF.2) and 3 (INF.3), respectively. The second input of the phase manipulator 8 is input basic information 1 (INF.1). The output of the inverter 19 is connected with the control input of the first electronic switch 21. The control input of the second electronic switch 22 is connected to the input of the inverter 19 is input additional information 4 (INF.4).

At the receiving side line of the radio contains the synchronization unit 15, the input of which shoedini. The outputs of block phasing 14 is connected with the second inputs of the second FOPP 12 and the second GAP 13, the output of which is connected in series through the fourth multiplier 11, the third PF 38 and the third delay line 39 is connected to the first input of phase detector 18, the output of which is the release of information I (INF.1). Connected in series with the first delay line 25, the first mixer 29, the bandpass filter bottom side of the strip 16, the third multiplier 31 and the first low-pass filter. 33, the output of which is the data output 3 (INF.3), connected in series, a second delay line 26, the second mixer 30, a band-pass filter top side of the strip 17, the fourth multiplier 32 and the second low-pass filter 34, the output of which is the data output 2 (INF.2). Connected in series, the first PF 27, and the block selection maximum of 35, the amplifier-limiter 36 and the synchronous phase demodulator 4, the first output of which is connected with the second inputs of the first 29 and second 30 mixers, with the second input 31 of the third and fourth 32 multipliers. The second output synchronous phase demodulator 40 is connected to a second input of the phase detector 18. The output of the second PF 28 is connected with the second input of the block selecting maximum 35 and the second input unit 37 comparison, the first input of which Inany with the output of the third multiplier 10. The output of the synchronization unit 15 is connected with the first inputs of the second FOPP 12 and the second GAP 13.

The proposed device operates as follows.

In the transmitter GNGC 1 generates two frequencies: a clock for POP 2 and SPT 3 and the carrier frequency signal. Clocked output GNGC 1 arrives at the inputs of POP 2 and 3 GPP, which produce a binary pseudo-random sequence - SRP. These SRP represent sets of bipolar pulses of direct current of the same magnitude and duration, which is determined by the value of the clock frequency. The laws of formation of the SRP shall be such to ensure low cross-correlation between the pseudo-random sequences FOPP 2 and 3 GPP at any phase shift between them (quasiorthogonal binary SRP). This condition is necessary for their effective separation and suppression of the echo signals in the receiver.

Block phasing 4 sets shift registers POP 2 and 3 GPP in the same initial state, so that the communication phase of their pseudorandom sequences.

Binary DSP output FOPP 2, is fed to the first multiplier 5, the second input is through the phase shifter 7 are variations of the carrier frequencies f1and f2are produced in the frequency synthesizer 20 and are interconnected by keys 21 and 22 according to the law 4 (INF.4) supplied to the control inputs of these keys, and the control input of the first key 21 is fed through an inverter 19. From the outputs of the keys 21 and 22 of the oscillations of the carrier frequencies f1or f2arrive at the inputs of the block 23, and with its output to the inputs of the phase shifter 7 and the phase of the manipulator 8. From the output of the unit 7, the signal at frequencies f1or f2supplied to the first input unit 24, the second and the third input of which is provided with the information 2 and 3 (INF.2 and INF.3). The output of block 24 will be at a frequency f1the upper and lower sidebands, or at a frequency f2- upper and lower sidebands. This signal is applied to the second input unit 5, to the first input of which POP 2 served binary SRP. As a result, the output unit 5 produces a signal representing oscillations of the carrier frequencies f1or f2with a constant amplitude shift keyed phase by 180oby law, the binary SRP.

Binary SRP output GPP 3 is supplied to the block 6, to the second input of which block 8 serves fluctuations of the carrier frequencies f1or f2, progenipoietin phase by law, "INF.1". Thus, vicodinno amplitude, manipulated in phase by 180oby law, the binary SRP "INF.1". Depending on the sign of the transmitted information "INF.1 unit 8 carries out the rotation phase of the carrier frequencies of the signal at the output of the multiplier 6 relative to the carrier frequencies of the signal at the output of the multiplier 5 to 0 or 180o. Thus, depending on the sign of information transmitted carrier frequencies of these signals are shifted from each other in phase. Outputs of blocks 5 and 6, the signals are sent to the block 9, the output of which appears the output signal of the oscillation of the carrier frequencies f1or f2with a constant amplitude shift keyed phase 0, 90o, 180oand 270oand moments of manipulation and the order of these values of the phases is determined by the ratio of characters of the binary elements of the SRP POP 2 and 3 GPP and transmitted phase difference "INF. 1", " block: 9 signal enters the high-frequency transmitter and radiated in the air.

The received signal output from the high frequency receiver is supplied to the blocks 10, 11 and the synchronization unit 15. Blocks 10 and 11 is similar to the blocks 5 and 6 of the transmitting side. In block 10 the received signal is multiplied by a binary SRP, which produces POP 12 (similar FOPP 2 transmitter), In block 11 the received signal is multiplied by the 4 transmitter) provides communication phase output sequences FOPP 12 and GAP 13. Binary SRP produced by the generators in the receiver is synchronized with the binary SRP received signal using the synchronization unit 15. As the synchronization unit 15 can be used the known device synchronization, ensuring the synchronism of the local signal of the receiver with one of the strongest rays of the received multipath signal on the basis of the analysis of the function of cross correlation between the received and local signals. As is known, when using broadband signals can be provided effective suppression of interfering rays, or the addition of several selected the strongest rays, and the suppression of concentrated interference.

From the output of the unit 10, the signal fed to the first inputs 25, 26 second delay lines and the inputs PF 27 PF 28. Depending on what carrier frequency f1or f2. was passed a signal at a given time with 27 PF or PF 28 is removed, the useful signal.

PF 27 PF 28 signal is received at block 37, which produces a comparison signal and the output of block 37 is obtained, the information signal INF.4". In addition, the outputs of the PF 27 PF 28 signal is input to the block 35. Thus, the signal at this time is supplied from only one of these BC the selection of the greatest values of the two signals, and this will be a useful signal, taken from one of the blocks 27 or 28. From the output of the block 35, the signal is fed to the block 36, which ensures the normal operation of the unit 40. From the output of block 40 reference signal is supplied to the blocks 18, 29, 30, 31 and 32.

Because the block 40 has a low-pass filter, the reference signal, it will linger on for a while3. For normal operation blocks 29, 30 signal applied to their inputs, must be detained at the same time3and I do delay lines 25 and 26. Similar functions are performed by the delay line 39.

From the outputs of the mixers 29, 30, the signal at the filter bottom side chaff 16 and the filter top side of the strip 17, which are filtered and fed to the inputs of the blocks 31 and 32, the second input of which the signal at the output of the Bloch 40. In the multipliers 31, 32 are migrating signals "INF.2" and "INF.3 in the region of low frequencies and passing through the blocks 33 and 34, the signals INF.2" and "INF.3" come on output line radio.

Thus, if the device prototype using two orthogonal channels is only one main information, the proposed device using the same two orthogonal channels is transmitted in addition to the basic information is et in many cases, to withdraw from the organization of special bearer service or other information.

Implementation of the blocks included in the proposed device, causes no trouble, as they are known and described in the technical literature.

Synchronous phase demodulator 40 includes a phase detector, a voltage controlled oscillator, and a low-pass filter.


Claims

The line radio that contains on the transmission side connected in series generator carrier and clock frequencies (GNCC), the first shaper orthogonal pseudo-random sequences (FOPP), the first multiplier, the output of which is connected to the first input of the first unit addition, the output of which is input to a transmitting side radio communication lines, in addition, connected in series pseudo-random sequence generator (HPG) and the second multiplier, the output of which is connected with the second input of the first block of addition, the second inputs of the first FOP and GPP connected to respective outputs of the block phasing, the first input of GPP is connected to the input of the first POP, the first input of the phase manipulator is connected to the input of the phase shifter, a second input of the phase manipulator is input information INF.1" and its output connected to the second input of the second multiplier, at the receiving side and an entrance of the receiving part radio communication lines, the output of the synchronization unit is connected with the first inputs of the second FOPP and second GPP, the output of which is connected to a second input of the fourth multiplier, a second input of the second FOPP and second GPP connected to respective outputs of the block phasing, as well as band-pass filter of the lower sideband, band-pass filter of the upper sideband and the phase detector, wherein imposed on the transmission side frequency synthesizer, the input of which is connected with the second output GNTI, the first and second electronic switches whose outputs are connected to respective inputs of the second block of addition, the output of which is connected to the input of the phase shifter and the phase inverter, the output of which is connected to a second input of the first electronic switch, a first input connected to a corresponding output of the frequency synthesizer, the other end of which is connected to the first input of the second electronic switch, a second input connected to the input of the inverter, which is the input information INF.4", in addition, one-sheet dual modulator first input connected to the output of the phase shifter, the second input is information INF.2", the third input information " INF.3, and its output is connected with the second wholesael, the output of which is connected to the input of bandpass filter of the lower sideband, the output of which through the fifth multiplier connected to the input of the first low pass filter (LPF) whose output is the output information "INF.3", connected in series, the second delay line and the second mixer, the output of which is connected to the input of bandpass filter upper sideband, the output of which through the sixth multiplier connected to the input of the second low-pass filter whose output is the output information "INF.2", and the first and second bandpass filters of the carrier frequency f1and f2(f1, f2) whose inputs are connected to inputs of the first and second delay lines and an output of the third multiplier, and the output of the first f1connected with the first inputs of the block select max unit comparison, the output of the second f2connected with the second inputs of the block select maximum and block comparison, the output of which is a data output "INF.4", in addition, connected in series amplifier-limiter and synchronous phase demodulator, the first output of which is connected with the second inputs of the first and second mixers and the fifth and sixth multipliers, the second output synchronous phase detector connected serially connected third band-pass filter and a third delay line, the output of which is connected to the first input of the phase detector whose output is the output information "INF.", the output of the fourth multiplier is connected to the input of the third bandpass filter.

 

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The invention relates to radio engineering, in particular to the transmission of discrete messages, and can be used to improve the efficiency of bandwidth usage lines and radio communications networks, in particular lines and communication networks in systems of automatic dependent observations when used on data lines of a complex of technical means of data transfer

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Line radio // 2160503
The invention relates to radio communications and can be used in space and terrestrial communication systems using spatial modulation

The invention relates to the field of frequency synthesis and can be used in the frequency synthesizer with a fractional value of the division factor

The invention relates to antenna arrays

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5 cl, 5 dwg

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6 cl, 12 dwg

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12 cl, 10 dwg, 1 tbl

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