Diagram of the automatic gain control to manage multiple cascades of amplifiers with adjustable gain when developing estimates the received power of the signal

 

The invention relates to circuits for automatic gain control. The technical result is to improve the working characteristics of the amplifier relative power products intermodulation of the third order and the reduction of the required power amplifier with simultaneous issuance estimation of the received power, which remains accurate regardless of the distribution of boost or attenuation between different amplifiers. A General scheme of the regulation (ORR) supports this assessment capacity in the same value of the total gain by distributing the gain of at least two cascaded amplifiers in response to this value. Due to programming or hard-coding a few key parameters of the SRF can be used with many configurations of amplifiers. 3 S. and 7 C.p. f-crystals, 10 ill.

The invention relates to circuits for automatic gain control. More specifically, the present invention relates to a new and improved type of automatic gain control made with the possibility of independent control of multiple cascades of amplifiers with adjustable gain and provide an assessment accept modestine (AGC) for amplifying or attenuating the received signals to the desired reference level for further processing by the receiver. Possible AGC circuit described in U.S. patent 5099204 entitled "Amplifier with linear gain control", assigned to the owner of the rights to the present invention. The essence of the communication system, which uses such AGC circuit is disclosed in U.S. patent 4901307 entitled "communication System with multiple access and spread spectrum, using satellite or terrestrial repeaters", assigned to the owner of the rights to the present invention. The above system is also described in the time standard of the electronic industry Association and the Association of communications industry (AEP/APSS) IS-95, entitled "Standard compatibility of the mobile stations and base stations for dual-mode wideband cellular systems with spread spectrum" (EIA/TIA Interim Standard IS-95 Mobile Station-Base Station Compatibility Standard for Dual-Mode Wideband Spread Spectrum Cellular System"), hereinafter referred to as IS-95.

The mobile station corresponding to the IS-95, in addition to fulfilling the requirements according to which the incoming signals are subjected to the gain control for further processing, must ensure that the power transmitted its signals necessarily regulated, so as not to cause interference with other mobile stations in the system. This algor emeu power in a cellular telephone system with mobile objects, multiple access, code-division multiplexing (MDCRC)", assigned to the holder of rights to the present invention. One element in this algorithm, the capacity adjustment is the application of measuring the received power of the signal, so that, in contrast to systems in which the only requirement for the AGC circuit is the provision of a suitable reference level of the incoming signals, the AGC circuit corresponding to IS-95, should provide for the calculation of received signal level.

In the ideal case could be developed amplifiers, which would be completely linear, at least in some range. Then the amplifier is characterized by the equation f(x)=k1x, where f(x) is the output signal, x is the input signal, a k1- gain amplifier. In fact, the amplifiers are not perfectly linear, and this nonlinearity makes the distortion in the amplified signal. Of all possible input voltages of the amplifier has a voltage within its linear range and to his "non-linear" range. In the linear range of the amplifier is most closely approximates a linear amplifier. Make the distortion could be seen as a component of the third order. A more realistic response of the amplifier is given by the equation f(x)=k3will be more linear than the amplifier to a large value.

One type of distortion introduced by non-linear amplifiers, which, in particular, creates problems due to intermodulation components of the signals of two frequencies that are outside the band of interest to the mobile station. An example of this is the system standard IS-95, operating in close proximity to the narrowband system, such as an improved system for radio communication with mobile objects (PRSPO) or global system for mobile communication (reference materials). The operating characteristic of the amplifier relative to the intermodulation is determined by its capacity point of intermodulation products of third order (point MIM). For the calculation it is assumed that transmitters operating in the band of desired frequencies, and the source of the unwanted frequencies are located nearby. This means that as the movement of the mobile station in the direction of the transmitter is increased and the useful received power, and the power of intermodulation. Point MIM is the point at which the power of intermodulation products of third order two tone signals of the same power shifted in frequency to Rafailovici strengthening of the third order, k3.

One way to improve the working characteristics MIM is to increase the linear range of the amplifier. This can be done by feeding more current in the amplifier. However, in typical communication systems, mobile power in the mobile station is a very critical factor and the increase in current is produced only when absolutely necessary. Reduced power consumption turns increased standby time and talk time for the mobile station or, alternatively, reduced requirement for battery power, which will reduce the size and weight of the mobile stations. Alternative to increase the linear range is the reduction of the amplitude of the incoming signal to its conservation within existing linear range of the amplifier.

The standard IS-95 specifies the minimum level parameter, which is defined in this standard as suppression of intermodulation. Fig.1 depicts a typical graph of the coefficient of suppression of intermodulation. For a specified range of the received power receiver must allow a certain amount of interference, or to have some factor suppress inter-modulation (KPIM), as shown by the line labeled "technology. Tr." IU the th point MEN will increase by 1/3 dB for each increment accept input power at 1 dB. The slope of the line technology. Tr." may not be equal to 1/3 dB dB, and this value is actually not in the standard IS-95. The slope in accordance with the standard IS-95 is approximately 1 dB per 1 dB. If the line "technology. Tr." is such, as shown in the drawing, the amplifier must meet the technical requirements at the point T. This should give KPIM specified line (gain) N1. To satisfy the technical conditions at the point T, you could use the amplifier with less current, which would KPIM defined by the line L2. As shown, the amplifier that meets the point T designed with a reserve for point T. This design margin can be considered equivalent to the increase in bias current, resulting in reduced service life of the batteries or the use of more expensive items, or to both of these consequences.

The AGC circuit, which could possess the intrinsic properties of lines U1 or U2, shown in Fig.2. The signals received by the antenna 100, is sent to a low noise amplifier (LNA) 110 ultra-high frequency (UHF). The amplifier 110 is shown with a dashed arrow indicates a possible variant of the amplifier with adjustable gain. This configuration with adjustable gain is rssmate 115 using UHF frequencies generated by the local oscillator 120 UHF. The signal converted to a lower frequency, is passed through band-pass filter 130 and is amplified by the amplifier 140 intermediate frequency (if) with adjustable gain. This amplified if signal is then converted with decreasing frequency in the mixer 145 using the frequency range FC generated by the generator 150 frequency range of the inverter. Now the received signal is in the frequency band of the modulating signals, and block 160 specify the level of the received signal (block 160 UUPS) generates the estimate of the received power signal. The difference between this estimate and the reference power stored in the block 165 reference power level is calculated in the adder 170, and the block 180 automatic gain control when receiving (ARUP) affects this difference error to obtain a suitable ZNACHENIYA 195.

ZNACHENIE AGC 195 is fed through linearization 190 in the amplifier 140 with adjustable gain. Linearization 190 compensates for any non-linear characteristics of "dB/" amplifier 140 with adjustable gain. Linearization is described in U.S. patent 5627857 called "Linearized digital automatic gain control", assigned to the owner of the rights to the present invention. As Ingenieure with the to make the difference calculated in the adder 170, as much as possible close to zero. Immediately after closure of this circuit the signal located in the frequency band of the modulating signals and output from the mixer 145, is at an acceptable level of input power and can be demodulated (diagram not shown). Typically, the conversion with decreasing frequency in the range of the inverter is above the in-phase and quadrature components of the signal, and there is an additional filter that is not shown in the drawings for reasons of clarity. The described scheme will have KPIM-response corresponding to the line L1 in Fig.1, when designing for a fixed level of current. Note that ZNACENJE can be used to estimate the received power, but only after factoring in the gain of the whole circuit of the reception.

One way to reduce the use of unnecessary power involves the application of the amplifier, designed for less current than that which would be required for the formation of the line N1, and enabling adjustment of the input gain stages, i.e., the LNA 110, as shown by the dotted arrow in Fig. 2. For example, assume that the amplifier is sexirani gain, or even disabled. After you disable the LNA 110 will increase or decrease will be made to weaken. This reduces the requirement to the linear range of the amplifier 140 FC.

When the cascade LNA is disabled, the operating expenses are covered by increased lower noise level. The approximate value of the ratio of carrier to noise ratio (N/P) is equal to this lower level of thermal noise amplifier circuits plus intermodulation components plus co-channel radio interference. The operating characteristic of the demodulator is a function of relationship N/a bandwidth of the modulating signal. With the increase of the received power (carrier (N)) may increase the total interference. Provided that the lower the noise level remains approximately constant, unless you are switching LNA, as a compromise to enter the border is exceeded for improved working characteristics MIM by disabling the amplifier, resulting in an improved working characteristics MIM due to the increased lower noise levels.

Fig. 3 depicts the line "technology. Tr." KPIM matching shown in Fig. 1. However, KPIM just described LNA with adjustable gain is completely different from the lines U1 or U2 KPIM. Gain the camping current less than one that needs to be coupled to the amplifier to match the line L1 shown in Fig.1. As input power increases, you're going to use the range of linearity of the amplifier necessarily would have to be below the point TT line "technology. Tr.". Instead entered weakening by disabling the LNA 110, and therefore, the input signals to the amplifier 140 FC, translated in its linear range, and the operating characteristic MIM rises above in this example, operating characteristics, comparable to that required to obtain the line U1. It shows a plot of K2 line. Similarly, if you use LNA 110 with a truly adjustable gain, and not just turn on and off, as in the example, the operating characteristic of the circuit amplifiers with AGC can be done very close to the required minimum line "technology. Tr.", as a result, the minimum consumption of power.

The value of the total gain in the chain of amplifiers with AGC can be used as a measure of total received power. This is possible because the main function of the AGC is to take the level of the input power and reduce it to the level of the reference power cefipra power. However, to improve the characteristics MIM it is desirable to have the ability to change the distribution of attenuation or gain of all amplifiers in the circuit AGC. Note that in case of distribution of amplification cascades ZNACENJE 195 is not an appropriate assessment. As shown above, the distribution of the gain of the overall amplifier is not necessarily automatically gives the total value of the gain of the AGC circuit, which can be used as an estimate of the received power (and, therefore, estimates of the transmitted power). Thus, in the prior art there is a need in the AGC circuit, managed to improve the working characteristics MIM when developing useful evaluation of the received power.

The present invention provides a new and improved AGC circuit, configured to work with different configurations of amplifiers with AGC to improve the working characteristics MIM and reduce the required current amplifier with simultaneous issuance estimation of the received power, which remains accurate regardless of the distribution of boost or attenuation between different amplifiers. A General scheme of the regulation supports this estimate of the power of one is the overall coefficient , by programming or hard coding the few key parameters generalised adjustment can be used with many configurations of amplifiers. Among the supported configurations - switchable LNA, switchable LNA with adjustable gain configuration with LNA FC and UHF with adjustable gain and configuration unleashed LNA FC and UHF with adjustable gain. The invention can be extended to the configuration of multi-stage amplifiers. Although the preferred specific implementation includes two cascades, one for UHF and one for the inverter, you can easily adapt the invention to the case of three or more stages. In order to adapt to the dynamics of the switching gain, you can apply different filtering schemes for cardinality estimation. For example, you can apply a low pass filter in the input stage of the UHF to give it a slower response than the cascade inverter. All of these configurations and any subset can be supported in one aggregate device.

The features, objectives and advantages of the present invention will become more apparent from the following detailed description when studying it in conjunction with the attached drawings, in which identical symbols respectively indicate the same elements in all the drawings, where Fig. 1 depicts a typical graph of the coefficient of suppression of mutually is acii, associated with the configuration of the AGC switchable LNA Fig. 4A depicts a configuration with switchable and/or speed gain LNA, Fig.4B depicts a configuration with a variable gain LNA, Fig.4C depicts switchable adjustable attenuator, Fig. 5 depicts the preferred specific implementation of the present invention, Fig. 6 depicts in detail a generalized diagram of the gain control corresponding to the present invention, Fig. 7A depicts a generalized diagram of a gain control configured for use in conjunction with switchable LNA,
Fig. 7B depicts a possible static transfer function of the attenuation of UHF and/or the inverter corresponding to the configuration shown in Fig.7A,
Fig. 8A depicts a generalized diagram of a gain control configured for use in conjunction with a switched attenuator with adjustable gain,
Fig. 8B depicts a possible static transfer function of the attenuation of UHF and/or the inverter corresponding to the configuration shown in Fig.8A,
Fig. 9A depicts a generalized diagram of a gain control configured for use in conjunction with a non-switched LNA with adjustable gain,
Fig. 9B depicts the th in Fig.9A,
Fig. 10A depicts a generalized diagram of a gain control configured for use in conjunction with a non-switched LNA with adjustable gain alternative unleashed configuration with gain of the inverter and/or UHF, and
Fig.10B depicts a possible static transfer function of the attenuation of UHF and/or the inverter corresponding to the configuration shown in Fig.10A
The present invention provides a generalized AGC for many configurations of amplifiers. Fig.4A-4C depict conceptually different types of configurations of amplifiers that are supported in the invention. They are given just as examples.

Fig. 4A depicts a configuration with switchable and/or speed gain LNA, which is conceptually similar to bypass LNA. The switch 305 under the control of the signal DIAPASONS selects between the incoming signal and the incoming signal, attenuated by the divider 300 capacity (DM 300). The signal from the switch passes through the LNA 310, the mixer 315 UHF and enters the amplifier 320 inverter with gain control. This power inverter 320 selects its value gain-controlled signal CORRECTIE ARE AT the RECEPTION. The amplified signal then undergoes preobrazovaniya weakening through DM 300 can be implemented by shunting LNA instead of attenuation. This is equivalent to bypass one or more stages of multi-stage LNA.

Fig. 4B depicts the configuration of the LNA with adjustable gain. It differs from that shown in Fig.4A, only the input stage. Instead of enable or disable fixed attenuation running signal DIAPASONS DM 300, switch and LNA 305 310 is replaced by LNA 330 with adjustable gain, which is set in accordance with the signal SELENIUMS.

Fig.4C depicts switchable adjustable attenuator. And in this case, the only difference from Fig.4A and Fig.4B is input to the cascade. As the scheme depicted in Fig.4A, this scheme makes or disables the weakening through switch 305 under the control of the signal DIAPASONS. However, an adjustable attenuator 330 under control of signal SELENIUMS provides attenuation.

Fig. 5 depicts one preferred specific implementation of the present invention. It is similar to the circuit shown in Fig.1, but has some important differences. Before linearization 190 receiving introduced generalised 200 gain control, which receives the signal ZNACENJE 195 as an input signal. Generalised 200 regulation is controlled by the gain. It also works in conjunction with optional linearization 190 and an optional linearization LNA 210 (which is another addition to Fig.1). As shown, LNA 110 UHF has an adjustable gain, but this is optional. Generalised 200 gain control can configure all conceptual modes described in Fig. 4A - 4C, and manage. Gain control LNA 110 UHF, if it is an amplifier with adjustable gain, by using signal UMILENIE LNA through linearization 210 LNA (if necessary linearization). If the configuration is applied with switchable LNA, LNA 110 of the inverter is enabled or disabled by the signal DIAPASONS. Management of LNA 110 FC is the signal CORRECTIE ARE WHEN received through linearization 190 admission (if necessary linearization). Note that the generalised 200 gain control manages all amplifiers on the basis of the signal ZNACHENIE AGC 195. Irrespective of the distribution of reinforcements on the various amplifiers in any of the supported configurations, signal ZNACENJE as such sets the strengthening of the chain of amplifiers, as described above, and can be used as a measure of the received power. This measure can be used to happen with hardcoded all the necessary parameters, in a possible specific embodiment is applied, the microprocessor 220 to control schemes and receive feedback from them. The microprocessor 220 is used to configure the generic schema 200 gain control and can give the values of the linearization in linearization 210 and 190, if linearization necessary.

Detailed image of a generalized schema 200 capacity adjustment shown in Fig.6. The signal ZNACENJE, which displays the strengthening of the chain of amplifiers is fed to the adder 350. Any gain allocated to other cascades chain of amplifiers, is subtracted from ZNACHENIYA, and the remainder is used as a gain - i.e., signal CORRECTIONAL RECEPTION. Regardless of the actual distribution of the gain signal ZNACHENIE AGC remains a reliable estimate of the received power signal, useful for solving such tasks as adjusting transmit power.

During normal operation speed controller 300 gain and a linear regulator 310 amplification trigger signal ZNACENJE. However, the multiplexers 370 and 380 are part of an optional configuration in which the exposed filter low pass version of the signal VALUE ZNACENJE. The signal VYBORNA LNA is used to control the choice of filtered or unfiltered signal ZNACENJE through multiplexer 370. The signal VYBOR FILTRATIONCELTIC is used to control the choice of filtered or unfiltered signal ZNACENJE through multiplexer 380. If you select filtered in the range of the lower frequency signal ZNACHENIE AGC, the AGC is carried out mainly at the if (path rapid correction), while the outer contour of the slow correction adjusts the gain UHF based on longer-term evaluation of the received power. To support the suppression of intermodulation band when the fading desirable slower correction gain UHF. Note that due to the innovative design of this scheme adjustment, regardless of the use, the filtered signal ZNACENJE or source signal ZNACENJE in blocks 300 and step 310 linear gain control (or in any number of applicable additional amplification stages or circuits of distribution of gain), through signal CORRECTIONAL RECEIVING guaranteed residual gain. For clarity, the version with pulator 310 gain is triggered by the signal ZNACENJE, giving the signal UNILINEAR. It is configured through two settings, MIN ARE LNA and DIAPAZONULUI. As shown, if the received power, which is an input signal in a linear regulator 310 strengthening of the multiplexer 380, less parameter (4), MINERALS, UMILENIE AGC will be zero. When the received power increases, passing the parameter (4), the output signal increases in accordance with the slope equal to 1, providing an increment of 1 dB for every 1 dB up until the signal SELENIUMS reaches a level programmed by setting (5), DIAPAZONULUI. The signal SELENIUMS is used to control LNA with adjustable gain, is used as the LNA 110 UHF, shown in Fig.5. Table linearization can be configured to provide, if necessary, other linear changes, in addition to 1 dB per 1 dB, for the actual amplification. This optional feature will be further described below. The signal SELENIUMS fed into the multiplexer 320, from which it passes into the adder 330, if not will be set equal to zero, which is programmed using the signal WYBOREM.

Speed controller 300 gain crobat the adder 330, where the addition value from the multiplexer 320. Speed controller 300 is programmed with parameters PADENIE LNA, ROSTRO and SMESHENIEM. As shown, if the received power, which is an input signal supplied to the speed controller 300 gain of the multiplexer 370, less than option (2), ROSTRO, the output signal of this block will be zero. When the received power of the receiver increases, passing the parameter (2), the output signal undergoes stepwise (step) increase to the value programmed using option (3), SMESHENIEM. After that activates the signal RESENAS to select a value from the adder 330 instead of zero values. The output signal will be obtained when the speed adjustment value (3), SMESHNIE LNA, up until the received power drops below option (1), PADENIE LNA. When this output signal is again set equal to zero and the signal RESENAS will be disabled. Independent control of parameters (1) and (2) allows the user to program the hysteresis so that the amplifier is not unnecessarily switching in coding point of activation.

The signal RESHENIE LNA is used for VC. The signal DIAPASONS can be easily modified on the basis of the signal RESENAS. For example, you can add a delay to match the characteristics of the amplifier. Alternatively, the signal RESENAS can control the microprocessor to control the lock LNA 110 UHF.

The output signal of the multiplexer 340 is strengthening, which is distributed to stage amplifier UHF. It is subtracted from ZNACHENIYA in the adder 350, and the remainder is used as the gain value for the amplifier cascade inverter. To a person skilled in the art it is obvious that this solution can be extended and modified without changing the basic structure, so that the signal ZNACENJE will be used for the circuit of the AGC circuit, and provide an estimate of the received power with the simultaneous distribution of the actual gain among the many amplifiers. You can adjust more than two stages of amplifiers, and gain can be added or subtracted, as shown above. Similarly, you can use an alternative scheme for filtering of the signal ZNACHENIE ARU, and the present invention will provide the required characteristics.

Fig. 7A depicts a generalized scheme 200 regulirovaniem in Fig.4A. This configuration can be used with switchable LNA 110 of the inverter with a gain equal to the unit (shown in Fig. 5). In this configuration not used output signal SELENIUMS. The signal WYBORNE is used to select zero to be added to the contents of the adder 330. In an alternative embodiment, the signal DIAPAZONULUI can be set so that the output signal SELENIUMS will always be zero. Parameter SMESHNIE LNA, (3), programming for matching the gain provided by UHF LNA. As described above, UHF LNA is turned on and off in accordance with the received power and options PADENIE LNA, (1), and ROST LNA, (2). An example of the resulting attenuation for each of the gain stages of the inverter and UHF shown in the graph of Fig.7V. Note that the sum of the gains of the if and UHF equal input ZNACHENIYA, as was to be expected.

Fig. 8A depicts a generalized scheme 200 gain control configured to perform a control switchable LNA with adjustable gain, conceptually shown in Fig.4C. This configuration can be used with switchable LNA 110 UHF with adjustable gain (shown in Fig.5). In this configuration, the signal WYBOREM, (4), and DIAPAZONULUI, (5), programmed as described above, and the signal SELENIUMS is adjusted in accordance with them. Parameter SMESHENIEM, (3), programmed for matching the gain provided by UHF LNA. As described above, UHF LNA is turned on and off in accordance with the output of the receiver and parameters PATENIEMI, (1), and ROSTRO, (2). Two examples of the resulting attenuation for each of the gain stages of the inverter and UHF are shown in graph form in Fig.8B. These two examples highlight the difference due to the relative provisions of the parameters (2) and (4). In example (a) of the LNA is switched on before added linear term gain. In example (b) linear component is increased to values greater than zero before the LNA. Note that the sum of the gains of the if and UHF in this case is equal to the input ZNACHENIYA, as was to be expected.

Fig. 9A depicts a generalized scheme 200 gain control configured to perform a control switchable LNA with adjustable gain, conceptually shown in Fig.4B. This configuration can be used with a non-switched LNA 110 UHF with adjustable gain (shown in Fig. 5). In this configura 340 to select the output signal of the adder 330. Alternatively, the parameters PADENIE LNA, (1), and ROSTRO, (2), can be programmed so that the signal RESENAS will always be connected. The signal RESENAS is used to select USILENIEM added to the contents of the adder 330. At the output of the controller 300, the gain should be set to zero, which can be done by programming the parameter (3), SMESHENIEM zero, or - alternatively - programmed parameters (1) and (2) so that the output signal will never be connected. Parameters MINOCYLINE LNA, (4), and DIAPAZONULUI, (5), programmed as described above, and the signal DIAPASONS is adjusted in accordance with them. An example of the resulting attenuation for each of the gain stages of the inverter and UHF shown in the graph of Fig.9B. Note that the sum of the gains of the if and UHF in this case is equal to the input ZNACHENIYA.

Fig. 10A depicts a generalized scheme 200 gain control, configured with the possibility of an alternative type of control LNA with adjustable gain. This configuration can be used with a non-switched LNA 110 inverter with adjustable gain (shown in Fig.5). In this configuration, the channels of signals UMILENIE M is a very useful job of the relative distribution of gain between the if amplifier and UHF. The output signal DIAPASONS not used. The signal RESENAS locked to activate the multiplexer 340 to select zero. Therefore, the output signal of the controller 300, the gain will be ignored. Parameters PATENIEMI, (1), and ROSTRO, (2) programmed as described above, and the signal UMILENIE LNA is adjusted in accordance with them. An example of the resulting attenuation for each of the gain stages of the inverter and UHF shown in the graph of Fig. 10V. And again, the sum of the gains of the if and UHF case of equal input ZNACHENIYA.

The foregoing description of the preferred embodiments are given to provide the specialist in the art the ability to play or to apply the present invention. For specialists in the art it is obvious that in these embodiments of you can make various changes and that described here generalized principles can be applied to other variants of implementation. Thus, the present invention is not limited to the described variants of implementation, and should be considered as appropriate in the broadest sense principles and new features, the essence of which is disclosed in the description.


FORMline to obtain the first value of the controlled gain in response to the value of the total gain, the first value of the controlled gain is zero when the total gain is less than the first predefined threshold value, the first value of the controlled gain increases linearly with the total gain when the total gain is greater than the first predefined threshold value and the first value of the controlled gain continues to grow immediately after reaching a predefined maximum level of amplification, the vehicle speed gain control for gain adjustment signal DC gain and the values of the constant gain in response to the gain signal adjustment constant gain disabled, and the value of the DC gain is equal to zero, when the total gain is less than the second predefined threshold value, the adjustment signal DC gain is connected, and the value of the constant gain corresponds to a predefined level constant gain when the total gain is greater than the third predetermined threshold value, and the adjustment signal DC gain is subject to hysteresis between connection and disconnection, the constant gain when the total gain is between the second predefined threshold value and the third predefined threshold value, a means of summation to obtain a second adjustable gain, which is the sum total of gain taken with a minus a predetermined constant gain when the signal adjustment constant gain connected, and taken with the minus sign of the first value of the adjustable gain.

2. The device under item 1, characterized in that the adjustment signal DC gain can be programmatically disabled or connected.

3. The device according to p. 2, characterized in that it further comprises a filter for filtering value adjustment total gain of the first multiplexer to select between the value adjustment total gain and the output signal of the filter to put in the tool manual gain control, a second multiplexer to select between the value adjustment total gain and the output signal of the filter to put in the tool a linear gain control.

4. The device under item 1, characterized in that it further comprises a filter for filtering the adjustment values abdom filter for input into the tool, manual gain control, a second multiplexer for selecting between the value adjustment total gain and the output signal of the filter to put in the tool a linear gain control.

5. Device for gain control, containing the means of the linear gain control to obtain the first value of the controlled gain in response to the value of the total gain, the first value of the controlled gain is zero when the total gain is less than the first predefined threshold value, the first value of the controlled gain increases linearly with the total gain when the total gain is greater than the first predefined threshold value and the first value of the controlled gain continues to grow immediately after it has reached a predetermined maximum gain, the vehicle speed gain control for gain adjustment signal DC gain and the values of the constant gain in response to the value of the total gain, the signal adjustment constant gain disabled, and the value of the DC gain is equal to zero when the total gain is less than the second predefined threshold value is entrusted certain level of constant gain when the total gain is greater than the third predetermined threshold value, and the adjustment signal DC gain is subject to hysteresis between disconnection and connection, and the value of the DC gain is subject to hysteresis between zero and a predefined level constant gain when the total gain is between the second predefined threshold value and the third predefined threshold value, the first means of summation to obtain the sum of the values of the constant gain and programmatically selected zero or the first value of the controlled gain and the second means of summation to obtain a second adjustable gain which is the sum of the total gain and either taken with the minus sign of the output signal of the first means of summation, when the adjustment signal constant gain connected, or zero when the adjustment signal DC gain is disabled.

6. The device under item 5, wherein the adjustment signal DC gain can be programmatically disabled or connected.

7. The device according to p. 6, characterized in that it further comprises a filter for Phi is the total gain and the output signal of the filter to put in the tool manual gain control, a second multiplexer for selecting between the value adjustment total gain and the output signal of the filter to put in the tool a linear gain control.

8. The device under item 5, characterized in that it further comprises a filter for filtering value adjustment total gain of the first multiplexer to select between the value adjustment total gain and the output signal of the filter to put in the tool manual gain control, a second multiplexer to select between the value adjustment total gain and the output signal of the filter to put in the tool a linear gain control.

9. Device for gain control that contains the vehicle speed gain control for gain adjustment signal, causing the bypass amplifier, in response to the amplification means of the linear gain control to obtain the first value of the controlled gain in response to the value of the total gain, the means of summation to obtain the second value adjustment adjustable gain as the difference between the value of the total gain and any gain entered in the adjustment process by using the manual adjustment preterit filter for filtering value adjustment total gain the first multiplexer to select between the value adjustment total gain and the output signal of the filter to put in the tool manual gain control, a second multiplexer to select between the value adjustment total gain and the output signal of the filter to put in the tool a linear gain control.

 

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FIELD: communication systems.

SUBSTANCE: one of methods is method for providing linear adjustment of level of output power of transmitter, containing device with multiple discontinuous setting values of amplification coefficient, and device with smooth adjustment of setting value of amplification coefficient, including steps for determining amplitude transfer function of transmitter for each said set of discontinuous setting values, forming of compensation table for amplification coefficient, receiving said setting values, reading compensated setting value of amplification coefficient from compensation table, adjustment of amplification coefficient.

EFFECT: higher efficiency, broader functional capabilities, lower costs, higher reliability, higher durability.

9 cl, 27 dwg

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