The phase method of direction finding and phase direction finder for its implementation

 

(57) Abstract:

The invention relates to radio navigation, radio navigation and can be used to determine the location and movement of radiation sources of complex signals. The technical result of the invention is to improve the noise immunity and accuracy of phase measurements of the emitter by suppressing spurious signals (noise) taken on additional channels. The proposed method can be implemented phase signal that contains reception antennas, amplifiers high frequency first local oscillator, mixers, amplifiers first intermediate frequency, a second local oscillator, the amplifier of the second intermediate frequency, multiplier products, narrowband filters, frequency, computing unit, the registration unit, adders, bass-reflex, phasers +90o, the amplitude detector and the key. 2 C. p. F.-ly, 4 Il.

The invention relates to radar systems and can be used to determine the location and movement of radiation sources of complex signals.

Known phase methods measurements and the phase direction finders (RF patents NN 2003131, 2006872, 2010258, 2012010, 2134429, 2155352; Space trajectory measurement. Under the General editorship Radio, 1979 and others).

The basic method should be considered "Phase method of direction finding" (patent of Russian Federation N 2155352, G 01 S 3/46, 1999), which provides the definition of the range D, the angular coordinate and the radial velocity and angular velocity in azimuth and elevation, radiator. While on the measured values of the distance D and the angular velocities and are determined by the tangential components of the velocity vector of the emitter and on the measured values of the six navigation options: three coordinates D, and the three velocities is determined by the module of the vector state of the emitter, i.e., along with the location determined by the motion parameters of the source signal.

This method converts the frequency of the received signals, in which are formed an additional receiving channels. This is because the same value of the first intermediate frequency may be obtained by receiving signals on two frequenciescandC, i.e.

< / BR>
Therefore, if the frequency settingscto take over the main channel, along with it will be a mirror of the receive channel frequencyCwhich differs from the frequencycon and located symmetrically (sodic with the same conversion coefficient KCRthat and the main channel. Therefore, it is most significantly affects the immunity and accuracy of phase measurements of the radiation source signal.

In addition to the mirror, there are other, additional (Raman) receiving channels. The most harmful combination receiving channels are channels formed by the interaction of received signals with harmonics of the local oscillator of small order (second, third, and so on), because the sensitivity of the receiver through these channels close to the sensitivity of the main channel. Thus, the two Raman channels correspond to frequency:

< / BR>
< / BR>
If the frequency of the interference is equal to the first intermediate frequency, a channel of direct transmission. A frequency Converter for a given interference performs the simple function of an intermediary.

The presence of false signals (interference), take on additional channels, resulting in reduced noise immunity and accuracy of phase measurements of the radiator.

An object of the invention is to increase the noise immunity and accuracy of phase measurements of the emitter by suppressing spurious signals (noise) taken on additional channels.

Postuleeritakse right angle, in the top of which is placed the antenna of the measuring channel, common to the four dynamical channels located in the azimuthal and elevation planes, two on each plane, thus forming in each plane, two measurement bases d and 2d, between which establish the inequality

< / BR>
where is the wavelength;

in this case, smaller base d form a rough but clear scale of reference angles and the large base 2d form accurate but ambiguous scale of reference angles, converting the received signals in frequency, the selection voltage of the first intermediate frequency re-converting the frequency of the voltage of the first intermediate frequency measuring channel, the selection voltage of the second intermediate frequency, the multiplication with the voltage of the first intermediate frequency direction-finding channels, the allocation of the received voltage harmonic oscillations at the frequency of the second lo preserving phase relationships, measuring the phase difference between the harmonic oscillations and the voltage of the second local oscillator and the evaluation of the values of the azimuth and elevation of the source signal, the multiplication of the received signal of the first DF channel, voltage-th voltage harmonic oscillations at the frequency of the first local oscillator preserving phase relationships, the measurement of the carrier frequency of the received signal, the angle of sight and the difference of difference of phases between the first dynamical and measurement channels, as well as between the second and first dynamical channels in the azimuthal plane and the evaluation of their values, the distance to the radiation source signal, determining from the measured values of azimuth, elevation and range location of the radiation source signal, the multiplication of the voltage of the first intermediate frequency measuring channel voltage of the first intermediate frequency of the second and the fourth direction-finding channels located in the azimuthal and elevation planes, respectively, the allocation of the received voltage harmonic oscillations with frequencies equal to the difference between the Doppler frequency, evaluating the values of the angular velocities of the source signal in azimuth and elevation, the implementation in the measuring channel dual conversion frequency of the received signal using two reference frequencies and frequency stand, which is injected to determine the sign of the Doppler shift, the allocation of harmonic oscillations with the Doppler shift, the measurement of its frequency and the assessment of the magnitude and knowledge on the measured values of range, radial velocity and angular velocity in azimuth and elevation of the module of the velocity vector of the source signal in the measuring channel produce a false signal at the first intermediate frequency shift its phase by +180oand summed with the original false signal, thereby suppressing it, the voltage of the first local oscillator shifts the phase by +90ouse it to convert the frequency of the received signal at the carrier frequency, allocate the voltage of the first intermediate frequency shift its phase by +90oand summarize the source voltage of the first intermediate frequency obtained the total voltage of the first intermediate frequency Peremohy with the received signal at the carrier frequency emit harmonic voltage at the frequency of the first local oscillator, will detect and use it for permission to re-convert in frequency the total voltage of the first intermediate frequency.

The location and the module state vector of the radiation source, for example, a complex signal with phase shift keying (QPSK), and the suppression of additional receiving channels on the proposed method is carried out by performing the following sequence of operations.

< / BR>
0tTn,

where Un,n,n, Tnthe amplitude, frequency, initial phase, and duration of false signal (interference), accepted on channel direct transmission at a frequency of

2. Shift its phase by +180o< / BR>
< / BR>
0tTn.

3. Summarize the source of the false signal, thereby suppressing it.

4. Take FMN complex signals with unstable carrier frequency of five antennas 1-5, located in the geometric form of a right angle (Fig. 2), the top of which is placed the antenna 1 of the measuring channel, thus forming in each plane, two measurement bases d and 2d:

u1(t) = U1cos[(c)t+ak(t)+a1];

u2(t) = U2cos[(c)t+ak(t)+a2];

u3(t) = U3cos[(c)t+ak(t)+a3];

u4(t) = U4cos[(c)t+ak(t)+a4];

u5(t) = U5cos[(c)t+ak(t)+a5];

0tTc,

where U1-U5- amplitude signals;

c,1-5, Tc- carrier frequency, duration, and initial phase signals;

- instability of the carrier frequency due to various destabilizing factors, including the Doppler effect;

k(t) = {0,}UB><t<(k+1)and, i.e., at the boundaries between elementary parcels (k = 1,2,..., N-1);

andN - the length and number of basic assumptions which form the signal duration

5. Transform their frequency and emit a voltage of the first intermediate frequency:

< / BR>
< / BR>
< / BR>
< / BR>
< / BR>
0tTc,

where

< / BR>
< / BR>
< / BR>
< / BR>
K1- transfer coefficient of the frequency Converter;

the first intermediate frequency;

- the voltage of the first local oscillator, thereby forming the one measuring and four dynamical channel, two on each plane.

6. The voltage of the first local oscillator shifts the phase by +90o< / BR>
< / BR>
7. Use it to convert the frequency of the received signal at the carrier frequency.

u1(t) = U1cos[(c)t+ak(t)+a1], 0 t tc,

8. Allocate the voltage of the first intermediate frequency

< / BR>
0tTc.

9. Shift its phase by 90o< / BR>
< / BR>
0tTc.

10. Summarize the source voltage of the first intermediate frequency

0 t tc,

where

11. Received total voltage of the first intermediate frequency U(t) Peremohy with accepted safety on the frequency of the first lo

< / BR>
0 t tc.

13. Detects and use it for permission to re-convert in frequency the total voltage u(t).

14. In the measuring channel voltage u(t) the first intermediate frequency second time transform on the frequency using the voltage of the second lo:

< / BR>
where is the amplitude, frequency and initial phase of the voltage of the second local oscillator;

and allocate the voltage of the second intermediate frequency:

< / BR>
where

< / BR>
the second intermediate frequency;

< / BR>
15. Peremohy voltage of the second intermediate frequency measuring channel voltage of the first intermediate frequency direction-finding channels.

16. From the obtained stress emit harmonic oscillations at the frequency of the second local oscillator preserving phase relationships:

< / BR>
< / BR>
< / BR>
< / BR>
0 t tc,

where

< / BR>
< / BR>
< / BR>
< / BR>
d, 2d measuring base;

- the angular coordinates in azimuth and elevation planes.

17. Measure the phase difference1-4between harmonic oscillations u6(t) - u9(t) and the voltage of the second local oscillator and evaluate the values of the azimuth of the elevation angle of the source from which progeniem first intermediate frequency of the second dynamical channel in the azimuthal plane.

19. From the obtained voltage emit harmonic oscillation at a frequency ofG1the first local oscillator preserving phase relationships:

< / BR>
0tTc,

where

< / BR>
(Fig.3).

20. Measure the phase difference5between harmonic oscillation u10(t) and the voltage of the first lo uG1(t).

21. Measure the carrier frequency of the received signal and the difference of the difference of phases

< / BR>
Expressing sin1and sin3through the sides of right-angled triangles 11'AND, 22'AND 33'AND get

< / BR>
< / BR>
where D is the distance from the radiation source signal.

The above expression can be written in the approximate form:

< / BR>
< / BR>
The value of difference of difference of phases in approximate form as follows:

< / BR>
22. The desired distance to the radiation source signal estimate using the following formula:

< / BR>
23. For measured values of azimuth , elevation and distance D determines the location of the radiation source signal.

24. Measure the radial velocity of a source of the radiation signal. The specified dimension is based on the use of the Doppler effect.

The essence of it lies in the fact that the frequency fcpride relative to each other.

As we know from the General theory of relativity, the relationship between frequency fcand fjis determined by the ratio

< / BR>
where c is the speed of light;

V - full speed of movement of the radiation source signal;

radial component of velocity of the source signal (emitter). Since

< / BR>
< / BR>
the expression for the carrier frequency can be written as

< / BR>
Limited to the first summands in the right hand side of the last equality, we get

< / BR>
where Fg- Doppler shift frequency.

Replacing the exact ratio close causes a truncation error of measurement of radial velocity.

To measure the radial velocity of the emitter in the measuring channel is dual conversion of the received signal using two reference frequencies1f2and frequency stand F0that is administered to determine the sign of the Doppler shift Fg. The voltage of the first intermediate frequency at which the gain of the received signal, is determined by the difference

= fc- f1= f0+ Fg- f1,

where f1the frequency of the reference signal in the second frequency conversion of the received signal, has a frequency of

f2= f0- f1- F0.

After the second frequency conversion of the received signal are generated oscillation frequency

fISM= - f2= f0+ Fg- f1- f0- F0= Fg+ F0.

Depending, fISM> F0or fISM< F0determine the sign of the Doppler shift, and hence the direction of the radial velocity.

25. Measure the angular velocity of the emitter. These measurements in two planes based on the comparison of Doppler shifts in the two systems separated antennas, the base of which is oriented in space at an angle of 90o(Fig. 2). While derivatives are measured two guides of the cosines of:

< / BR>
< / BR>
From derivatives it is easy to go to the angular velocity in azimuth and elevation:

< / BR>
< / BR>
where is the difference between the Doppler frequencies in the azimuthal and Utamaro planes

< / BR>
< / BR>
Thus, to measure the angular velocities of the source signal, in addition to the Doppler difference frequency, it is necessary to measure and guide cones in the azimuthal and elevation planes.

On detected values of the angular speed is
26. The module of the velocity vector of the source signal

< / BR>
is the measurement result is six radio navigation options: three coordinates , D and three speeds

The proposed phase method of direction finding can be implemented in the phase direction finder, a block diagram is shown in Fig. 1. The mutual arrangement of the receiving antennas is shown in Fig. 2 and 3.

Frequency chart explaining the principle of education for more channels, shown in Fig. 4.

The phase signal includes receiving antennas 1-5, 6-10 amps high frequency first local oscillator 11, mixers 12-16, 23, 51, 53, 60, amplifiers 17-21, 52, 61 first intermediate frequency, a second local oscillator 22, an amplifier 24, a second intermediate frequency, multiplier products 25-29, 44, 45, 64, narrowband filters 30-34, 46, 47, 54, 56, 65, phasemeter 35-40, the counters 41, 48, 49, 55, computational block 42, block 43 of the Desk, the adders 58, 63, an inverter 57, phasers 59 and 62 +90, the amplitude detector 66 and the key 67.

Measuring channel consists of a series of antennas 1, amplifier 6 high-frequency, narrow-band filter 56, a phase inverter 57, adder 58, a second input connected to the output of the amplifier 6 high frequency, the shift of the Oh frequency, adder 63, the multiplier 64, a second input connected to the output of the adder 58, a narrow-band filter 65, the amplitude detector 66, the key 67, a second input connected to the output of the adder 63, a mixer 23, a second input connected to the output of the local oscillator 22, an amplifier 24, a second intermediate frequency and the frequency of 41.

Each DF channel consists of a series of 2 antennas (3, 4, 5), amplifier 7 (8, 9, 10) high frequency mixer 13 (14, 15, 16), a second input connected to the output of the local oscillator 11, the amplifier 18 (19, 20, 21) of the first intermediate frequency, multiplier 25 (26, 27, 28), a second input connected to the output of the amplifier 24, a second intermediate frequency, narrow-band filter 30 (31, 32, 33) and phase meter 35 (36, 37, 38), a second input connected to the output of the local oscillator 22. The output of the amplifier 7 high frequency sequentially connected to the multiplier 29, the second input connected to the output of the amplifier 19, a narrow-band filter 34, the phase meter 39, a second input connected to the output of the local oscillator 11, the phase meter 40, a second input connected to the output of the phase meter 35, the computing unit 42, a second input connected to the output of the phase meter 39, and a third input connected to the output of the counter 41, and nl is significant. The output of the amplifier 17, the first intermediate frequency connected in series multiplier 44, a second input connected to the output of the amplifier 19, the first intermediate frequency, narrow-band filter 46 and the counter 48, the output of which is connected to the fourth input of the computing unit 42 and the sixth input of the recording unit 43. The output of the amplifier 17, the first intermediate frequency connected in series multiplier 45, a second input connected to the output of the amplifier 21 and the first intermediate frequency, narrow-band filter 47 and the counter 49, the output of which is connected to the fifth input of the computing unit 42 and the seventh input of the recording unit 43.

The output of the amplifier 6 high frequency connected in series mixer 51, a second input connected to the first output unit 50 reference frequencies, the amplifier 52, the first intermediate frequency, a mixer 53, a second input connected with the second output unit 50 of the reference frequency, narrow-band filter 54 and the counter 55, the output of which is connected to the sixth input of the computing unit 42 and the eighth input unit 43 of the Desk.

The phase signal is as follows.

Accept FMN signals from the outputs of the antennas 1-5 through gain is correspondingly the voltage of the first local oscillator . In this case, the adder 58 operates only one shoulder. The frequency notch filters 56 and 65 is as follows:

< / BR>
At the outputs of mixers 12-16, 60 are formed voltage Raman frequencies. Amplifiers 17-21, 61 are voltage, only the first intermediate frequency. At the output of the adder 63 is formed, the total voltage u(t), in which the multiplier 64 is multiplied by with the received signal u1(t). A narrow-band filter 65 is allocated harmonic voltage u12(t) at the frequency of the first local oscillator 11. This voltage is detected by the amplitude detector 66 and is supplied to the control input of the key 67, opening it. In the initial state, the key 67 is always closed. The total voltage of the first intermediate frequency u(t) from the output of the adder 63 through the public key 67 is supplied to the first input of the mixer 23, the second input of which is applied the voltage of the second local oscillator 22. At the output of mixer 23 is formed voltage Raman frequencies. The amplifier 24 is allocated the voltage of the second intermediate frequency, which is fed to the second inputs of the multiplier products 25-28, at the first input of which receives the voltage of the first intermediate frequency. From the obtained naprej to the first inputs of the phase meter 35-38, on the second inputs of which are supplied with voltage of the local oscillator 22. The measured phase shifts1,2,3,4register unit 43 of the Desk.

The work described above, the phase of the signal, corresponds to the case of reception of signals through the main channel at a frequency ofc(Fig. 4).

If a false signal (interferer) is accepted by the channel direct transmission on the frequency it is suppressed by a chain consisting of a narrow-band filter 56, a phase inverter 57 and the adder 58. When this is implemented photocomposition method.

If a false signal (interferer) is taken as the image channel frequency 3< / BR>
u3(t) = U3cos(3t+a3), 0 t t3,

in measuring the channel it is using the mixers 12 and 60 is converted by the frequency. Amplifiers 12 and 61 are highlighted in the following voltages:

< / BR>
< / BR>
0 t t3,

where

- intermediate frequency;

< / BR>
The voltage output from the amplifier 61 of the first intermediate often you received at the input of the phase shifter 62 +90o, the output of which produces a voltage

0 t t3.

The voltage received at the two inputs of the adder 63, at its output out. Therefore, a false signal (the room is ensational method.

If a false signal (interferer) is received by the first Raman channel at a frequency , it also suppressed photocomposition method.

If a false signal (interferer) is received by the second Raman channel at a frequency of

< / BR>
the mixers 12 and 60, it is converted to the following voltages:

< / BR>
< / BR>
where

the first intermediate frequency;

< / BR>
The voltage output from the amplifier 61 of the first intermediate frequency is fed to the input of the phase shifter 62 90o, which produce a voltage

< / BR>
Voltage is fed to two inputs of the adder 63, the output of which is formed by the total voltage

< / BR>
where

This voltage is fed to the second input of the multiplier 64, the first input of which is received a false signal (interferer) . In the result of the multiplication of these stresses is formed harmonic voltage

< / BR>
where

which does not fall within the bandwidth of the narrow-band filter 65. The key 67 is not opened and a false signal (interferer) taken by the second Raman channel at the frequency of the suppressed. This method is used narrowband filtering.

The phase meter 39 is measured phase shift5. The difference is the manner defined by the distance D from the radiation source complex signal, and then is logged in block 43 of the Desk. In the last determined location of the radiation source complex signal.

The maximum error in determining the distance D is estimated by the expression:

< / BR>
For measured values of azimuth , elevation and distance D is determined by the location of the radiation source signal.

To measure the radial velocity of the emitter voltage U1(t) from the output of the amplifier 6 high frequency is supplied to the first input of the mixer 51, the second input of which is applied the first reference frequency f1. At the output of mixer 51 are formed voltage Raman frequencies. Amplifier 52 is allocated the voltage of the first intermediate frequency

< / BR>
which is supplied to the first input of the mixer 53. and the second input to the mixer 53 is supplied reference signal, the frequency of which is determined by the expression

f2= f0- f1- F0.

where F0- frequency stand, which is introduced to determine the sign of the Doppler shift Fg.

At the output of mixer 53 is formed of the oscillation frequency

fISM= - f2= f0+ Fg- f1- f0+ f1+ F0= Fg+ F0,

allocated ut is elicina and the sign of the Doppler shift estimate the magnitude and direction of the radial velocity of the source signal.

To measure the angular velocity of the emitter along the azimuth and elevation angle voltage, the outputs of the amplifiers 17, 19 and 20 of the first intermediate frequency is fed to two inputs of the multiplier products 44, 45. While narrowband filters 46 and 47 produce harmonic oscillations at frequencies equal to the difference of the Doppler frequency in the azimuthal and elevation planes:

< / BR>
< / BR>
These differential Doppler frequency measured by the frequency 48 and 49, respectively, are received in the computing unit 42 and fixed unit 43 of the Desk.

In the computing unit 42 are determined by the tangential components of the velocity vector of the emitter:

< / BR>
and the module of the velocity vector of the emitter

< / BR>
also fixed unit 43 of the Desk.

Thus, the proposed method is compared with the base provides increased noise immunity and accuracy of phase measurements of the emitter. This is achieved by the suppression of spurious signals (noise), accepted on channel direct transmission on the frequency and the image frequency at a frequency of3used photocomposition method. To suppress false signals (interference), adopted by Raman channels used narrowband method is built in the form of a geometrical straight angle, in the top of which is placed the antenna of the measuring channel, common to the four dynamical channels located in the azimuthal and elevation planes, two on each plane, thus forming in each plane, two measurement bases d and 2d, between which establish the inequality

< / BR>
where is the wavelength,

in this case, smaller base d form a rough but clear scale of reference angles and the large base 2d form accurate but ambiguous scale of reference angles, converting the received signals in frequency, the selection voltage of the first intermediate frequency re-converting the frequency of the voltage of the first intermediate frequency measuring channel, the selection voltage of the second intermediate frequency, the multiplication with the voltage of the first intermediate frequency direction-finding channels, the allocation of the received voltage harmonic oscillations at the frequency of the second lo preserving phase relationships, measuring the phase difference between the harmonic oscillations and the voltage of the second local oscillator and the evaluation of the values of the azimuth and elevation of the source signal, the multiplication of the received signal of the first DF channel, voltage-th voltage harmonic oscillations at the frequency of the first local oscillator preserving phase relationships, the measurement of the carrier frequency of the received signal, the angle of sight and the difference of difference of phases between the first dynamical and measurement channels, as well as between the second and first dynamical channels in the azimuthal plane and the evaluation of their values, the distance to the radiation source signal, determining from the measured values of azimuth, elevation and range location of the radiation source signal, the multiplication of the voltage of the first intermediate frequency measuring channel voltage of the first intermediate frequency of the second and the fourth direction-finding channels located in the azimuthal and elevation planes, respectively, the allocation of the received voltage harmonic oscillations with frequencies equal to the difference between the Doppler frequency, evaluating the values of the angular velocities of the source signal in azimuth and elevation, the implementation in the measuring channel dual conversion frequency of the received signal using two reference frequencies and frequency stand, which is injected to determine the sign of the Doppler shift, the allocation of harmonic oscillations with the Doppler shift, the measurement of its frequency and the assessment of the magnitude and knowledge on the measured values of range, radial velocity and angular velocity in azimuth and elevation of the module of the velocity vector of the source signal, characterized in that in the measuring channel produce a false signal at the first intermediate frequency shift its phase by +180 and summed with the original false signal, thereby suppressing it, the voltage of the first local oscillator shifts the phase by +90, use it to convert the frequency of the received signal at the carrier frequency, allocate the voltage of the first intermediate frequency shift its phase by +90 and summed with the source voltage of the first intermediate frequency, received total voltage of the first intermediate frequency Peremohy with the received signal at the carrier frequency emit harmonic voltage at the frequency of the first local oscillator, will detect and use it for permission to re-convert in frequency the total voltage of the first intermediate frequency.

2. The phase signal containing measuring and four dynamical channel while measuring channel consists of series-connected antenna and amplifier of high frequency series of the first mixer, the second input is SKN included sixth mixer, a second input connected to the output of the second local oscillator, the amplifier of the second intermediate frequency and the first frequency, each of the direction-finding channel consists of series-connected antenna, amplifier high frequency mixer, a second input connected to the output of the first local oscillator, amplifier first intermediate frequency, multiplier, a second input connected to the output of the amplifier of the second intermediate frequency measuring channel, notch filter and phase meter, a second input connected to the output of the second local oscillator, connected in series to the output of the amplifier high frequency of the first DF channel fifth multiplier, a second input connected to the output of the amplifier, the first intermediate frequency of the second direction-finding channel, the fifth narrowband filter, the fifth phase meter, a second input connected to the output of the first local oscillator, the sixth phase meter, a second input connected to the output of the first phase meter, computing unit, a second input connected to the output of the fifth phase meter, and a third input connected to the output of the first frequency and the recording unit, second, third, fourth and fifth inputs of which are connected to the outputs of the first, the first intermediate frequency measuring channel of the sixth multiplier, a second input connected to the output of the amplifier, the first intermediate frequency of the second direction-finding channel, the sixth narrowband filter and the second frequency, the output of which is connected to the fourth input of the computing unit and the sixth input of the recording unit, sequentially connected to the amplifier output of the first intermediate frequency measuring channel of the seventh multiplier, a second input connected to the output of the amplifier, the first intermediate frequency DF fourth channel, the seventh narrowband filter and the third frequency, the output of which is connected to the fifth input of the computing unit and the seventh input of the recording unit, sequentially connected to the output of the amplifier high-frequency measuring channel seventh mixer, the second input is connected to the first output of the reference frequency, the sixth power of the first intermediate frequency, the eighth mixer, a second input connected to the second output of the reference frequency, the eighth narrowband filter and the fourth frequency, the output of which is connected to the sixth input of the computing unit and to the eighth input of the recording unit, characterized in that it is equipped with the ninth and tenth narrowband file, two phasers to +90, the eighth multiplier, the amplitude detector and the key, and to the output of the amplifier high-frequency measuring channel connected in series ninth notch filter, phase reverse and the first adder, a second input connected to the output of the amplifier high-frequency measuring channel, and the output connected to the first input of the first mixer of the measuring channel, the output of the first adder connected in series ninth mixer, a second input connected through a first phase shifter to +90 with the second output of the first local oscillator, the seventh power of the first intermediate frequency, a second phase shifter to +90, a second adder, a second input connected to the output of the amplifier, the first intermediate frequency measuring channel, the eighth multiplier, a second input connected to the output of the first adder, the tenth notch filter, peak detector, a second input connected to the output of the second adder, and the output connected to the first input of the sixth mixer measuring channel.

 

Same patents:

The invention relates to electrical engineering and can be used for detection and estimation of the number of spatially-correlated radiation sources in RDF, radar, sonar, geophysical and other multi-channel systems, passive and active locations that use antenna arrays

The phase finder // 2169377
The invention relates to the field of radio and can be used for determining the angular coordinates of the source of continuous harmonic signal

The phase signal, // 2165628
The invention relates to radar, radio navigation and can be used for determining the angular coordinates of the radiation source photomanipulating (QPSK) signal

The invention relates to radar, radio navigation and can be used to determine the location and movement of radiation sources of complex signals

The invention relates to measurement technology and automation

The phase signal, // 2143707
The invention relates to the field of radar and radio navigation, in particular the phase direction finders

The invention relates to the radiolocation and radionavigation

Multi-finder // 2110809
The invention relates to radio direction-finding with the measurement of the phase shift removed from the diversity antenna signals and is intended for use in the system of direction finding high-speed low-flying targets, in particular in the system of active protection of the tank against tank shells

Direction finder // 2073880

The phase signal, // 2069866

FIELD: finding of azimuth of radio emission source (RES) in wide-base direction finding systems.

SUBSTANCE: angle of azimuth of RES is measured with high degree of precision due to elimination of methodical errors in direction finding caused by linearization of model electromagnet wave propagation wave front. As surface of RES location the plane is used which has RES line of location which has to be crossing of two hyperbolic surfaces of location corresponding to difference-time measurement. Method of RES direction finding is based upon receiving its signal by three aerials disposed randomly, measuring of two time differences of RES signal receiving by aerials which form measuring bases and subsequent processing of results of measurement to calculate values of RES angles of azimuth and coordinates of point through which the RES axis of sight passes. The data received are represented in suitable form. Device for realization of the method has three aerials disposed at vertexes of random triangle, two units for measuring time difference of signal receiving, computing unit and indication unit. Output of common aerial of measuring bases is connected with second inputs of time difference meters which receive signals from outputs of the rest aerials. Measured values of time differences enter inputs of computing unit which calculates values of RES angle of azimuth and coordinates of point through which the RES axis of sight passes. Data received from output of computing analyzing unit enter indication unit intended for those data representation.

EFFECT: widened operational capabilities of direction finder.

2 cl, 7 dwg

FIELD: radio engineering, applicable for location of posthorizon objects by radiations of their radars, for example, of naval formations of battle ships with operating navigational radars with the aid of coastal stationary or mobile passive radars.

SUBSTANCE: the method consists in detection of radiations and measurement of the bearings (azimuths) with the use of minimum two spaced apart passive radars, and calculation of the coordinates of the sources of r.f. radiations by the triangulation method, determination of location is performed in three stages, in the first stage the posthorizon objects are searched and detected by the radiation of their radars at each passive radar, the radio engineering and time parameters of radar radiations are measured, the detected radars with posthorizon objects are identified by the radio engineering parameters of radiations and bearing, and continuous tracking of these objects is proceeded, the information on the objects located within the radio horizon obtained from each passive radar is eliminated, the working sector of angles is specified for guidance and tracking of the selected posthorizon object, in the second stage continuous tracking of one posthorizon object is performed at least by two passive radars, and the time of reception of each radar pulse of this object is fixed, in the third stage the period of scanning of this radar, the difference of the angles of radiation by the main radar beam of each passive radar and the range to the posthorizon object with due account made for the difference of the angles of radiation are determined by the bearings (azimuths) measured by the passive radar and the times of reception of each pulse of the tracked radar. The method is realized with the aid at least of two spaced apart passive radars, each of them has aerials of the channel of compensation of side and phone lobes, a narrow-band reflector-type aerial, series-connected noiseless radio-frequency amplifier, multichannel receiving device, device of primary information processing and measurement of carrier frequency, amplitude and time of reception of signals of the detected radar, device of static processing of information and measurement of the bearing, repetition period, duration of the train and repetition of the pulse trains and a device for calculation of the difference of the angle of radiation of the aerials of the passive radars by the detected radar.

EFFECT: reduced error of measurement of the coordinates of posthorizon sources of radio-frequency radiations.

3 cl, 5 dwg

FIELD: radio engineering, applicable in electromagnetic reconnaissance, radio navigation and radio detection and ranging for determination of the direction to the source of radiation or reflection of radio waves.

SUBSTANCE: the phase direction finder has two antennas, two receiving paths, three phase shifters, two phase detectors, two limiters, three adders, two modulus computation devices, subtracting device, amplifier, comparator, gate circuit and an oscillator.

EFFECT: enhanced accuracy of direction finding and excepted its dependence of the attitude of the object of direction-finding.

2 cl, 10 dwg

FIELD: radio engineering.

SUBSTANCE: device has the first, the second and the third receiving antennas, the first, the second and the third high frequency amplifiers, the first and the second heterodynes, the first, the second and the third mixers, the first, the second and the third multipliers, the first, the second, the third and the fourth narrowband filters, the first, the second and the third intermediate frequency amplifiers, frequency multiplier by two, the first, the second and the third phase detectors, the first and the second correlator units, the first, the second, the third and the fourth threshold units, the first, the second, the third and the fourth keys and unit for recording.

EFFECT: wide range of functional applications.

3 dwg

FIELD: the proposed mode and arrangement refer to the field of radio electronics and may be used for definition of position of sources of emitting complex signals.

SUBSTANCE: the phase direction finder realizing the proposed phase mode of direction finding, has receiving aerials, receivers and a supporting generator, an impulse generator, an electronic commutator, a phase changer on 90, a phase detector and an indicator, a heterodyne, a mixer, an amplifier of an intermediate frequency, multipliers and band filters and a line of delay.

EFFECT: elimination of antagonism between requirements to accuracy of measuring and unique angle reading at phase mode of direction finding of sources of emitting of complex signals.

2 cl, 2 dwg

FIELD: the invention refers to the field of radio technique and may be used in range-difference systems of definition of the position of the sources of radio emissions.

SUBSTANCE: the mode is based on measuring of two differences of distances Δr12 and Δr13 to two pairs of mobile supporting points {O1,O2}and {O1,O3 , } the coordinates ,j= 1,2,3 supporting points Oj in the moment of time of measuring of distances, then the vector of measured values is transformed into the vector of the coordinates of the three points F1,F2 and M belonging to a hyperbolina: the vector is stored and transmitted along the channels of transmitting information into the center of processing information for using it in quality of initial data at solution a range-difference navigational task; at that the points F1 and F2 defines the focuses of the hyperbolina if it is a hyperbola or an ellipse or a focus and its projection on a directrix if it is a parabola and the third point belongs to the hyperbolina in such a manner that the position of its project on the direct F1F2 defines the form of the curve of the second order.

EFFECT: decreases volume of stored and transmitted data.

5 dwg

FIELD: radio electronics, applicable for passive radio monitoring in multi-channel system designed for direction finding of several sources of radio emission simultaneously getting into the reception zone.

SUBSTANCE: expanded functional potentialities by way of direction finding in two planes of several sources of radio emission simultaneously getting into the reception zone.

EFFECT: expanded functional potentialities.

2 dwg

FIELD: finding coordinates of radio source.

SUBSTANCE: as planes of position of radio source the planes are used, which have line of position of radio source, which has to be crossing of two hyperbolic surfaces pf position corresponding to time-difference measurements. Method is based upon reception of signal of radio source by four aerials, on measurement of three differences in time of reception of radio source signal by aerials, which aerials form measuring bases, upon subsequent processing of results of measurements for calculation of values of parameters of position of radio source and for calculating coordinate of radio source as crossing point of three planes of position. Device for realization of the method has four aerials which aerials form three pairs of measuring bases, which bases are disposed in non-coincident planes, three calculators for calculating parameters of position of radio source, calculator of radio source coordinates made in form of unit for solving system of linear equations and indication unit.

EFFECT: precise measurement of linear coordinates of object.

2 cl, 8 dwg

FIELD: radio detection and ranging, radio navigation, applicable for determining the angular co-ordinates of the signal radiation source.

SUBSTANCE: the claimed method is realized with the aid of a device having three receiving derails, three receivers, two phase-meters, computer, adder and a recording unit connected in a definite way.

EFFECT: enhanced range of one-valued measurement of angles at a small length of the rough measuring base.

3 dwg

FIELD: proposed invention refers to radiolocation and may be used for definition of position and movement of sources of radiation of complex signals.

SUBSTANCE: achieved technical result of invention is increase of trustworthiness of reception of useful signals with a priori known carrier frequency and removal of ambiguity of direction finding by suppression false signals (interference) not interesting for radio control and coming from other directions. At that proposed arrangement has receiving antenna with circle diagram of radiation pattern , receiving antenna with cardioidic diagram of radiation pattern, block for control over diagram of radiation pattern, first and second receiving sets, division block, threshold block, former of control pulse, first and second keys, meter of frequency, memory block, block for comparison of codes, motor and register block.

EFFECT: increases trustworthiness of direction finding.

4 dwg

Up!