Adaptive partitioning in the system spread spectrum communications

 

(57) Abstract:

System and method for adaptive partition on sector channel resources in a digital cellular communication system. The system uses the antenna array to generate at least first and second electromagnetic beams for receiving a first information signal transmitted by a specific user from multiple users, and receiving the first and second received signals. Then from the first and second received signals using diagrammable circuit and the switching matrix is formed by the first set lucabrasi signals. Provided demodulates receivers for the demodulation of at least first and second lucabrasi signals contained in the first set lucabrasi signals, obtaining thus the first and second demodulated signals. In addition, the system includes a tracking scheme for tracking multipath information signals taken from different positions and at different angles. Achievable technical result is the creation of a method of adaptive partitioning into sectors, allowing selective tracking and reception of direct and multipath signals is s invention relates to communication systems, using signals with spread spectrum and, in particular, to a new improved method and apparatus for adaptive partitioning into sectors in the system of spread spectrum communications.

II. Description of the prior art

Known communication systems that allow the transfer of information signals from the base station to the location of the individual user or subscriber. For the transfer of such information signals via the communication channels connecting the base station and the location of the users, uses both analog and digital methods. Digital methods differ in a number of advantages over analog, including, for example, reduced susceptibility to noise and mutual interference, increased throughput and improved protection against unauthorized access through the use of encryption.

When transmitting the information signal over the communication channel in either direction information signal is first converted into the format suitable for efficient transmission over the channel. Conversion or modulation of the information signal includes modifying a parameter of the carrier in accordance with an information signal such Oia channel. In the place of reception of the original message signal is restored from copies of the modulated carrier received after its propagation through the communication channel. Such reversal is usually performed using process, the reverse process of modulation used for the transmission of the message.

Modulation also facilitates multiplexing, i.e. simultaneous transmission of multiple signals over a common channel. Multiplex communication systems typically contain many remote subscriber devices that require short sessions with breaks, not continuous access to the communication channel. Systems designed for communication with the selected subset of the entire set of subscriber devices, referred to as systems with multiple (shared) access.

A particular type of communication system with multiple access, known as the modulation system with multiple access, code-division multiplexing (mdcr), can be implemented using the extension methods of the spectrum. In systems with spread spectrum used modulation method leads to a distribution of a transmitted signal in a wide band of frequencies within the channel. Other ways is) and multiple access frequency division multiple access (FDMA equipment). However, the modulation method spread spectrum type mdcr has significant advantages compared to other ways of modulation for communication systems with multiple access. The use of the method mdcr in the communication system with multiple access are disclosed in U.S. patent N 4901307 dated February 13, 1990 on "communication System with multiple access spread spectrum using satellite or terrestrial repeaters", assigned to the assignee of the present invention.

In U.S. patent N 4901307 disclosed method multiple access, in which a large number of mobile users, each having a transceiver, perform the exchange of information through satellite repeaters or terrestrial base stations using signals spread spectrum communications mdcr-type. When the communication method mdcr frequency spectrum can be reused, which allows to increase the throughput to users of the system. Method mdcr provides higher spectrum efficiency compared to that which can be provided by different multiple access methods.

For specific Sotovaya is carried out by distributing each of the signal being transmitted in the corresponding bandwidth of the channel using a unique extender user code. In such systems mdcr code sequence used to spread spectrum, constructed from two different types of sequences, each of which has different properties for different functions. For example, the sequence of the first type are pseudosolenia (PN) codes I (inphase) and Q (quadrature) channel that is shared by all signals in the cell or sector. In addition, each user can be identified by a unique long PN code, which is usually longer than the PN codes of the I and Q channels.

In Fig. 1 shows an example of a cell 10 of a cellular communication system with mdcr, in which there are a number of stationary or mobile subscriber device 12 and base station 14. Subscriber units 12 are grouped into first, second and third sectors of the users 16, 18 and 20, each of which supports an equivalent number of traffic channels. The base station 14 can contain a set of antennas with a fixed position pattern (not shown) intended to facilitate communications with the subscriber devices in each user sector. As an option to split the cell into three separate user s is that that base station 14 typically contains a receiver with diversity, providing separate individual multipath reflected signals PSH-signal spread spectrum transmitted by each subscriber device 12. Multibeam echo signals may be caused by reflection of transmitted user signal from objects in the path of signal propagation. Then individual multipath signals are aligned in time (combined) on the specific findings receiver designed for receiving particular multipath signals, and are summed to improve the signal-to-noise ratio. If the cell 10 is divided into a sufficiently large number of sectors (for example, six sectors, each sector is allocated a relatively narrow beam. Unfortunately, increasing the number of sectors may hinder the reception of multipath signals outside of the directional antenna of each sector, which leads to an undesirable decrease in signal-to-noise ratio.

Accordingly, the present invention is to provide a method of adaptive differentiation by sector, allowing selective tracking and reception of direct and multipath signals transmitted to the floor is Britanie provides a system and method of adaptive separation of sector resources channels of digital communication systems, for example, cellular communication systems. The system includes an antenna device for creating at least first and second electromagnetic beams for receiving a first information signal transmitted by one particular user of the multiple users, and receiving the first and second received signals. Then from the first and second received signals generates a first set diagrammatic signals.

There demodulate receiver for demodulation of at least first and second diagrammatic signals contained in the first set diagrammatic signals to obtain first and second demodulated signals. The system also includes a tracking for tracking multipath information signals received from different positions and at different angles of arrival, based on a comparison of the first and second demodulated signals.

Brief description of drawings

Additional objectives and features of the invention are disclosed in the following detailed description and the claims, and illustrated in the drawings, which represent the following:

Fig. 1 is an example communication system with multiple non-the supervising system spread spectrum communications, in which the transmitted signals of the direct and multipath propagation are taken in accordance with this invention;

Fig. 3 is a block diagram of the transmitter spread spectrum, suitable for use in the preferred embodiment of the invention;

Fig. 4 is a block diagram of an example implementation of the radio frequency transmitter;

Fig. 5A is a block diagram of a reception system of a base station with adaptive partitioning according to this invention;

Fig. 5B is a block diagram of the receiving station that uses a specific implementation of the channel unit;

Fig. 5C is a block diagram of the receiving system, base station, antenna containing the grating is placed at a remote position;

Fig. 5 is a block diagram of RAKE receiver with adaptive formation pattern for handling set converted to a lower frequency digitized signals rays antennas;

Fig. 6 is an example implementation of the receiving antenna array, containing the antenna elements to receive both horizontally and vertically polarized signals;

Fig. 7 - circuit switches in the switching matrix to provide a single path signal propagation for this the receiver with diversity, included in the reception system of a base station;

Fig. 9 is an example of the implementation of the processor right/left beam;

Fig. 10 is a block diagram of the accumulating adder tracking beam associated with the first receiving channel in the receiver with diversity;

Fig. 11 is a schematic representation of a circular antenna array.

Detailed description of preferred embodiments of the invention

1. Introduction

As described below, the present invention relates to adaptive control of directional diagrams generated by the one or more antenna arrays in the system spread spectrum communications. In a preferred embodiment, one or more antenna arrays are grouped in the base stations of the cells of the cellular communication system. According to this invention, for receiving both direct and multipath transmitted signals from the subscriber device associated with the individual subscribers of the system there are separate sets of rays. A new scheme tracking allows you to track the direct and multipath signals transmitted from the subscriber point, both in time and in space. As will be described below, the tracking time is performed by adjusting f is the results of demodulation of the received signals.

In Fig. 2 shows a communication system 20 spread spectrum according to this invention. Within the coverage area of the communication system 20 are a number of stationary and mobile subscriber device 22, the first and second base stations 24 and 26 and the control station 30. Each base station 24 and 26 includes an antenna array (not shown) for receiving signals from the subscriber device 22. In the system 20, each subscriber paragraph 22 allocated a unique pseudo-random code to distinguish the signals of the users are transmitted over multiple channels of traffic associated with the subscriber device 22. Such a distinction is ensured, even if all channels of the traffic system is transmitted on a single RF channel.

As shown in Fig. 2, the information signal S transmitted subscriber device 22a falls, which is situated near the first object 34 (e.g., building). It is seen that the signal S is received by the direct path of distribution of the base stations 24 and 26, while the first multipath component (Sm1) of the signal S is reflected by the object 34 to the base station 26. According to this invention, the signals S and Sm1 are monitored respectively by the base stations 24 and 26 both in time and in proslavlenija 30. In the control station 30 demodulated signals are aligned in time and added in the receiver with diversity spread spectrum. A variant of the preferred embodiment of such a receiver with diversity are described in detail below.

According to this invention antenna array each base station forms a pattern, which differs in that it contains a set of related electromagnetic rays (petals), which may overlap in space. For separate tracking and reception of signals S and Sm1 in the base station 26 is provided by the first and second subsets of rays. In a preferred embodiment, different subsets of rays are allocated dynamically for election tracking and reception of signals S and Sm1 in accordance with change of the angle of arrival of the rays at the base station 26. These changes can occur, for example, due to movement of the subscriber device 22a or move any object 34. Such changes of the angle of arrival may be the result of movement of the base station 26 in those embodiments where, for example, a base station is deployed at the orbital satellite.

In the base station 26 includes a receiver with diversity, the block for the reception of multipath signal Sm1. After modulation of received signals in each channel using PN code associated with the subscriber device 22a, the demodulated signals are aligned in time and summed up. It provides the signal-to-noise ratio of the information signal extracted from the total signal, as compared with the case where the receive signal by using a signal received through a single pathway.

II. Detailed description

A. signal Transmission spread spectrum

In Fig. 3 shows a block diagram of the transmitter spread spectrum suitable for use in the subscriber device 22 (Fig. 2A-B). In the preferred embodiment, to provide a suitable signal-to-noise ratio in the channel service unit - base station" or "back" channel, used this form of orthogonal signaling as binary, Quaternary, or C-ranks. It is proved that the methods of orthogonal C-ranks signaling is less sensitive to distortion of signals due to Rayleigh fading and the like, than, for example, involving the use of canvasnational (Costas) diagram of the carrier recovery or Spasenie "signal to noise", for example, in embodiments, based on the use of base stations orbiting satellites.

In the transmitter according to Fig. 3 data bits 100, consisting, for example, from the speech converted into data using a vocoder, served in the encoder 102, where these bits are subjected to convolutional coding with rate of the input data. If the rate of information bits is less than the bit rate of the processing of the encoder 102 may be used by copying the code symbols, when the encoder 102 copies the bits of the input data 100, in order to create duplicated data stream with a bit rate that is coincident with the operating speed of the encoder 102. In the present embodiment, the encoder 102 receives data bits 100 with a nominal bit rate (Rb) 9.6 kbit per second and generates Rb/r symbols per second, where "r" denotes the code rate (e.g., 1/3) of the encoder 102. Then the encoded data are fed to the interleaver 104, where they block interspersed.

In 64 hexadecimal (i.e., C=64) orthogonal modulator 106 characters are grouped into a character combination that contains log2C characters, with a speed of (1/r)(Rb/log2C) character combinations per second, and there are C possible combinations. In the preferred embodiment, each character whom the Walsh contains 64 binary bits or "chip" (element), and the result is a set of 64 Walsh codes of length 64. 64 orthogonal code correspond to Walsh codes from Hadamard matrix 64x64, where the Walsh code is a single line or column of the matrix.

The Walsh sequence generated by the modulator 106, is fed to the logical element exclusive OR 108, where it is then "imposed" or multiplied by the adder with the PN code unique to a particular subscriber paragraph 22. Such a long PN code is generated with the speed Rc oscillator the long PN code 110 in accordance with the mask long PN code of the user. In this example, the long code generator 110 operates with a frequency 1,2288 MHz (Rc = 1,2288 MHz), so as to form four PSH-item one item Walsh.

In Fig. 4 shows an example implementation of a radio frequency (RF) transmitter 150. When using multiple access code division multiplexing mdcr spread spectrum pair of short PN sequences PNIand PNQserved respectively by the PN generatorI152 and generator PNQ154 adders "exclusive OR" 156 and 158. Sequence PNIand PNQare respectively the in-phase (I) and quadrature (Q) channels of communication and have a length (32 what other code extended sequence 160 and Q-channel code extended sequence 162 pass through the filter bandwidth of the modulating signal spectrum group 164 and 166. Then the filtered Q-channel sequence may be delayed by 1/2 PSH-element, in order to compensate for the nonlinearity of the RF amplifier.

Digital to analogue Converter (DAC) 170 and 172 are provided for converting respectively the digital I-channel and Q-channel information in analog form. Analog signals generated by the DAC, served together with bearing signals of the local oscillator cos(2ft) and sin(2ft) respectively to the mixers 188 and 190, where they are mixed and fed to the adder 192. Quadrature carrier signals sin(2ft) and cos(2ft) is fed from a suitable source of carrier frequency (not shown). These mixed signals to intermediate frequency (if) are summed in the adder 192 is fed to the mixer 194.

The mixer 194 mixes total signal with an RF signal from the frequency synthesizer 196, so as to ensure the conversion frequency to band RF. The RF signal includes in-phase (I) and quadrature (Q) components and can then be passed through a band-pass filter and fed to the RF amplifier (not shown). It should be clear that in various embodiments, the RF transmitter 150 may be used various ways of summing, mixing, filtering, and sileby coding and modulation, in some alternative implementations can improve the performance of the system.

B. General description of the receiving system, the base station

In Fig. 5A shows a block diagram of a reception system of a base station 210, corresponding to this invention. In the embodiments according to Fig. 5A and 5B antenna array of the base station is located in the same place, where the signal processing unit receiving system 210. As described below with reference to figures 5C and 5D, the antenna array may be, alternatively, placed in a remote location, and communication with the rest of the receiving system may be implemented using a fiber-optic line or other similar means.

In accordance with Fig. 5A, the M-element antenna array (not shown) outputs the signals in the set of M signal tyres 212. In this embodiment, antenna array contains multiple (M) Omni-directional antenna elements, evenly spaced on a circular periphery, thereby allowing reception of signals coming from any direction. Detailed description of example circular antenna is given below in section F.

As shown in Fig. 5A, the signal bus 212 is connected to the inverter with penii in the set of signals of the inverter 218. Then each of the signals of the inverter 218 is sampled using a separate analog-to-digital Converter (ADC), which generally presents the ADC 220. ADC 220 with frequency, which in this example is approximately equal to four times the frequency of the PN expansion, generates a set of M complex digital signals (Ii, Qi), where i = 1 to M. Thus, in the example implementation, the sampling rate is 4 1,228, or 4,912 MHz. The sampling frequency may be reduced to approximately the Nyquist frequency, if together with ADC 220 to use the interpolating filter.

Digital signals (Ii, Qi) served in diagrammatology circuit 224, designed to produce a set of N digital beam signals Bzwhere z = 1 to N and N = (L) (M). Each of the N beam signals Bzis formed in the following way

< / BR>
where each weighting factor qizcontains a complex number. As described below, the weights qizare selected so that each beam signal Bzconsistent with the desired directivity of the receiving antenna, formed by the M-element antenna array. The shape and direction of the antenna beam associated with each signal Bzcan be adapco, the parameter L can be selected to set the desired degree of overlap between the antenna beams associated with the selected sets of signals Bz. For example, if L is greater than one, the antenna beams associated with specific combinations of beam signals Bzshould spatial overlap.

Each of the digital beam signals Bz, z = 1, ... N is applied to the set of channel units, one of which is shown in Fig. 5A. Each channel unit performs other functions for the processing and detection of signals for a single communication line (e.g., telephone call) between the mobile subscriber terminal and the base station. In response to selection information of the beam provided by the controller 244, the switching matrix 228 in each channel unit selects a subset of the radiation signals Bzfor processing in the channel block. To identify the strongest signal received from the moving subscriber device associated with the channel block, use one or more search receivers 227. That is, the search receiver(s) 227 is normally provided to measure the levels of different multipath component arriving at the base station at different points in time, policealna embodiment, the switching matrix 228 selects the J sets of one or more radiation signals for processing by the set of J correlation receivers 230. This choice is based on the search results received at the controller 244 of the search receiver(s) 227. That is, the controller 244 determines which of radiation signals Bzmust be filed for each correlation receiver 230 and which of the multipath signal component from each of the rolling devices should be handled. The controller 244 may also be responsible for the adjustment of weights in diagrammatology scheme 224 to change the shape and/or direction of the beam generated beam signals Bz. The antenna pattern is usually formed so that the maximum amplification corresponded to those areas, which is the highest concentration of signals transmitted by mobile stations. Alternatively, in diagrammatology the circuit 224 may be formed from a sufficiently large number of rays, which gives the opportunity to get a custom pattern in accordance with the requirements of a particular system.

According Fig. 5A, the demodulated signals generated by each of the correlation receiver 230, served on summing module 235. In summing module 235 the demodulated sissiestiny signals after removal of the alternation are decoded according to a decoding algorithm Viterbi and then fed into the vocoder or other functional block.

In Fig. 5B shows a block diagram of the receiving system, the base station 210 to the concrete implementation of the channel block. Digital beam signals Bz, z = 1, ... N are formed diagrammable circuit 224 essentially the same manner as described above with reference to Fig. 5A.

Digital beam signals Bz, z = 1, ... N are served by switch matrix 228 selected channel unit, which is designed for the distribution of a set of beam signals Bzthe set of J receivers with diversity 232a-232j, respectively, is included in the correlation receiver 230. Each switching matrix 228 contains a diagram of the unidirectional action intended for connection N = (L)(M) beam signal inputs to a set of P = J*3K outputs. P outputs switch matrix 228 are separated by a set of J channels of traffic associated with receivers with diversity 232a-232j, where each of J users attached to one of the J channels of traffic, that is, to one of the J-channel blocks. In a possible embodiment, each of the receivers with diversity 232 is designed to process signals received from a group of K-1 distribution channels from a specific subscriber, where K denotes the number of the 232 and is usually meant to search for the strongest signal, taken from a specific subscriber unit.

Each receiving channel forms a complete demodulate receiver, which contains the schematic phase and time tracking for demodulating the selected temporal components spaced in time of the received signal multipath propagation. As described in U.S. Patent N 5109390 "Receiver with diversity in a cellular telephone system with MDR", assigned to the assignee of the present invention, a RAKE receiver with diversity can contain one or more of these receiving channels. In a possible embodiment of the present invention, each channel traffic is served by a three-channel RAKE receiver of the mobile station and channel RAKE receiver of the base station. It should be noted that for the identification and measurement of (but usually not for tracking time and/or phase) pilot signals and control signals circulating through active communication channels, typically used for more "search engine" correction circuits PN-signals.

The signals passing through the K-1 route distribution associated with each subscriber device, contain information that is sent over channel traffic allocated to each abonents each channel traffic. That is, for the reception of multipath signal, the processed data reception channel, uses a subset of three adjacent antenna beams. If two or more multipath signals allocated to different receiving channels which are spatially close, the same three-beam subset may be selected for receiving each of the two or more signals. In this case, the channel traffic may be allocated less than 3K radiation signals.

According Fig. 5B, the selection of three rays, used to receive each incoming signal, enables the schemes of the tracking beams 240a-240j track in the space of each received signal. Suppose, for example, that as the beam carrying the strongest signal of the three antenna beams associated with the receiving channel, was identified by the j-th beam formed by the antenna array of the base station. Can then be performed spatial tracking, as described in detail below, by calculating the spatial signal tracking based on the energy difference between "right" and "left" adjacent antenna beams (i.e. beams j 1). Each of the resulting K signals spatial tracking of each of the schemes tracking locomotoric set of K signal lines, corresponding to K blocks each receiver with diversity 232a-232j. If the tracking signals indicate that the signal received through the "right" beam j + 1, significantly stronger than the signal obtained with the "left" ray j - 1, then the controller 244 may improve signal reception, giving the command to switch matrix 228 change the set of rays allocated to this receiving channel with j, j 1 j, j + 1, j + 2.

In a preferred embodiment, the timing of demodulation of the signals received by the left and right rays of this receiving channel, shifted by a predefined interval. That is, the timing of demodulation signals for the left and right rays (i.e. rays j 1), is shifted so that one of the beams j 1 is considered "early" beam, while the other is considered "late" beam. Each of the circuits of the tracking beams 240a-240j generates a tracking signal based on the energy difference between the signals received at the left and right rays associated with each receiving channel. Suppose also that, for example, the rays j, j 1, generated by the antenna array of the base station, correspond to the three antenna beams associated with the data receiver channel. The signal is ti energies of demodulated signals, received from the left and right rays (i.e. rays j 1). Then in the corresponding receiver with diversity 232a-232j controller 244 corrects binding-time demodulation.

In Fig. 5C shows a block diagram of a reception system of a base station 219', containing the antenna grid placed at a remote position. In accordance with Fig. 5C, where the M-element antenna array (not shown) for receiving the set of signals received by the M signal lines 212'. In this example, the implementation of the antenna array includes a number (M) Omni-directional antenna elements, evenly spaced on a circular periphery, which allows the reception of signals coming from any direction.

In alternative embodiments of the M-element antenna array can be replaced by a rectangular grid of M omnidirectional antenna elements. You can then pick up the weights associated with each element in the lattice to give the opportunity to form beams in any direction. In the General case for the formation of beams in any direction you can use any configuration of antenna elements using appropriate diagrammen in Fig. 5C, the signal line 212' from the antenna array is connected to the inverter with decreasing frequency before the inverter 214', intended to reduce the frequency of the received signals and convert them into a set of signals of the inverter 218'. Then the signals of the inverter 218' is discretized in ADC 220' to obtain a set of M complex digital signals (I'i, Q'i), where i = 1,..., M. In the preferred embodiment, the sampling frequency of the ADC 220' is selected approximately four times greater than the frequency of the PN-expansion. Therefore, in the example implementation, the sampling frequency is equal to 41,228, or 4,912 MHz. The sampling frequency can be reduced to the Nyquist frequency, if together with ADC 220' is used interpolation filter.

Digital signals (I'i, Q'i), i = 1 to M, optionally, converted by the multiplexer 226' in the serial stream and fed to the modulator/encoder 228'. In the embodiment of Fig. 5C antenna array ADC 220', the multiplexer 226' and the modulator/encoder 228' are at the point remote from the elements, processing the signals of the receiving system 210'. Information from the remote position is supplied via the connection line 229' (for example, fiber optic cable) to the diagram of the demodulator/decoder 230', located at the Central processing point Il is t remote point, to ensure reliable transmission over a communications line 229'. It should be borne in mind that the specific format used modulation and coding will depend on the characteristics of the connection line 229'. In addition, it should be borne in mind that such a modulation and coding are performed solely to protect the integrity of data transmission from a remote location. Accordingly, the optional inclusion of schema elements 226'-231' shown by a dotted selection of these element in Fig. 5C.

Then demodulated and decoded signal generated by the demodulator/decoder 230', distributed by the demultiplexer 231' on the set of J diagrammatic circuits 224a'-224j'. As described above, each diagrammatica circuit 224a'-224j' generates a set of Q radiation signals to be processed by the corresponding receiver with diversity 232a'-232j'. The parameter Q is equal to the product of the number of receiving channels each receiver with diversity 232a'-232j' on the number of points allocated to each receiving channel.

In a preferred implementation for the reception of multipath signal, the processed data reception channel, uses a subset of three adjacent antenna beams. If two or more multipath signal allocated to different receiving is for receiving each of the two or more signals. In this case, the channel traffic will be allocated is less than Q/3 radiation signals. This distribution of rays enables schemes tracking beams 240a'-240j' to perform tracking both in time and in space for each received beam signal. This tracking is performed essentially as described above except that the controller 244' sends information about the choice of the beam separately for each diagrammatology circuit 224a'-224j".

Refer now to Fig. 5, which shows a block diagram of an adaptive radial RAKE receiver set for processing a set of M digitized antenna beam signals, converted to a lower frequency, such as signals, which are issued by the A/D Converter 220 (Fig. 5A). M antenna signals are distributed over the set of J-channel blocks, one of which is shown in Fig. 5D. Each channel unit performs other processing functions and detection signals for a single communication line (e.g., telephone call) between the mobile subscriber terminal and the base station. In response to selection information of the beam generated by the controller 244', switching matrix 233' in each channel unit selects a subset of the M receiving antenna signals to one signal, received from the mobile subscriber item associated with a channel block. That is, the search receiver(s) 227' is usually designed to measure the levels of different multipath component arriving at the base station at different points in time, after they have been respectively different distances following their transfer to the mobile subscriber. In a preferred implementation of the switching matrix 233' in each channel block J are selected sets of one or more signals of the antenna array for processing by the set of J correlation receivers 230' in channel block. This choice is based on the search results supplied to the controller 244' search receiver(mi) 227'. That is, the controller 244' determines which of the M signals generated by the antenna array must be sent for each correlation receiver 230', and which of the multipath signal component from each of the rolling devices should be handled.

The digitized signals from the antenna array, the selected switching matrix 233' of each channel unit, served on diagrammatology circuit 224' in channel block. Diagrammatica scheme is designed for the eat linear summation of the selected signals of the antenna array with a set of weighting coefficients, selected to maximize the signal-to - noise ratio of the strongest received multipath components processed by the receiver 230'. This usually leads to the choice of weights that maximizes the gain of the beam in the direction of the strongest received multipath signal components, defined by the search receiver(s) 227'. For each correlation receiver 230' may be filed more than one beam, because usually at the base station from different directions enters one or more multipath signal component processed each correlation receiver 230'. The shape and direction of the antenna beam associated with each radiation signal can be modified adaptive way controller 244' by dynamically changing the values of each weighting factor. The rays selected other channel blocks (Fig. 5D not shown), can also be directed to maximize the signal-to-noise ratio of the signals processed by these units.

According Fig. 5D, the correlation receiver 230' of each channel unit participates in the implementation of other functions of the signal processing performed for a single communication line between the mobile subscriber terminal and Batsi module 235'. In summing module 235' demodulated signals are summed and fed to the scheme exceptions interleave and decode (not shown). In a possible embodiment, the signals after exclusion of alternation are decoded according to a decoding algorithm Viterbi and consistently served on the vocoder or other functional block. The principal advantage in Fig. 5D is that the switching matrix handles a relatively small number of beam signals. Although you may need additional diagrammatized elements, however, this option provides the most cost-efficient circuit implementation.

In Fig. 5A-5D, the width of the antenna beams, the selected specific channel traffic will depend on the distance between the corresponding subscriber device and the base station. Wider beams can be allocated to the subscriber device located relatively close to the base station, while the more narrow beams are allocated more remote subscriber device.

C. Diagrammatica diagram of the formation of

In Fig. 6 shows an alternate implementation of an antenna array UB>)hand (Ii, Qi)v. In this implementation, a separate diagrammatized circuits 224a and 224b are used to generate separate sets lucabrasi signals Bz,hand Bz,vcorresponding to the diagrams of horizontally and vertically polarized beams. Signals Bz,hand Bz,vgenerated respectively schemes beam forming 224a and 224b according to expressions

< / BR>
where, as in the case of equation (1), z = 1 to z = (L)(M).

In the implementation of Fig. 6 both sets of beam signals Bz,hand Bz,vcan be treated the same switching matrix. Also, while i-I pair of beam signals B(z,h)iand B(z,h)vin the General case should not be allocated to one and the same receiving channel associated with a particular channel traffic, each signal can be used separately in different receiving channels of the receiver. Additional details regarding the implementation of the selective polarization for a variant of the antenna of Fig. 6, described, for example, in the aforementioned U.S. Patent N 4901307.

D. Switching matrix

In the following description switch matrix 228 (Fig. 5A), it is assumed that the antenna beams associated the e (L > 1) each pair of adjacent beams (i.e., Biand Bi+1will be in space to overlap. J traffic channels supported by P = J*3K outputs switch matrix 228 (Fig. 5A), can be denoted as Tj,k,mwhere the first index j takes on the values 0, 1, ..., J-1, and determines one of the J channel traffic; the second index k identifies a specific transmission path (receiving channel) channel traffic and takes on the values 0, 1, ..., K-1; the third index m, where m = 0, 1, or 2, specifies one of three adjacent antenna beams, the selected receiving channel concrete channel traffic.

In the example implementation of the input beam signals Bidistributed between the outputs of the Tj,k,mtrafc channel switching matrix as follows:

1) For each channel traffic Tjeach of 3K associated outputs connected to separate input beam Bi. The set of input radiation signals Biconnected to this channel traffic usually consists of K groups, and each group includes a set of three spatially adjacent rays. For example, if K=3 (i.e., three-channel reception channels), then the set of rays Bi-1BiBi+1Bj-1BjBj+1Bk-1Bkand Bk+1connected kN to one or more traffic channels. However, if radiation signal Biserved in this channel traffic, it is served by one and only one output switching matrix allocated for this channel.

3) the Connection between the input beam signals Biand outputs channel traffic Tj,k,mcan be described by a matrix with M rows corresponding beam signals Bi, i = 1, 2, ..., M, with P = J3K columns corresponding to the output channel of the traffic switching matrix. The element at the intersection of the m-th row and the p-th column of the matrix is assigned the value "1" if the input radiation signal Bmmust be connected to a specific output channel traffic Tj,k,m. The element is assigned the value "0" if such a connection does not exist. Example of matrix compounds for the case

nine of the input beam signals (M=9), four channels of traffic (J=4) and one receiving unit for one trafc channel (K=1) are presented in the table. Table determines that radiation signals B1B2B3must be connected to channel traffic "0" (i.e., B1to T0,0,1B2to T0,0,2and B3to T0,0,0), radiation signals B3B4and B5must be connected to channel traffic to "1" (i.e., B3for T7to T2,0,1B8to T2,0,2and B0to T2,0,0), and the radiation signals B5B6B7must be connected to channel traffic "3" (i.e., B5to T3,0,2B6to T3,0,0and B7to T3,0,1).

In a preferred embodiment, the implementation of the switch matrix 228 each beam signal can be connected to each output channel traffic Tj,k,m. In Fig. 7 shows a tree configuration switches 250, intended to produce a single signal path between the radiation signal Biand each channel traffic. Each switch 250 in the preferred embodiment, should consist of binary switch with one input and two outputs that can switch between the four conditions (for example, the States S0-S3). In state S0, the input switch is disconnected from both outputs, in state S1, the input is connected only to the first output state S2 input is connected only to the second output and S3, the input is connected to both outputs.

As noted above, each of the input radiation signal must be associated with up to one 3K lines associated with each channel traffic. Accordingly tree and from a set of eight traffic channels T1-T8. Using a set of N switching structures is implemented by a switching matrix that allows you to connect a set of N input beam signals to the set of T' channels of traffic, where T' denotes the number of outputs provided by each of the switching structure. In the General case, each of the switching structure includes (T'-1) binary switches.

E) Receiver with diversity

In Fig. 8 presents a block diagram of a receiver with diversity 232, and it should be understood that the receivers with diversity 232b-232j can be implemented in essentially the same way. In a preferred implementation of the switching matrix 228 serves to ensure that the receiver 232a set of 3K radiation signals associated with a particular channel traffic. Three beam signal associated with K transmission paths of the receiving channel of the traffic handled each one of the K receiving channels, and the first and K-th reception channels in the receiver 232a marked positions respectively 300 and 300'. Although in Fig. 8 shows more detail only the first receiving channel 300, it is assumed that each of the remaining K-1 receiving channels are essentially identical to the first.

As shown in Fig. 8, the switching matrix 228 takes the I and Q Ko's) rays on the first receiving channel 300. The switching matrix 228 also carries the I and Q components of the signals Right, Left, and Exact rays on the remaining K-1 receiving blocks, where Fig. 8 as an example of how the signals RKI, RKQ), Left (LIK, LKQ) and Central (CKICKQ) ray served on the K-th receiving unit 300'.

According Fig. 8, the signals of the Central (C1IC1Qthe beam is fed to the demodulator quadrature phase manipulation of the shift 304 together with the separately generated copies (PN'Iand PN'Q) sequence PNIand PNQ. The resulting dekorrelirovannyih output signals I and Q channels of the demodulator 304 is accumulated in the buffer accumulating the adders 306 and 308 I-channel and Q-channel, each of which accumulates the character data interval, equivalent in duration to the four elements of the PN signal. The output signals of the accumulative adders 306 and 308 are fixed by a processor, performs a fast Hadamard transform 310 at the end of each accumulation interval.

As noted above, when the transmission of 64 hexadecimal signals Walsh transmitted symbols encoded in one of 64 different binary sequences, known as Walsh functions. In agonally code of Walsh sequences of length 64. It is known that the operation of the fast Hadamard transform, implemented by the processor 310, provides a convenient way to determine the correlation of the received signal with each of the 64 Walsh sequences.

In particular, the processor 310 produces a set of 64 "hypotheses" I(W1), I(W2), . .. I(W64) I-channel and 64 "hypotheses" Q(W1), Q(W2), ... Q(W64) Q-channel on the basis of the results of each of the 64 correlations performed in the processor during each processing cycle. The adder 312 is provided for receiving 64 parallel output signals of the I-channel and 64 parallel output signals of the Q-channel, generated by the processor fast Hadamard transform each receiving channel during each processing cycle. In the example implementation, the outputs of the I and Q channels generated by the processor fast Hadamard transform in this receiving channel, weighed in the adder 312 proportional to the average energy of the signal received over the transmission path associated with the data receiver channel. In such an implementation, the signal generated by the processor fast Hadamard transform each receiving channel, usually continuously monitored at successive intervals, each of which covers several periods Perdomo receiving channel adder 312, can be adjusted at the end of each inspection interval.

Based on the weighted output signals I and Q channels formed by the processors for fast Hadamard transform of each of the receiving channel, the adder 312 delivers a parallel set of 64 signals Walsh on the detection unit maximum 316. The detection unit maximum 316 determines which of the 64 Walsh sequences generated by the adder 312, has the highest level of energy, i.e. the energy Emax. The amount of energy Emaxcan be served on the controller 244 in which it can be used during the next cycle of processing to perform the functions of power control and detection of capture. The detection unit maximum 312 generates an index of the Walsh Imaxwhere Imax{1, 2, ..., 64}, in accordance with the selected sequence of Walsh with energy Emax. As described below with reference to Fig. 9, the index of the Walsh Imaxdetermines which of the 64 Walsh sequences will be used in the processor 320 of the right/left beam for demodulation of the R1I, R1Q, L1Iand L1QThe right and Left beams.

In Fig. 9 provides a more detailed view of the processor 320 of the right/left of the rays. As shown is whether 342 and 344 I-channel through the delay elements 352 and 354 are counts of the I-channel, right (R1L) and left (L1L) signal beams. Similarly multipliers 344 and 346 Q-channel through the delay elements 356 and 358 are samples of the Q-channel, right (R1Q) and left (R1Q) signal beams. The delay elements 352, 354, 356 and 358 are designed to delay the I and Q component signals of the right and left beams, pending identification of the index of the Walsh Imax. In example implementations of the logical high and low levels of +1 and -1 are served with elements of the delay multipliers 340, 342, 344 and 346.

In Fig. 9 shows a character generator Walsh, which feeds on multipliers 340, 342, 344 and 346 Walsh sequence containing the character Walsh specified by the index Imax. The sequence defined by the index Imaxmultiplies the I-channel sampling signals R1Iand L1Ithe right and left beams, and the Q-channel sampling signals R1Qand L1Qthe right and left beams. Then the resulting demodulated output signals of the multipliers 340 and 342 are served respectively to the adders with saturation 370 and 372 I-channel, and demodulated output signals of the multipliers 344 and 346 are served respectively to the adders with saturation 374 and 376 of the Q-channel. Adders with saturation 370, 372, 374 and 376 nakae each accumulation is performed on the 64 elements Walsh (q=64), that is, the period symbol Walsh, q-bit output signals of the adders of the I-channel served on schema squaring 380 and 382 I-channel and q-bit output signals of the adders Q-channel served on schema squaring 384 and 386.

Estimate of the energy of the right beam is formed by summing the output signals of the circuits squaring 380 and 384 of the I and Q channels in the adder 392. Similarly energy "late" beam is estimated by summing the output signals of the circuits squaring 382 and 386 of the I and Q channels in the adder 394. Then an error signal beam using a digital differential circuit 396 based on the difference between the energies of the right and left beams formed respectively by the adders 394 and 392. The sign and magnitude of the error signal beam depends on the results of demodulation Walsh left and right rays performed the matching pairs of multipliers 342, 346 and 340, 344. For example, if the phase of the sampling ADC (Fig. 5A) is set so that the value of the demodulated signal Walsh "late" beam exceeds the value of the demodulated signal Walsh starboard beam, then the error signal beam will be positive. Similarly, if the magnitude of the demodulated signal Walsh PA will be negative.

A tracking signal generated by the data receiving unit, facilitates the adjustment of the set of rays allocated to this receiving unit. As noted previously, the switching matrix 228 is designed for the distribution of a set of three adjacent beams (for example, Bi-1Biand Bi+1) to each receiving unit. According to the invention, the tracking beam 240 (Fig. 5A) associated with the particular receiver with diversity 232, signals switching the beam on the controller 244 based on the tracking signals received from each of the receiving channel of the receiver 232. As a consequence, the controller 244 may issue periodic command on the switch matrix 228 to shift the direction of this beam receiving channel on one beam width. For example, if the receiving channel has previously been selected for beams Bi-1Biand Bi+1it can be switched to the rays of BiBi+1and Bi+2in response to the formation of a specific switching signal beam. Thus, each receiving channel provides spatial tracking of the received multipath signal, for which he was selected.

According Fig. 8, the tracking beam 240a includes a set of accumulative adders tracking C is that the adder tracking beam 240aiprocesses the error signal beam generated by the processor of the right/left beam in the associated receiving channel. As described below with reference to Fig. 11, in some circumstances the error signal beam generated in the receiving channel of the receiver 232a, is used to increase/decrease the content accumulating register in the appropriate nakaplivaya the adder tracking beam 240ai. If accumulating register overflows or there is a loss of significant digits, the signal switching beam is supplied to the controller 244, and a set of rays distributed to the receiving unit of the switching matrix is adjusted accordingly.

In Fig. 10 shows the block diagram of the accumulating adder tracking beam 240aiassociated with the first receiving channel 300 (Fig. 8) receiver with diversity 232a. Accumulating adder tracking beam 240aiincludes input register 402, which is an index Imaxcharacter hypotheses Walsh, generated by the detection unit maximum 316, and the error signal beam from the processor to the left/right beam 320. These values are stored in the register 402, while the adder with the division 312 will not take "hard decisions" on the basis of character hypotheses Walsh, formed each is and Imax'from adder with 312 passing existing index channel Iavgives the ability to supply the stored value of Imaxthe digital comparator 406 and receive buffer register 408 stored error signal beam.

If the comparator 406 determines that the Imaxand Imax'equal, the enable signal output appearing on line 407, leads to the fact that the error signal stored in the buffer register 408 is added to the contents of the accumulating register 410. When overflow occurs the content accumulating register 410 is above the upper threshold or there is a loss of significant digits (the content is below the lower threshold), the signal switching beam of appropriate polarity is applied to the controller 244. When the signal beam switching controller 244 issuing the RESET command, which causes the discharge accumulating adder 410. The RESET command is served when the receiver is out of state capture when receiving character data, that is, when the comparator 406 determines that the Imaxnot equal to Imax'.

F. a Circular antenna array

In Fig. 11 presents an example of a circular antenna array 500. Assuming a circular grating has a radius R and contains 2N evenly spaced antimage to be described by the diagram of the gain G(-i), which determines the direction of arrival of an electromagnetic signal S, andispecifies the position of the antenna element Ei. As can be seen from Fig. 11, the signal S is supplied to each of the antenna elements Eiat different points in time. The time delayibetween the arrival of the received signal S to the center C of the lattice 500 and ward over the element Eican be expressed as follows:

< / BR>
The energy of the received signal Xi(t) generated by the element Eiwhen receiving the signal S, is determined by the expression:

< / BR>
where fwiththe Central frequency of the received signal S, and direpresents the phase shift due to the spatial separation between antenna elements of Eiand Ei-1. If we assume that each delayimuch less than the period PSH-element, then the value of S(ti) remains relatively constant in the range 1i2N. In a preferred implementation, the radius of the antenna R is less than about 30 meters, and therefore, each delayiwill be of the order of fractions of nanoseconds. Thus

< / BR>
The resulting composite reception signal Y(t) generated by the grating can be expressed as

< / BR>
where Wimean weight, p is azan) signals Xi(t) are weighted to maximize the signal-to - noise energy that is perceived by a lattice. The signal-to - noise ratio proportional to Y(t)/IT(t), where the parameter IT(t) is the total interference power received by all elements of Eiin the lattice. The parameter IT(t) is defined as

< / BR>
where Ii(t) corresponds to the interference power received i-th antenna element of Ei. The weighing operation, designed to maximize the S/N of the energy of the reception signal can be performed according to the method of calculation of the lattice, such as, for example, described in Pillai, S. Unnikrishna, Array Signal Processing, p.p. 16-17; Springer Verlag, New York, N. Y. (1989).

Description of the preferred embodiments will provide professionals with the opportunity to make or use the present invention. Professionals should be obvious various possible modifications of these options, and are defined here source principles can be applied to other cases without additional inventive activity. Thus, the present invention is not limited to the presented here options of implementation, and has a wide scope, defined open here Panigale between multiple users, containing means for creating at least first and second electromagnetic beams for receiving the component information signals transmitted by the users, and a means for assigning a first electromagnetic beam for receiving the first component of the information signal transmitted through the first transmission path, for forming a first received signal, characterized in that the said first component of the information signal contains at least a portion of the first information signal transmitted from the first user, while the system further comprises means for processing the signals of the first beam of the above-mentioned first received signal, scheme tracking the first beam for signal tracking for the first beam through a demodulation signal of the first beam, and means for switching beams for spatial monitoring of the aforementioned first component signal by assigning the second electromagnetic beam for receiving the aforementioned first component signal based on the signal tracking for first light.

2. The system under item 1, characterized in that it further comprises a means for forming a signal of the second beam from the second the I formation of the above-mentioned signals of the first and second beams includes means for sampling the aforementioned first and second received signals for forming the first and second discretized received signals.

3. The system under item 2, characterized in that the means for demodulating comprises means for adjusting the time samples at least the first sample of the received signal in accordance with signal tracking for first light.

4. The system under item 1, characterized in that the circuit of the tracking beam includes a tool for spatial monitoring of the first component of the information signal, and means for spatial tracking includes accumulating adder for forming the accumulated error signal by accumulating the specified signal of the tracking beam.

5. The system under item 1, characterized in that the means for creating first and second electromagnetic beams housed in a base station of a digital communication system, and a means for creating first and second beams includes the antenna system.

6. The system under item 1, characterized in that it further comprises means for creating a third and fourth electromagnetic beams for receiving the second components of the information signal on the second transmission path for the formation of the third and fourth received signals, the second component of the information signal contains the means for generating signals of the third and fourth beams from the third and fourth received signals, means for demodulation of these signals of the third and fourth beams to obtain the third and fourth assessments of the information signal and the second tracking scheme for the formation of the second signal tracking on the basis of the third and fourth assessments of the same information signal.

8. The system under item 2, characterized in that it contains means for demodulation of the second beam, means for forming a set of signals symbol estimates by correlating the signal of the first beam with a corresponding set of information symbol sequences, a means for selecting one of the information symbol sequences by comparing the signals of symbol estimates.

9. The system under item 8, characterized in that the said means to demodulate the first and second beams includes means for correlating the selected one of the character information sequence signal of the second beam.

10. Digital communication system for exchanging information signals between multiple users, containing means for creating at least one set of electromagnetic beams for reception of multipath signal component mn is investing set of received signals, characterized in that it further comprises means for generating a set of signals rays based on a set of received signals, switching means for spatial monitoring mentioned multipath signal components by changing the distribution of subsets of signals rays among the many traffic channels, each of the traffic channels associated with said at least one user, and receiving means for restoring the first of the above-mentioned information signals from a first of the subsets of signals rays assigned to the first channel of the traffic associated with the first of the said at least one user.

11. The communication system according to p. 10, wherein the receiving means includes first and second reception channels for processing the first and second multipath signal component of the first information signal.

12. The communication system according to p. 11, characterized in that the means for switching includes means for assigning a first of the subsets of signals rays to the first receiving channel and the second of the subsets of signals rays second receiving channel.

13. The communication system according to p. 10, characterized in that the above-mentioned PR signals rays, to obtain the first set of estimates of the first information signal, and the first tracking scheme for the formation of the first signal tracking based on the first set of estimates of information signal.

14. The system under item 13, wherein the first demodulator comprises means for correlating signals rays contained in the first set of signal beams, using sequence spread spectrum.

15. The system under item 10, characterized in that the means for forming a set of signals of the beams includes means for sampling the set of received signals for the formation of quantized signals, means for weighting the received quantized signals and means for summing the signals from among these weighted quantized signals.

16. The system under item 10, characterized in that the receiving means contains a number of receivers connected to the switching means, and each of the receivers includes a receiving channel for processing one of these subsets of signals rays.

17. Digital communication system for exchanging information signals between multiple users at least one base station, contains the first set of electromagnetic beams for reception of information signals, transmitted by multiple users, for forming the first set of received signals, characterized in that it further comprises first diagrammatology matrix connected to the grid of antenna elements for forming a first set of signal beams on the basis of samples from a set of received signals, and diagrammatica the matrix contains a means for weighting and summing the samples of the set of received signals, switching means for spatial monitoring of the mentioned information signals adopted in the base station, by changing the distribution of subsets of signals rays among the many traffic channels, each of the traffic channels associated with one of multiple users, and a set of receivers, connected to the switching means, each of which contains a means for selecting the information signal from a subset of signal beams that are assigned to one of these channels traffic.

18. The system under item 17, characterized in that it contains a remote grid antenna elements located outside the base station and operatively associated with the specified diagrammable matrix to generate a second set of electromagnetic beams for men received signals, second diagrammatology matrix, connected to the specified remote grid antenna elements to form a second set of signal beams on the basis of samples from a set of received signals, while the second diagrammatica the matrix contains a means for weighting and summing the selected samples of the signals contained in the second set of received signals, and the specified diagrammatica matrix operatively connected to the switching matrix contained in the means of commutation.

19. The method of transferring information signals between multiple users in a digital communication system, wherein creating the first and second electromagnetic beams for receiving the first component of the information signal on the first beat of the transfer for the formation of the first and second received signals, and the first component of the information signal contains at least a portion of the first information signal transmitted from the first specified users, wherein forming the signals of the first and second beam from the first and second received signals, demodulated signals of the first and second beams for receiving the first and second estimates of the same information signal and the cash tracking is used for spatial monitoring the first transmission path.

20. The method according to p. 19, characterized in that when forming the signals of the first and second beams discretizing the first and second received signals to obtain first and second discretized received signals.

21. The method according to p. 20, characterized in that during demodulation regulate temporary timing of the first and second discretized received signals in accordance with the first signal tracking.

22. The method according to p. 19, characterized in that the implement spatial tracking of the first component of the information signal, and spatial tracking involves the formation of the accumulated error signal by accumulating the error signal.

23. The method according to p. 19, wherein creating the first and second electromagnetic beams is carried out in a base station of a digital communication system.

24. The method according to p. 19, wherein creating the third and fourth electromagnetic beams for receiving the second components of the information signal on the second path for the formation of the third and fourth received signals, and the specified second component of the information signal contains the second part of the above mentioned first information signal.

25. and fourth received signals, demodulated signals of the third and fourth beams to obtain the third and fourth assessments of the information signal and generate the second signal based tracking of the third and fourth assessments of the information signal.

26. The method according to p. 19, characterized in that during demodulation of the first and second beams form a set of signals of a character assessment by correlating the signals of the first beam with a corresponding set of information of the character sequences and buy one of these informational character sequences by comparing these signals to symbolic evaluation.

27. The method according to p. 26, characterized in that during demodulation of the first and second beams is performed by correlating the selected sequence specified information of the character sequences with the specified signal of the second beam.

28. The method of transferring information signals between multiple users in a digital communication system, wherein creating at least one set of electromagnetic beams for reception of multipath signal component of at least one information signal corresponding at least on the b rays based on a set of received signals, perform spatial tracking mentioned multipath component by changing the distribution of subsets of signal beams of a plurality of traffic channels, each channel traffic associated with one user, and restore the first information signals from a first of the subsets of signals rays assigned to the first channel of the traffic associated with the first user.

29. The method according to p. 28, characterized in that the restoration process of the first and second multipath signal component of the first information signal using respectively the first and second receiving channels of the first receiver.

30. The method according to p. 29, characterized in that in the distribution appoint the first of subsets of signal beams to the first receiving channel and the second of the subsets of signals rays to the second receiving channel.

31. The method according to p. 28, characterized in that it further demodulated signals rays contained in the first set of signal beams to obtain the corresponding first set of estimates of the first information signal, and generate the first signal tracking based on the first set of estimates of information signal.

33. The method according to p. 28, characterized in that when forming a set of signals rays carry out the discretization of a set of received signals to obtain a quantized signal, weigh the received quantized signals and sum signals from among these quantized signals.

 

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FIELD: radio communications.

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FIELD: radio communications.

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FIELD: radio communications.

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EFFECT: reduced mass and size of transceiver stations, enhanced noise immunity and electromagnetic safety of personnel.

2 cl, 6 dwg, 1 tbl

FIELD: radio communications.

SUBSTANCE: proposed method for single-ended radio communications between mobile objects whose routes have common initial center involves use of low-power intermediate transceiving stations equipped with non-directional antennas and dropped from mobile objects. Proposed radio communication system is characterized in reduced space requirement and, consequently, in enhanced effectiveness when operating simultaneously with several other radio communication systems.

EFFECT: reduced mass and size, enhanced noise immunity and electromagnetic safety for attending personnel.

2 cl, 7 dwg, 1 tbl

FIELD: radio communications.

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EFFECT: reduced mass and size of transceiver stations, enhanced noise immunity and electromagnetic safety of personnel.

2 cl, 7 dwg, 1 tbl

FIELD: radio communications.

SUBSTANCE: proposed method intended for data transfer to mobile objects from stationary one residing at initial center of common mobile-objects route using electronic means disposed on stationary and mobile objects involves radio communications with aid of low-power intermediate transceiving stations equipped with non-directional antennas and dropped from first mobile object, these intermediate transceiving drop stations being produced in advance on first mobile object. Proposed radio communication system is characterized in reduced space requirement which enhances its effectiveness in joint functioning with several other radio communication systems.

EFFECT: reduced mass and size of transceiver stations, enhanced noise immunity and electromagnetic safety of personnel.

2 cl, 7 dwg, 1 tbl

FIELD: radio communications.

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EFFECT: reduced mass and size, enhanced noise immunity and electromagnetic safety of personnel.

2 cl, 7 dwg, 1 tbl

FIELD: radio communications.

SUBSTANCE: proposed method intended for data transfer to mobile objects from stationary one residing at initial center of common mobile-objects route using electronic means disposed on stationary and mobile objects involves radio communications with aid of low-power intermediate transceiving stations equipped with non-directional antennas and dropped from first mobile object, these intermediate transceiving drop stations being produced in advance on first mobile object and destroyed upon completion of radio communications between mobile and stationary objects. Proposed radio communication system is characterized in reduced space requirement which enhances its effectiveness in joint functioning with several radio communication systems.

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12 cl, 11 dwg

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