The transmission of signals with variable speed in the system spread spectrum communications using group coding

 

(57) Abstract:

The proposed system and method of sharing information at variable speeds by in-phase (I) and quadrature (Q) channels in the communications system spread spectrum D . The input information signal is transmitted to either the I or Q channel. First information signal is divided into first and second subsignal served respectively to the first and second device group coding. In the first device combines the first subsignal with the first group ID, in the second device group encoding the second subsignal is combined with the second group code orthogonal to the first group code. Then the composite encoded group codes the signal is modulated orthogonal functional signal to provide the first modulated signal. Phase psevdochumoy ( PNI) and quadrature psevdochumoy (TLQsignals in the specified codes are used to extend the first modulated signal for transmission to the receiver either I or Q channel, respectively. The receiver provides reception assessment input information signal based on the modulated is.p. f-crystals, 14 Il., table 1.

The present invention relates to communication systems that use signals with spread spectrum, and in particular, to a new improved method and apparatus for exchange of information in the system of spread spectrum communications.

Prior art

Developed communication system, which can transmit information signals from a source in a geographically dispersed points of users. For the transfer of such information signals via the communication channels connecting the source of the message with the locations of the users, uses both analog and digital methods. Digital methods demonstrate a number of advantages over analog, including, for example, increased protection from noise in the channel and interference, increased throughput and improved secure communication using encryption.

When transmitting the information signal from the source location over the communication channel information signal is first converted into a form suitable for efficient transmission over the channel. Conversion or modulation, the information signal includes changing settings of the carrier depending on informationapple channel. At the location of the user signal of the original message is reproduced from a version of the modulated carrier, adopted after the passage of the signal through the channel. Such reproduction is usually achieved by inverting the modulation process performed by the transmitter source.

Modulation also facilitates multiplexing, i.e., simultaneous transmission of multiple signals over a common channel. Multiplex communication systems typically include a variety of remote subscriber items requiring rather intermittent service with a relatively small duration than continuous access to the communication channel. Systems designed for communication with subscriber set points for short periods of time, called communication systems with multiple access.

A known type systems in connection with collective access, entitled "system spread spectrum". In systems with spread spectrum used modulation method leads to the broadening of the transmitted signal in a wide band of frequencies within the channel of communication. One type of system of collective access spread spectrum is a modulation system with the advanced spectrum connection with collective access for example, with multiple access and time division multiplexing (TDMA), multiple access and frequency division multiple access (FDMA), as well as amplitude modulation (AM), for example, by compounding amplitude on one side of the strip. However, the modulation method of the extended spectrum (CDMA) has significant advantages over these methods of modulation when used in communication systems with multiple access. The method D in the communication system with public access are disclosed in U.S. patent N 4901307, issued February 13, 1990, entitled "SPREAD SPECTRUM MULTIPLE ECCESS COMMUNICATION SYSTEM USING SATELLITE OR TERRESTRIAL REPEATERS", the rights to which are owned by the assignee of the present invention.

In the above-mentioned U.S. patent N 4901307 disclosed a method of collective access, in which a large number of users of mobile telephone systems, each having a transceiver shall exchange information through satellite repeaters or terrestrial base station using the communication signals with spread spectrum CDMA. When using connection with CDMA frequency spectrum can repeatedly re-used, which allows to increase the capacity of the system to users. The use of CDMA Prive other ways of collective access.

In particular, the link in the CDMA system between two points is achieved by extending each of the signal being transmitted in the channel bandwidth through the use of code extension, unique to each user. Specific transmitted signals are allocated from the communication channel by narrowing the spectrum of the composite signal in the communication channel using custom code extensions corresponding to the transmitted signal subject to selection.

In certain communication systems, spread spectrum, it is necessary to have different types of channels the user (e.g., voice, Fax and high speed data) operating with different data rate. These systems are usually designed so that there are channels that operate with a nominal data rate, and channels, working with a reduced speed graphics to provide higher throughput. However, increasing the bandwidth by using channels with low data rate, and increases the time required for data transfer. In addition, in some systems, spread spectrum communications there is a need in Cana CLASS="ptx2">

In order to provide data transfer at different speeds, in General you will need to change the speed of encode, interleave, and modulate in accordance with the speed of the input data. This speed change usually requires complicated control processes of channel coding and decoding, which increases the cost and complexity of the system.

Thus, the present invention is the task of creating a system of spread spectrum communications, in which the communication channels would be available for data transmission at speeds both above and below the nominal system speed, you would use a common format to encode, interleave, and modulate data to be transmitted at different speeds, and which would allow to increase channel capacity without a corresponding reduction in the speed data.

Disclosure of the invention

The implementation of the method in CDMA communication systems with spread spectrum using orthogonal code sequence with pseudotumor (PN), reduces mutual interference between users, thus enabling to increase the bandwidth and improve performance. Currently sabram communication in the communication system spread spectrum CDMA.

In the example of the input information signal is betrayed as I and Q channel using a directional serial signal to spread spectrum communications. Information original signal is divided into first and second subsignal served respectively by the first and the second circuit group coding. When the first group encoding the first subsignal is combined with the first group ID and the second group encoding the second subsignal is combined with the second group code orthogonal to the first group code. Thus the first and the second circuit group coding provide the first and second coded group of code signals, respectively. Composite coded group code signal formed from the first and second coded group code signals are then modulated orthogonal functional signal for receiving the first modulated signal.

The signals in-phase pseudoloma (PNI) and quadrature pseudoloma (PNQ) in predetermined PN codes are used to extend the first modulated signal in either the I or Q channels, respectively. For example, PNIpower for transmission to the receiver via the first communication channel.

In the example implementation, the receiver generates the evaluation of the input information signal based on the modulated carrier signal received or I or Q channel. The received signal is first demodulated by using the orthogonal function signal. Then demodulated signal decorrelated by using a narrowing of the spectrum of the PN signal, and the resulting signals projections are fed to the phase shifter. The phase shifter provides an estimate of the composite encoded group code signal on the basis of the signals of the projections and the received pilot signal. Evaluation of the first and second subsignals produced by performing one of decorrelation based on the orthogonality of the first and second group of codes.

Brief description of drawings

The invention is further illustrated by a description of its variants, with reference to the accompanying drawings, in which:

Fig. 1 depicts a block diagram of a known transmitter spread spectrum.

Fig. 2 is a block diagram of the preferred options for performing transmitter spread spectrum intended for transfer to the I-channel and Q-channel information signals.

Fig. 3 - BL is s according to the present invention.

Fig. 4 is a block diagram of a group of encoder speed 1/p, adapted to be included in the device group coding in Fig. 3.

Fig. 5 is a block diagram of a pair of devices of the group encoding the I-channel and Q-channel is used in the preferred embodiment of the invention for data transmission with a speed four times higher than the nominal.

Fig. 6 is a block diagram of a pair of devices group coding with rate 1/4 I-channel and Q-channel is used in the preferred embodiment of the invention for transmitting data at a rate eight times higher than the nominal.

Fig. 7 is a block diagram of the device group of the encoding used in the preferred embodiment, for data transmission with a speed equal to half the nominal one.

Fig. 8 is a block diagram of the device group of the encoding used in the preferred embodiment, for data transmission with a speed equal to one-fourth of the nominal.

Fig. 9 is a scheme of generating the pilot signal to generate a sequence of pilot signals of the I-channel and Q-channel.

Fig. 10 is an example implementation of a RF (radio frequency) transmitter included in a preferred variant of the invention.

Phi is transmitted on the I and Q communication channels.

Fig. 13 is a block diagram of the receiving and the finger that is part of the receiver with the division according to Fig. 12 and intended for processing the signal received by the selected transmission path.

Fig. 14 provides a more detailed view of the selected finger of the receiver shown in Fig. 13.

The best option of carrying out the invention

In Fig. 1 shows the transmitter spread spectrum, such opened in U.S. patent N 5103459, issued in 1992, entitled "SYSTEM AND METHOD FOR GENERATING SIGNAL WAVEFORMS IN a CDMA CELLULAR TELEPHONE SYSTEM"; the rights in which are owned by the assignee of the present invention.

In the transmitter of Fig. 1 data bits 100, containing, for example, the elements of speech, converted into data using a vocoder, served on the encoder 102, where these bits are subjected to convolutional coding with a repetition code symbol in accordance with the rate of the input data. If the baud rate is less than the processing speed of the encoder 102, the repetition code prescribes that the encoder 102 repeated bits of the input data 100, in order to create a flow of repetitive data with a bit rate that matches the processing speed of the encoder 102. The ZAT is e character data are derived from permiates 104 at a speed for example, 19,2 KS/s (kilosymbols per second) to the input of logic gate exclusive-OR 106.

In the system of Fig. 1 peremerzanie data characters scribblenauts (encrypted) to provide a higher degree of protection when they are transmitted over the channel. Scrambled speech channel signals can be performed by pseudotumour (PN) coding perenesennyj data using a PN code for each individual receiving subscriber item. Is the PN scrambling can be provided P by the generator 108 using an appropriate PN sequence or encryption schemes. PN generator 108 typically includes a generator of a long PN sequence to obtain a unique PN code at a fixed repetition rate elements PN 1.2288 MHz. Then this PN code passes through the thinning, and the resulting scramblers sequence at the speed of 19.2 KS/s is fed to another input of the logical element "exclusive OR" 106 in accordance with the identifying information of the subscriber's point, which he provided. The output of the logic gate exclusive-OR 106 then served on one of the inputs of a logic gate exclusive OR 110.

Again, please see enerator Walsh 112 generates a signal Walsh, designed for the data channel on which to send information. The signal Walsh provided by the generator Walsh 112, is selected from a set of 64 signals Walsh, each of which has a length of 64 elements Walsh. 64 orthogonal signal correspond to the elements of the matrix 64x64 Hadamard where the particular signal Walsh is determined by the row and column of the matrix. Scrambled character data and signal Walsh are the logical exclusive OR operation using the logical element exclusive OR 110, and the result is fed to the inputs of two logic elements "exclusive OR" 114 and 116.

The logical element "exclusive OR" 114 receives PNIsignal, while to the other input of the logical element "exclusive OR" 116 receives PNQsignal. PNIand PNQthe signals are pseudosolenia sequence typically associated with a particular zone, that is, the cell is covered with a CDMA system, and refer respectively to the in-phase (I) and quadrature (Q) channels. PNIand PNQthe signals are subjected to the logical exclusive OR operation with the output of a logic gate exclusive OR 110, so as to further enhance data is spider veins encoded sequence 126 Q-channel are used to bi-phase modulate a quadrature pair of sinusoids. Modulated sine waves added together, are subjected to bandpass filtering, shifts into radio frequencies, again filtered and, prior to transmission via the antenna, amplified to the final transmission over the communication channel.

Known methods of distribution of the variables of speed in the transmission system according to Fig. 1 generally require the use of the controller to change the operating speed of the encoder 102, the interleaver 104 and generator Walsh 112 in accordance with the speed of the input data. As will be shown, the present invention makes it possible to transmit one information signal spread spectrum with a speed higher than the nominal or transfer a lot of information signals at speeds below rated using the overall speed of the encode, interleave, and modulate.

In Fig. 2 shows a block diagram of the preferred option the transmitter spread spectrum 150 according to the invention, which serves for transmission of the input information signal SINon the data transfer rate kRbwhere is a constant, and Rbdenotes the nominal transmission rate (binary) data. Used here, the nominal data rate R is determined equal to the product with the ox signal Walsh. In the example of realization of the nominal data rate set at the level of 9.6 KS/s by using a set of modulation parameters, in which the transmission frequency of PN elements is selected to be 1.2288 MHz, rate convolutional coding 1/2, and the length of the signal Walsh is set to 64 characters. A distinctive feature of the invention is that the transmitter 150 can be used for transmission of information signals with data rates that equal or larger nominal, without having to reconfigure the values of the above parameters modulation. As will be shown, the present invention also provides a method for transferring multiple data signals at speeds below rated without having the appropriate reconfiguration of the modulation parameters.

In particular systems, the input information bit sequence SINmay consist of, for example, from the speech data converted by the vocoder in the binary data stream. As shown in Fig. 2, the input data stream is supplied to the encoding scheme and interleave 160. The circuit 160 performs convolutional encoding an information bit sequence, then the encoded data evaluation of the SSI to believe, what convolutional coding occurs at a rate of 1/2, the stream of symbols will be transmitted to the demultiplexer 170 with a symbol rate of 2kRb. The demultiplexer 170 converts the character stream SINTin the set of k-character sub-workflow { A(1), A(2), ... A(k)}, each of which has a speed 2Rbby sending the following character sequence SINTin the following sequence, the symbols of the sub-workflow {A(1), A(2), ... A(k)} the First k/2 character sub flows are served in the scheme of group coding of the first channel 190. As described here, in an exemplary implementation of the schemes group coding 180 and 190 character encoding sub flows using orthogonal sets of group codes of length p, where p=k/2. Then the encoded group codes in circuits 180 and 190 character sub-summed to form a composite I-channel and Q-channel symbol streams Icand Qcaccordingly, although in Fig. 2 for the community is depicted as the I-channel and Q-channel circuit group coding in a specific implementation, you can optionally split the character stream SINTonly k/2 character sub-workflows to transfer or I-channel or Q-channel.

Refer again to Fig. 2, hanala 200 and 205. The signal Walsh used in circuits 200 and 205 to modulate the composite character streams I-channel and Q-channel Icand Qc. In addition, PN extends the signals are modulation schemes and extensions 200 and 205, respectively, of the generators PNIand PNQsequences 215 and 220. PNIthe sequence is used to extend the composite symbol stream Icin the extended code sequence I-channel SI. Similarly PNQthe sequence is used by circuit 205 to extend the composite symbol stream Qcin the extended coded sequence Q-channel SQ. Received advanced coded sequence I-channel and Q-channel SIand SQused to bi-phase modulate a quadrature pair of sinusoids generated by the RF transmitter 225. The modulated sine wave is usually summed up, are filtered, shifted into the region of the RF frequency and amplified prior to distribution through the antenna I and Q channels of communication.

In Fig. 3 shows the block diagram of the device group encoding the I-channel, and it should be borne in mind that the group scheme of encoding the Q-channel can be implemented in essentially the potokov from the demultiplexer 170. Coders 250 are used to generate k/2 sequences {a(1) and(2),...a(k/2)} where

where S1, S2,...,Sk/2form a set of k/2 orthogonal group codes of length p, and where the operation [] is defined as follows. Let A = (a1... ar) is a sequence of length r, and let B = (b1b2, . . . bk) is a sequence of length k, then A [] denotes the sequence (a1b1,...a1bk, a2b1,...a2bk,...arbk), where denotes the exclusive OR operation. When generating sequences { a(1) and(2),...a(k/2)} each character in the character sub {A(1), A(2), ...A(k/2)} is repeated p times, and the p-th repeated symbol is subjected to exclusive OR operation with the p-th coefficient of the corresponding group code. This operation is known to experts as the encoding using the group code of repetition with a speed of 1/p.

In Fig. 4 presents a block diagram of a group of encoder speed 1/p 300, use group code C to encode the input symbol stream R in the output coded symbol stream RS.encwhere C {c1c2,..., cp}. Group encoder includes demultiplication OR 310. Each of the symbols ri subjected to exclusive OR operation with one of the factors group codepand the result is fed into a p:1 multiplexer 315. Then the multiplexer 315 generates the encoded character stream RS. encwhere in the General case, for each symbol rigroup encoder speed 1/p generates a sequence of

{ric1, ric2,..., ricp) = ric.

Refer again to Fig. 3, where in the preferred embodiment, sub { A(1), A(2), . ..A(k/2)} and group codes S1, S2, ..., Sk/2consist of logical 0 and 1, in the form of sequences {a(1), a(2),...a(k/2)}, the group generated by the encoder 250. The sequence {a(1), a(2),...a(k/2)} is converted to an integer (i.e. 1) performance using a set of converters "binary-integer" 260 as follows:

0 ---> + 1

1 ---> -1

As shown in Fig. 3, then the digital adder 270 is formed by a sequence of Icby combining the output signals of the circuits convert 260.

Implementation support high data transmission speeds 1.4 x nominal speed

In Fig. 5 presents a block diagram of a pair of devices of the group encoding the I-channel and Q-channel OTU, four times higher than the nominal. In particular, the encoded group code with rate 1/2 and perenesennyj character stream, running at a speed eight times (for example, 76,8 KS/s) nominal (e.g., 9.6 KS/s), demultiplexed by successive selection of characters in one of the four sub-workflow {A(1), A(2), A(3), A(4)}, where A(1) = {A11,A12,...} A(2) = { A21, A22, ...}, A(3) = {A31,A32,...}, and A(4) = {A41,A42,...} In the implementation of Fig. 5 is encoded with a rate 1/2 and perenesennyj stream of symbols is formed from the input bit sequence (data not shown) supplied with a speed four times greater than nominal. As shown in Fig. 5 sub A(1) and A(2) are respectively in the group encoders with rate 1/2 code 370 and 372 in the device group encoding the I-channel 350, while the sub-A(3) and A(4) are directed respectively in group encoders with rate 1/2 code 375 and 377 in the device group coding Q-channel 360. Repeat with rate 1/2 encoding character sub-workflow A(1) and A(3) encoders 370 and 375 using the group code (0,0) with a repetition rate of 1/2, while for encoding character sub-workflow A(2) and A(4) group coders roll forming devices "binary-integer 380 in integer format () and combined in a digital adder 385 in a valid sequence of Ic.4. In the same way sub-group of coders 375 and 377 of the Q-channel is converted by the conversion of binary to integer 390 in integer format, and then are summed in a digital adder 395, forming a valid sequence of Qc.4.

In Fig. 5 also shows the implementation of the modulation devices and expansion I was kakala and Q-channel 200 and 205. The device I-channel 200 includes a multiplier 400 for multiplying the sequence of Ic.4and Qc.4the Walsh function W, provided by generator 210 Walsh in an integer (i.e., + / - 1) format, where in this example, the implementation of W = (W1, W2,...,W32, W33,..., W64). Thus the device group encoding 350 and 360 operate together with expansion devices 200 and 205, providing the values of the Walsh function W to the sub-A(1) and A(3) and providing the values of the Walsh functions W*the sub-A(2) and A(4), where W*= (W1, W2,...,W32,-W33,...,-W64).

PNIthe sequence is fed to the multiplier 402 that is used to extend the sequence of Ic.4in the extended code sequence I-channel SI. 4created by the device I-channel 200. Similarly PNQused is the anal SQ. 4created by the device 205. The resulting advanced code sequence of the I-channel and Q-channel SI. 4and SQ. 4used to bi-phase modulate a quadrature pair of sinusoids generated in an RF transmitter (not shown).

II. 8x rated speed

In Fig. 6 presents a block diagram of a device group coding with rate 1/4 I-channel and Q-channel 450 to 460, used in the preferred embodiment of the invention for data transmission rates up to eight times the nominal. The input bit sequence at a speed eight times the nominal subjected to coding with rate 1/2 and permitiu, forming a stream of characters with speed, sixteen times (for example, 153,6 KS/s) is greater than the nominal (for example, a 9.6 KS/s), and demultiplexed by successive selection of characters in one of the eight sub-workflow A(i), i=1,...,8, where A(i) = {Ai1Ai2,...}, i=1,...8.

As shown in Fig. 5 sub A(1) - A(4) are respectively in the group encoders with rate 1/4 I-channel 470, 472, 474, and 478 in the device group encoding the I-channel 450, while the sub-A(5) - A(8) are directed respectively in group encoders with rate 1/4 Q-Kahn, the coders 470 and 480 use group code S1with the speed of 1/4, to encode a character sub-workflow A(2) and A(6) encoders 472 and 482 using the group code S2to encode a character sub-workflow A(3) and A(6) encoders 474 and 484 using the group code S3, while to encode a character sub-workflow A(4) and A(8) encoders 478 and 488 using the group code S4Group codes with S1S4defined by the following expressions;

S1= (s11, s12, s13, s14) = (0,0,0,0);

S2= (s21, s22, s23, s24) = (0,1,0,1);

S3= (s31, s32, s33, s34) = (0,0,1,1);

C4= (c41c42c43c44) = (0,1,1,0);

In the same way eight group of coders generate set of eight coded character streams a(i), where i=1,..., 8, reaching speeds (for example, 76,8 KS/s), at eight times the nominal. Coded character streams a(i) are formed according to the following expression

< / BR>
In order to simplify the recording without loss of generality, here for further suppose that each substream A(i) consists of single characters Aiand not sequences Aijwhere the index "j" represents the time. For example, using this to record the sequence a(i), i=1,...,8 is converted by the converters binary integer 490 in the set of valid sequences r(i), i=1,.. .,8 according to the expression

r(i) = (-1)a(i)= ((-1)ai1,...,(-1)air)= (ri1,...,rip)

where aij= AiSjand where Sijdenotes the j-th symbol included in the i-th group code Si. The sequence r(i), i=1,..., 4 are combined in a digital adder 494 in a valid sequence of Ic.8. In the same way the actual sequence r(i), i= 5,...,8 are summed in a digital adder 498, forming a valid sequence of Qc.8.

Please refer to Fig. 6, where the multipliers 502 and 504 are used for multiplication of sequences 1c.8and Qc.8the Walsh function W, provided by the generator Walsh 506, in this example, the implementation of W = (W1, W2,...,W32,W33. . . ,W64. Thus, functions, Walsh W0, W1, W2, W3effectively distributed symbolic sub A(i), i=1,...,4 A(1), i=5,...,8, respectively, where W0, W1, W2, W3defined as:

W0=(Wa, Wb, Wc, Wd;

W1= (Wa, -Wb, Wc, -Wd);

W2= (WaWa, Wb, Wc, Wdcan be defined in the signal components Walsh W as

Wa(W1,...,W16);

Wb(W17,...,W32);

Wc(W33,...,W48);

Wd(W49,...,W64);

PNIM is supplied to the multiplier 510, designed to extend the sequence of Ic.8in the extended code sequence I-channel SI. 8. Similarly, the multipliers 514 when the extension is valid sequence Qc.8in the extended code sequence Q-channel SQ. 8use the sequence PNQ. Advanced code sequence of the I-channel and Q-channel SI. 8and SQ. 8used to bi-phase modulate a quadrature pair of sinusoids generated in an RF receiver (not shown).

Implementation support low data rates

1.1/2-speed data transfer

Please refer to Fig. 7, where the pair of input data streams Asweat/2and Bsweat/2with a data rate equal to half of the rated speed, is fed to the encoder and interleave 550 and 554. Device 550 and 554 performs convolutional coding of the signals Asweat/2and Bsweat/2in Kodirov is 2(2) = {A21, A22,...}. If we assume that the rate of the convolutional coding 1/2, the resulting character peremerzanie flows A1/2(1) and A1/2(2) will be submitted to the group coders 558 and 560 with a nominal speed. Group code S1where S1= (0,0), is used by the encoder 558 to encode with repetition speeds of 1/2 symbol substream A1/2(1) in the encoded substream and1/2(1). Similarly group code S2where S2= (0,1), served in group encoder 560 to encode with repetition speeds of 1/2 character substream A1/2(2) in the encoded substream and1/2(2). The coded sub1/2(1) and a1/2(2) defined as

< / BR>
The coded sub-group derived from encoders 558 and 560 at a speed two times higher than nominal, and is converted into integer format (1) pair of transducers binary integer 570. The resulting valid sequence rj(1) and rj(2) are combined in a digital adder 575 in the actual sequence R1/2for subsequent transfer to the j-th reception area. The actual sequence R1/2served in the multiplier 580 for multiplication by the function Uo is.,W64).

In the function values Walsh (W1W) feature character stream A1/2(1), and the values of the Walsh function W*feature character stream A1/2(2) where W*= (W1- W). After multiplying the Walsh code W sequence R1/2usually expands the sequence PNIor PNQfor RF transmission or in-phase (I) or quadrature (Q) channel.

II. 1/4 data rate

Please refer to Fig. 8, where a set of four input data streams Asweat/4Bsweat/4Csweat/4and Dsweat/4served with a data rate equal to one-fourth of the nominal, the encoder and interleave 601, 602, 603 and 604.

Devices 601-604 perform convolutional encoding of data streams Asweat/4Bsweat/4Csweat/4and Dsweat/4in coded peremerzanie character streams A1/4(1), A1/4(2), A1/4(3) and A1/4(4) where

A1/4(1) = {A11, A12,...},

A1/4(2) = {A21, A22,...},

A1/4(3) = {A31, A32,...} and

A1/4= {A41, A42,...},

If you put the speed convolutional coding 1/2, the resulting primry 611, 612, 613 and 614 with a speed equal to half of the nominal. To encode A character streams1/4(2), A1/4(3) and A1/4(4) in the coded sub-a1/4(2), a1/4(3) and a1/4(4) group coders 611-614 group codes are used{(0000), (0101), (0011), (0110)}. Sub1/4(1), and1/4(2) and1/4(3) and a1/4(4) can be represented as follows:

< / BR>
The coded sub-group derived from encoders 611-614 speed, two times higher than nominal, and is converted by the converters binary integer 620 in integer format (). The result set of valid sequences of rj(i), i = 1,...4 for transmission to the j-th receiver combined in a digital adder 575 in the actual sequence R1/4. The actual sequence R1/4served in the multiplier 624 for multiplying the Walsh code Wjassociated with the j-th receiver. The sequence Wjis provided by generator Walsh 630 and is defined as Wj= (Wj1,Wj2,...,Wj32,Wj33,...,Wj64.

In the result, the values of the Walsh function W0, W1, W2, W3feature character threads A1/4(1), A1/4(2), A1/4(3) and A>, Wj);

W1= (Wj, -Wj, Wj, -Wj);

W2= (Wj, Wj, -Wj, -Wj);

W3= (Wj, -Wj, -Wj, Wj);

Thus it is obvious that four separate information signal, respectively identified by the Walsh functions W0, W1, W2W3you can pass on the j-th receiver by using one signal Walsh Wjusing the method of group coding considered in the invention. After multiplying the Walsh code Wjthe sequence R1/4usually expands psevdochumoy sequence P or PNQfor RF transmission, respectively, or in-phase (I) or quadrature (Q) channel.

If we assume that the transfer goes by I-channel to the j-th user, then the transmitted sequence, synthesized from sequences (rj(i) can be represented as

< / BR>
where p = 4 in the example of Fig. 8. If, in contrast to the previous case, the transmission is on the Q channel, the transmitted sequence can be represented as

< / BR>
Examples of the sets of parameters used to support the transfer of the input character streams on restabilize offers a corresponding repetition rate of the input symbols, rate group code of repetition, as well as the signal length Walsh and the rate of repetition of elements Walsh. Each element (X-Y) in the column "DEMUX" (Demultiplexing) determines the number of input character streams (X) with the corresponding data rate Rband the number of character sub-workflows (Y), in which the input character stream (s) demultiplexers for group coding

The transmission of encoded data group code on the I and Q channels

In a preferred embodiment, the pilot channel signal containing the modulated data is transmitted "N" receiver in a given cell or sector, together with extended sequences of the I channel and Q channel SIjand SQj, j= 1, ...N. the Channel, the pilot signal can be characterized as a non-modulated signal is spread spectrum, which is used for synchronization and tracking. In systems containing multiple transmitters, according to this invention a set of communication channels is identified by a unique for each channel pilot signal. However, it is clear that more effectively use the generating set of pilot signals using shifts of the same base sequence, than to use a dedicated examines the entire sequence of pilot signals and is configured to bias or shift, with whom he had the strongest correlation.

Accordingly, it is desirable that the sequence of pilot signals had a length sufficient so that you can generate, through shifts of the base sequence, many different sequences, to support a large number of pilot signals in the system. In addition, diversity or changes must be large enough to ensure the absence of interference in the pilot signals. Therefore, in the example implementation, the length of the sequence of pilot signals is chosen equal to 2, which allows to obtain 512 different pilot signals through shifts of the base sequence of 64 elements.

Please refer to Fig. 9, where the scheme of generating the pilot signal 630 includes a generator 640 Walsh for filing a "zero" Walsh W0consisting of all zeros into the digital multipliers 644 and 646. The signal Walsh W0is multiplied by PNIand PNQsequence supplied by generators PNIand PNQ647 and 648 multipliers 644 and 646, respectively. Because the signal W0includes only units, the information content of the resulting sequences depends only on PNIand PNQsequences. The placenta is Oh (FIR 650 and 652. The filtered sequence, the output of the FIR filters 650 and 652, respectively, in the form of sequences of pilot signals of the I-channel and Q-channel PI0and PQ0served in RF transmitter 660 (Fig. 10).

Please refer to Fig. 10, which shows an example implementation of a RF transmitter 660. The transmitter 660 includes an adder I-channel 670 for summing the set of extended PNIinformation signals SIj, j = 1,... N with the pilot signal PI0I-channel for transmission to N receivers within a particular cell or sector. Similarly, adder Q-channel 672 is used to combine the set of extended PNQinformation signals SQj, j = 1,...,N with the pilot signal PQ0Q-channel. Digital-to-analog (D/A) converters 674 and 676 provides conversion of digital information received from the adder I-channel and Q-channel 670 and 672, in analog form. Analog signals generated by the D/a converters 674 and 676 together with the signals of the carrier frequency of the local oscillator Cos (2ft) and Sin (2ft), respectively, are fed into the mixers 688 and 690, where they are mixed and fed to the adder 692. Quadrature carrier signals Sin (2ft) and Cos (2ft) received from the respective carrier generators (not shown). These with mesial 694 mixes the total signal from the RF frequency signal, coming from a frequency synthesizer 696, to provide conversion with increasing frequency in the band of RF frequencies, the RF signal includes in-phase (I) and quadrature (Q) components, it is filtered by bandpass filter 698 and fed to the RF amplifier 699. The amplifier 699 amplifies the signal with a limited bandwidth in accordance with an input control signal received from the control circuit power transmission (not shown). Obviously, in various embodiments of RF transmitter 630 you can use various ways of summing, mixing, filtering and signal amplification, which are not described here but is well known to specialists.

In Fig. 11 for example, presents the block diagram of the receiver with diversity, which serves for receiving RF signals transmitted RF transmitter 630. In Fig. 11 the transmitted RF signal from an antenna 710 and served on a RAKE receiver with diversity, which includes an analog receiver 712 and digital receiver 714. The signal passed by the antenna 710 and the received analog receiver 712 may include radiated in all directions of transmission of the same pilot signal and the information signals intended for a single or for multiple subscriber the Quaternary signals) modem, performs frequency decrease and discretetime received signal on the composite I and Q components. The composite I and Q components are fed into a digital receiver 714 for demodulation. Then demodulated data is provided in the digital circuit 716 for combining the inverse interleave and decode.

Each I and Q component output from analog receiver 715 may include radiated in all directions broadcast an identifying pilot signal and the information signals. In a digital receiver 714 specific multipath transmission of broadcast signal selected by the search receiver 715 together with the controller 718, processed, each one of the multiple data receivers or demodulators a-720p, which are referred to here as the "fingers". Although in Fig. 11 shows only three fingers for demodulating data demodulators a-720p), it should be clear that you can use more or fewer fingers. Each finger of the components I and Q component by compression (range) selects the I and Q components RI and RQ pilot signals and information signals corresponding to a particular path.

We can say that the I and Q components of the pilot signal for each finger to obrazuyetsya these I and Q components of the vector of the pilot signal and data are allocated from a received signal to obtain an estimated data of I-channel and Q-channel. Typically, the pilot signal is transmitted with a higher level than the data signals, and therefore the module of the vector of the pilot signal is greater than the received data vectors. Accordingly, the vector of the pilot signal can be used as an accurate reference phase signal for signal processing.

In the process of transmission of the transmitted pilot signals and data signals pass through the same path to the receivers. However, due to channel noise signal is usually mixed relative to the transmitted phase angle. The representation of the scalar products of the vector of the pilot signal on the information signal vectors of the I-channel and Q-channel are used as described for selecting data of I-channel and Q-channel of the signal selected by the finger of the receiver. In particular, the scalar product is used to determine the component values of the data vectors, which are in phase with the vector of the pilot signal, through the projection vectors of the pilot signal to each of the data vectors. One of the procedures for the allocation of the pilot signal from the signal selected by the finger of the receiver described below with sipcam in Fig. 8, and in pending patent application U.S. N 07/ the present invention and incorporated by reference.

Restoring the encoded group code character sub-workflow

Next will be described the recovery of the data transmitted on the I channel, one coded group ID substream a(i).

a(i) = A(i)Si= (Ai1Si1,...,Ai1Sip).

Suppose that before transmission to the j-th of the N receivers (Fig. 8) I and Q channels of the substream a(i) is converted into a valid sequence r(i), where

< / BR>
After expansion using signal Walsh W and corresponding sequences PNIand PNQthe resulting sequence SIjand SQjadapted for receiving the j-th receiver can be represented as

< / BR>
< / BR>
The composite signal is transmitted to the N receivers in a specific cell, defined as

< / BR>
where

< / BR>
For definiteness, assume that the signal S(t) is distributed according to m-th transmission path to the j-th receiver, which allows the received signal Rj(t) be expressed as

< / BR>
where the signal Rj(t) is a random phase shift relative to the local reference signal receiver, and where n(t) denotes the signal self-noise.

Refer to the block diagram in Fig. 12, which shows that j is animemanga "r" paths of transmission. The signal Rj(t) transmitted by the m-th path, passes through the band-pass filter having a transfer function h(t) and sampled at time t=kTwwhere Twrefers to the period between successive elements in the corresponding Walsh function Wj. As a result of these operations receive I and Q are the projection of RIm.kand RQm.kserved in the m-th demodulate finger 720, where

< / BR>
< / BR>
wheremcorresponds to the delay associated with the m-th transmission path and where noise components Niand Nqcan be defined as random processes with zero mean and variance2. According to the invention, evaluation of the sequence r(i) transmitted through m-th transmission path, are made from random projections RIm.kand RQm.km-m receiver finger 720.

Please refer to Fig. 13, which presents a block diagram of the m-th receiving finger 720, intended for the treatment of random projections of RIm.kand RQm.k. The receiving finger 720 includes a demodulation scheme/compression and rotation phase 740, and the scheme assessment phase and synchronization 744. According to the invention circuit 740 is designed for selective demodulation of the projections of RIm.kand RQm.kby executing the first set of even-numbered correlations with oresti using their assigned functions Walsh and PNQsequence. Each individual correlation is performed at the interval of L/p elements of Walsh, where L denotes the length of the signal Walsh Wjused to cover the "p" character sub-workflow, which is an integral part of the sequences SIjand SQj. Then the results of private correlations change in phase, to obtain the desired variables Ihat(m) and Qhat(m), which are derived m-m receiver finger 720. The specified phase rotation is performed in accordance with the estimated phase shift between the transmitted signal and is generated at the place of reception of the reference signal. In a preferred embodiment, the implementation of the scheme assessment phase and synchronization 744 includes a phase synchronization to generate the evaluation phase

The scheme assessment phase and synchronization 744 provides an assessment of the pilot/signal (Pm) transmitted by the m-th path, based on the intermediate signals generated by the circuit 740 during demodulation and compression of random projections of RIm.kand RQm.k. A dedicated pilot signal is used to rotate the phase of private correlations in the circuit 740, as well as for synchronization in selective adder 750 (Fig. 12). The results of these independent correlations are used to obtain the m-th pair of the sought displacement(1), 1=1,..., r generated by the set of "r" foster fingers 720, synchronized and combined as desired variables Qhat(m).

Please refer to Fig. 14, which shows that the m-th receiving finger 720 includes multipliers 780 and 782 for selective reception of the projections of RIm.kand RQm.kat the frequency of the PN expansion of 1.2288 MHz. Generator Walsh 786 is connected to both multipliers 780 and 782, where its output signals (Wj) multiplied by the projection of RIm.kand RQm.k. The receiving finger 720, in addition, includes PN generators 790 and 792 for filing PNIsequence in multipliers 798 and 800 and PNQsequence in multipliers 802 and 804. As shown in Fig. 14, the demodulated using Walsh projection R'Im.kand R'Qm.kof the multiplier 780 multiplied by PNIthe sequence in the multiplier 798 and PNIthe sequence in the multiplier 802. Similarly, the output of the multiplier 872 is multiplied in the multiplier 800 PNIthe sequence, and the multiplier 804 on PNQsequence.

Multipliers 798 and 800 compares the demodulated by the Walsh projection R'Im.kand R'Qm.kPNIsequence. Between PNIsequence and sequences R'Im.kIm.kand R'Qm.kmapped to PNQsequence using multipliers 802 and 804. Then the correlated outputs of the multipliers 798, 800, 802 and 804 are served in the appropriate drives I channel 814 and 816 and drives the Q channel 818 and 820. Drives 814, 816, 818 and 820 accumulate input information on L/p elements of Walsh, where, as before, denotes the signal length Walsh Wj. Drives 814, 816, 818 and 820 are used for the formation of private correlations AIn, AQnBInBQnduring each of the "p" intervals private correlation length L/p elements Walsh (i.e., n=1,...,p) appearing within each signal Walsh. Private correlation, AIn, AQnBInBQnserved on the delay elements 824, 826, 828 and 830 via the appropriate keys 834, 836, 838 and 840. The keys are transferred from normally open to closed at the end of each interval private correlation in accordance with the synchronization signals provided by the timing circuit 810. Private correlation, AIn, AQngenerated by the drives of the first channel 814 and 816 at the completion of the n-th interval of the correlation can be expressed as:

< / BR>
< / BR>
moreover, it is clear that private correlation B is alaysia rjn, j= 1, ...,p, represent the evaluation of the "p" integral values included in a valid sequence r(i) defined by the expression (5). Refer again to Fig. 14, where the scheme assessment phase and synchronization 744 includes the allocation of the pilot signal 850 for receiving signals phase of the pilot signal that are used to support synchronization in the receiving finger 720. The allocation of the pilot signal 850 includes a multiplier 854, which are output signals of the multipliers 798 and 802, and the multiplier 856 for multiplying outputs of the multipliers 800 and 804. Circuit 850, in addition, includes generators Walsh 862 and 864, intended for signalling Walsh Wiand W0accordingly, the multiplier 866. The resulting demodulated signal WiW0generated by the multiplier 866, respectively synchronized by time signals from circuit 810 in the generators Walsh 862 and 864, and supplied to the multipliers 868 and 870. The signal WiW0is multiplied by the output signal of the multiplier 854 in the multiplier 868, while the multiplier 870 performs the same operation in accordance with the signal WiW0and the output signal provided by multiplier 856.

The output signals of the multipliers 86 to form unbiased estimates of the phase of the received pilot signal. In the example implementation of the accumulation interval is the period 2rL where, as mentioned above, L corresponds to the period of the Walsh symbol, This accumulation interval usually takes periods of time length "rL" each appearing immediately before and after the moment when it is desirable to estimate the phase of the pilot signal. Synchronization between the output signals generated by the drive 814, 816, 818 and 820 and the output signal drives the allocation of pilot signals 874, 880, supported by elements of the delay 824, 926, 828 and 830. The delay of the signal performed by each delay element 824, 826, 828 and 830, selected equivalent in duration to the interval occupied by the "r" followed by characters Walsh. Accordingly, when generating the evaluation of the pilot signal, the corresponding n-m correlations private AInAQnthat drives 874 and 878 accumulated set of data samples Dj, (L/p)(n-r) + 1 j (L/p)(n+r).

The signals generated by the drives of the evaluation of pilot signals 882 and 886 correspond to the projections of the pilot signal (Pm) I-channel and Q-channel, the transmitted m-th path, and can be respectively represented as:

< / BR>
< / BR>
Please refer to Fig. 14, where the projection of the pilot signal of the I-channel and Q-channel are served each fosovi output, appropriate estimation of the sequence r(t) transmitted through the m-th path, weighted by the pilot signal Pm. The desired component of In(m) generated by the phase shifter I-channel 850 at the completion of the n-th interval of the correlation may be represented as

(17)

Selective adder 750 (Fig. 12) combines the desired components of the I-channel In(i) i=1,..., generated by the demodulator 720 during the n-th interval correlation in the composite desired component of Icnand combine the desired variables Q-channel Qn(i) compound in the desired component of Qcn. Compound desired components of Icnand Qcnsequentially outputted by the adder 750 in the form of sequences

< / BR>
< / BR>
where the indices indicate compliance with the "p" character sub, combined in a valid sequence r(i). Compound desired sequence Icand Qcserved in the multiplexers of the I-channel and Q-channel 870 and 874, which respectively form a parallel output signals

< / BR>
< / BR>
According to the invention the set of estimates of AI(t) the input character spotakova AI(i) transmitted on the I channel, where i=1,..., p, is generated by means of decorrelation sought after the character stream of AI(i) is performed through the following calculation of the scalar product r(i) to the desired sequence of II(i):

(18)

where ci,nand denotes the n-th member of the group codeiused to encode the i-th character of the stream. The calculation given in equation (18), based on the orthogonality between group codes used to encode the input symbol streams. That is,

< / BR>
for all j j. For p 4 equation (18) can be solved by performing, for example, a fast Hadamard transform (FHT) on sequences of ICTprovided by the multiplexer 870 (Fig. 12). Then assess the character of the flow is restored after multiplication and decoded to give the possibility to estimate the transmitted data.

This description of the preferred options for implementation are given in order to enable the person skilled in the art to implement or use the present invention. For professionals in this field are obvious, various modifications of the embodiments and what is articulated here, the basic principles can be used to implement other embodiments, without resorting to izobretatel is implementing in the framework of the disclosure of the invention.

1. The transmitter for modulation of the information signal for transmission in the communications system spread spectrum, which includes an encoder, interleaver, a means for generating an orthogonal function signal, characterized in that it contains means demuxing the specified information signal in the first and second subsignal, first means for combining the specified first subsignal with the first group ID and for combining the specified second subsignal with the second group code orthogonal to the first group code, with the possibility of receiving the first composite coded group code signal, means for modulation of the specified first composite coded group code signal by means of an orthogonal function signal for forming a first modulated signal.

2. The transmitter under item 1, characterized in that it further includes means for generating pseudotumor signal in a predetermined PN code and the means for the combined specified first modulated signal with the specified pseudotumour signal in a predetermined PN code to provide the first output signal.

3. The transmitter under item 1, is different and the fourth subsignal, second means for combining the specified third subsignal with the third group code and for combining the specified fourth subsignal with the fourth group code with the possibility of receiving the second encoded composite group code signal, and the first, second, third and fourth group codes are mutually orthogonal, and means for modulation of the specified second encoded composite group code signal by means of an orthogonal function signal to provide a second modulated signal.

4. Transmitter on p. 3, characterized in that it further comprises means for generating in-phase pseudotumor (PNI) and quadrature pseudotumor (PNQ) signal in predetermined PN codes, and means for combining the specified PNIsignal from the first modulated signal to provide an I output signal and for combined specified PNQsignal with the specified second modulated signal to provide a Q output signal.

5. The transmitter under item 4, characterized in that it further includes means for modulating in-phase (I) and quadrature (Q) carrier signals with a given phase sootechest for combining includes first means for copying the first subsignal for receiving the first and second identical character streams, first means for multiplying each symbol stream by a factor of the first group of code for providing first and second intermediate sequences, the first multiplexer for combining these first and second intermediate sequences in the first coded group code signal, second means for copying the second subsignal for receiving the third and fourth identical character streams, second means for multiplying the third and fourth character of the flow coefficient of the second group of code for providing third and fourth intermediate sequences a second multiplexer for combining these third and fourth intermediate sequences in the first coded group code signal and means for combining these first and second coded group code signals into a first composite coded signal.

7. The transmitter under item 1, characterized in that the means for combining the first and second coded group code signals includes means for converting the first and second coded group code signals into an integer chosen from the set is the speed of data transmission for simultaneous transmission in the communications system spread spectrum, includes encoder, interleaver, a means for generating an orthogonal function signal, characterized in that it contains means for combining each of the information signal from one of the group codes from the set of the p group codes to obtain a set of coded p-code signals, means for combining these p coded group code signals and to generate the encoded composite group code signal, means for modulating the encoded composite group code signal orthogonal functional signal to provide the first modulated signal.

9. The transmitter under item 8, characterized in that it further includes means for generating pseudotumor signal in a predetermined PN code, and means for combining the modulated signal pseudotumour signal in a predetermined PN code with the possibility of providing the first output signal.

10. The transmitter under item 8, characterized in that the means for combining the information signals with the group codes includes means for copying the first of these information signals to obtain a set of p identical character streams, among the patients group code included in the first group of codes, to provide a set of p intermediate sequences, and a multiplexer for combining the p intermediate sequences in the first coded group code of signals.

11. Transmitter on p. 5, characterized in that it further includes means for transmitting the I-modulated and Q modulated carrier signals on the I and Q channels, respectively.

12. Communication system with spread spectrum for modulation of the information signal to be transmit in-phase (I) and shifted in phase 90o(Q) by using the carrier signal and the copy carrier signal shifted in phase by 90omoreover , this system contains a transmitter comprising an encoder, interleaver, a means for generating an orthogonal function signal, means for generating in-phase pseudotumor (PNI) and quadrature pseudotumor (PNQsignals in predetermined PN codes, characterized in that it contains a tool for demuxing of the information signal in the first and second sets of subsignals, means for combining the set of subsignals with the first set of orthogonal group codes for the signals with the second set of orthogonal group codes, to obtain a second encoded composite group code signal, means for combining PNIsignal from the first composite coded group code signal and the orthogonal functional signal for forming a first modulation signal, and for combining PNQsignal with the second composite coded group code signal and the orthogonal functional signal for receiving the Q signal modulation.

13. The system under item 12, characterized in that it includes means for modulating a carrier signal using the first modulation signal and the modulation copies of a carrier signal with the Q signal modulation for the formation of I-modulated and Q-modulated carrier signals, respectively, and the means of transmission of I-modulated and Q modulated carrier signals on the I and Q channels of communication.

14. System on p. 13, characterized in that it further includes a receiver containing means for obtaining the assessment information signal in accordance with the first modulation and Q-modulated carrier signal received by the I and Q channels of communication.

15. The communication system according to p. 14, characterized in that said receiver further includes means for obtaining an intermediate PFD functional signal.

16. The communication system according to p. 15, characterized in that the receiver further includes means for generating a first signal compression through replication PNIsignal and the first tool to correlate these intermediate signals by using the first signal compression, to provide the first set of signals in-phase (I) and quadrature (Q) projections.

17. The communication system according to p. 16, characterized in that it further includes means for combining the orthogonal function signal with the pilot signal to provide a modulated pilot signal, means for transmitting the modulated pilot signal on the pilot channel signal.

18. The communication system under item 17, characterized in that the receiver further includes means for demodulating the modulated pilot signal transmitted on the pilot channel signal, means to derive an estimate of the pilot signal transmitted on the pilot channel signal, the first tool rotation phase to generate a first information signal based on the first set of I and Q are the projection and evaluation of a carrier signal, pilot signal.

19. The communication system under item 18, characterized in that the receiver is additionally the which means for correlating these intermediate signals by using the second signal compression, to provide a second set of signals in-phase (I) and quadrature (Q) projections.

20. The communication system according to p. 19, characterized in that the receiver further includes a second tool rotation phase to generate the estimate of the second information signal based on a second set of I and Q projections and evaluation of a carrier signal, pilot signal.

21. The communication system under item 18, characterized in that the receiver further includes means for delaying the first set of signals I and Q projections.

22. The modulation method information signal for transmission in the communications system spread spectrum, consisting in the fact that produce coding, interleaving the information signal, generating an orthogonal function signal, wherein producing the demultiplexing of the information signal in the first and second subsignal, the combination of first subsignal with the first group ID and the combination of the second subsignal with the second group code orthogonal to the first group code, with the possibility of receiving the first composite coded group code signal, generating an orthogonal function signal, and the modulation of the first composite coded La.

23. The method according to p. 22, characterized in that it additionally produce generating pseudotumor signal in a predetermined PN code, and combining the first modulated signal with pseudotumour signal in a predetermined PN code with the possibility of receiving the first output signal.

24. The method according to p. 23, characterized in that it additionally produce demultiplexing the information signal in the third and fourth subsignal, combining subsignal with the third group code m combining the fourth subsignal with the fourth group code with the possibility of receiving the second encoded composite group code signal, and the first, second, third and fourth group codes are mutually orthogonal, and the modulation of the second composite encoded group code signal orthogonal functional signal to obtain a second modulated signal.

25. The method according to p. 24, characterized in that it further perform generating in-phase pseudotumor (PNI) and quadrature pseudotumor (PNQsignals in the set R codes, and combining PNIsignal from the first modulated signal to provide a 1 output signal and for combining is to modulate a set of p information signals with equal data rate for simultaneous transmission in the communications system spread spectrum, consisting in the fact that produce coding, interleaving the information signal, characterized in that it is produced by combining each of the information signal from one of the group codes of the p group codes to obtain a set of p-coded group code of signals, the combination of p-coded group code signals with the possibility of generating a composite encoded group code signal, the modulation encoded composite group codes signal orthogonal functional signal for forming a first modulated signal.

27. In the communication system, multiple access, code-division multiplexing method for forming in-phase (I) and quadrature (Q) channels of communication spread spectrum transmission information signal, consisting in the fact that produce coding, interleaving the information signal, generating a phase pseudotumor (PNI) and quadrature pseudotumor (PNQsignals in predetermined PN code, wherein the produce demultiplexing the information signal in the first and second sets of subsignals, combining the first set of subsignals with the first set of orthogonal is the second set of subsignals with the second set of orthogonal group codes to obtain a second encoded composite group code signal, combining PNIsignal from the first composite coded in the group code signal and the orthogonal functional signal to provide the first modulation signal, and combining PNQsignal with the second composite coded group code signal and the orthogonal functional signal for the formation of the Q signal modulation.

28. The method according to p. 27, characterized in that it additionally produce a modulated carrier signal of the first modulation signal and the modulation copies of a carrier signal Q of the modulation signal for the formation of I-modulated and Q-modulated carrier signals, respectively, and the transfer of I-modulated and Q modulated carrier signals on the I and Q channels of communication.

29. The method according to p. 29, characterized in that it additionally produce the reception I-modulated and Q modulated carrier signals I and Q communication channels, and receive on the basis of their assessment of the information signal.

30. The method according to p. 29, characterized in that the step of obtaining evaluation information signal to produce demodulation of the received carrier signal with replicas of the orthogonal function signal PNIsignal and PNQsignal.

 

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FIELD: radio communications.

SUBSTANCE: proposed method intended for single-ended radio communications between mobile objects whose routes have common initial center involves radio communications with aid of low-power intermediate transceiving stations equipped with non-directional antennas and dropped from mobile object, these intermediate transceiving drop stations being produced in advance on mentioned mobile objects and destroyed upon completion of radio communications. Proposed radio communication system is characterized in reduced space requirement which enhances its effectiveness in joint functioning of several radio communication systems.

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EFFECT: reduced mass and size of transceiver stations, enhanced noise immunity and electromagnetic safety of personnel.

2 cl, 6 dwg

FIELD: radio communications.

SUBSTANCE: proposed method intended for data transfer to mobile object from stationary one residing at initial center of mobile-object route using electronic means disposed on stationary and mobile objects involves radio communications with aid of low-power intermediate transceiving stations equipped with non-directional antennas and dropped from mobile object, these intermediate transceiving drop stations being produced in advance on mobile object. Proposed radio communication system is characterized in reduced space requirement which enhances its effectiveness in joint functioning with several other radio communication systems.

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FIELD: radio communications.

SUBSTANCE: proposed method for single-ended radio communications between mobile objects whose routes have common initial center involves use of low-power intermediate transceiving stations equipped with non-directional antennas and dropped from mobile objects. Proposed radio communication system is characterized in reduced space requirement and, consequently, in enhanced effectiveness when operating simultaneously with several other radio communication systems.

EFFECT: reduced mass and size, enhanced noise immunity and electromagnetic safety for attending personnel.

2 cl, 7 dwg, 1 tbl

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