Reception device, reception method and programme

FIELD: information technology.

SUBSTANCE: reception device has apparatus for determining the first, second and third position of the initial position of the fast Fourier transform (FFT) interval, apparatus for selecting one of the determined initial positions of the FFT interval, FFT apparatus for performing fast Fourier transformation of an orthogonal frequency division multiplexing (OFDM) signal in the time domain by using the initial position selected by the selection apparatus in order to generate a first OFDM signal in the frequency domain. The apparatus for determining the first position calculates the value of correlation between the OFDM signal in the time domain and the signal obtained by delaying said time-domain OFDM signal by the length of the effective symbol. Apparatus for determining the second position estimates the channel characteristic for transmitting the OFDM signal and the delay profile before estimating the value of interference between symbols with respect to each of the FFT intervals. The apparatus for determining the third position establishes the FFT interval with offset from the FFT interval used for generating the first OFDM signal, for generating the second OFDM signal before eliminating distortions from the first and second OFDM signals in order to generate an adjusted signal.

EFFECT: reducing multiple-beam interference by adjusting the symbol synchronisation signal.

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The technical field to which the invention relates.

The present invention relates to a pickup device, method and program. More specifically, the invention relates to a pickup device, method and program, by which method, using which synchronize the OFDM symbols (MOCR, multiplexing orthogonal frequency division), switch in accordance with the circumstances.

The level of technology

One of the modulation techniques, currently used for digital terrestrial broadcasting, called MOOR. In accordance with the technology MOCR many orthogonal subcarriers provided within the bandwidth of the transmission. Data prescribed amplitude and phase of each subcarrier and execute their digital modulation using PSK (QPSK, phase shift keying) or QAM (QAM, quadrature amplitude modulation).

According to the technology MOCR carry out the separation of the entire bandwidth into a large number of subcarriers. This means that the bandwidth is limited, and the transmission rate is reduced for each subcarrier, but the overall transmission rate remains the same as in traditional technologies of modulation.

In accordance with the technology MOCR data assign multiple subcarriers in such a way that modulate data by performing IFFT operation (ABOUT the f, inverse fast Fourier transform). The signal MOCR, the resulting modulation, demodulated by performing the operation FFT (FFT, fast Fourier transform).

Thus, the device for signal transmission MOCR can be made of schemes relating to OBPF, and a device for receiving the signal MOCR can be formed using schemes related to the FFT.

Given the above properties, technology MOCR often used in terrestrial settings of the digital broadcast, which are highly susceptible to multipath interference. Standards for terrestrial digital broadcasting, in which technology is used FDM (CDM multiplexing frequency division), include DVB-T (DVB-H, digital terrestrial television), ISDB-T (XCV-N, integrated service digital terrestrial broadcasting) and XCV-NSV (XCV-NSV, integrated service digital terrestrial sound broadcasting).

Figure 1 shows the symbols MOCR. In accordance with the technology MACHR signaling occurs in modules called symbols MOCR. As shown in figure 1, one character MOCR consists of effective symbols representing the time window within which perform OBPF during transmission, and guard interval (below called GI (ZI)), which replicate some form of vibrations in the direction of end the effective symbol.

ZI insert chronologically before the effective symbol. In accordance with the technology MOCR insert ZI prevents interference that may occur between characters MOCR in an environment with multipath propagation.

Many of these characters MOCR are brought together to form a single frame transmission MOCR. As an illustration of one frame transmission MOCR form of 204 symbols MOCR in accordance with the standard XCV-N. The position in which you want to insert a pilot signal, determine the modules of the transmission frame MOOR.

Technology MOCR involves the use of methods based on the QAM to modulate the subcarriers. The technology MOCR influenced by negative effects, such as multipath interference, during transmission, resulting in the amplitude and phase of each subcarrier may be different during the reception, from what they originally were. Multipath interference can be caused by, as an illustration, reflections from mountains, buildings, or may be caused by SFN (SFN, a single-frequency network).

On the receiving side, therefore, it is necessary to align the signals to ensure that the amplitude and the phase of the received signal were the same as in the original transmission.

In accordance with the technology MOOR side transfer discrete inserts pilot shall ignal in the transmitted signals, moreover, this pilot signal is a known signal having a predetermined amplitude and a predetermined phase. The receiving side receives the frequency response of the used transmission channel on the basis of the amplitude and phase of the pilot signal for equalizing a received signal. The pilot signal is used thus to calculate the characteristics of the transmission channel, known as the scattered pilot signal (below called the signal SP (RP)).

Figure 2 schematically presents another typical structure of the layout of the TL signal within symbols MOCR in accordance with the standard XCV-N. Figure 2 on the horizontal axis presents the set of subcarriers identifies subcarriers signal MOOR, and on the vertical axis the numbers of characters MOCR identifying characters MOCR signal MOCR. Non subcarriers correspond to the frequencies, and the number of characters MOCR correspond with the time.

In figure 2 each empty circle represents the data symbol transmitted on each subcarrier, and each shaded circle indicates the signal RP. As shown in figure 2, the signal RP is set intervals four characters MOOR in the time direction and at intervals of 12 subcarriers in the direction of frequency.

In the case of standard XCV-N signal, called (UCPM/VK, configuration management, transmission and multiplexing/auxil athelny channel), placed in each subcarrier. The signal UCPM/VK designed specifically for signal synchronization, which provides for pickup device obtaining information about the transmission parameters, which operated during the transmission (that is, information such as the used modulation method and the coefficient encoding), and the number of character for a given character within the transmission frame MOOR.

In the case of standard DVB-H insert a signal, called signal TPS. As with signal UCPM/VC in accordance with the standard XCV-N, the signal TPS also form using the synchronization signal, which provides the transmission parameters and enables the synchronization of the frame. In this regard, the reader can refer to Japanese laid patent No. 2005-303440.

The invention

On the characteristics of the receiving device receiving significantly affects the accuracy of the synchronization signal symbol, which is used to determine the FFT interval during which to perform the FFT. The synchronization signal symbol should be adjusted in such a way as to minimize multipath interference. For example, adjustment is performed so that the position of the boundary between ZI and an effective symbol shown in figure 1, was designated as the initial position of the interval is PF.

Thus, it is preferable to use different signals to obtain synchronization character at different points in time and to choose optimally in accordance with one of the other ways of ensuring synchronization of the symbol.

The present invention was made in view of the above circumstances and aims at pickup device, method and program, under which switches the method by which synchronizes the characters MOCR, in accordance with the circumstances.

When performing the present invention and in accordance with one variant of its embodiment provided by the reception device, comprising: means for determining a first position that is intended for calculating correlation values between the signal MOCR in the field of time, the components of the signal MOCR in the field of time, representing the character MOOR, on the one hand, and a signal obtained by delaying the signal MOCR in the field of time on the length of the effective symbol, on the other hand, to determine the start position of the FFT interval, which is equal to the length of the effective symbol and which is used as an interval signal representing a target for FFT performed using means of FFT, with reference to the higher of the correlation values; means for determining a second location, designed the TES to assess the characteristics of the transmission channel is known signal, included in the first signal MOCR in the frequency domain comprising signal MOCR in the frequency domain obtained by performing FFT for signal MOCR in the field of time before interpolation estimate characteristics of the transmission channel in the time direction to obtain assessment data characteristics of the transmission channel, before performing OMPF data for evaluation of characteristics of the transmission channel, to assess the profile of the delay before measurement of the interference between symbols in relation to each of the set of candidates of the FFT interval based on the delay profile, before determining the initial position of the candidate interval FFT with the least amount of interference between symbols in the initial position of the interval FFT, which represents a goal for the FFT performed by using the FFT; means for determining a third location that is designed to set a different interval FFT in position established with the offset of the FFT interval used to generate the first signal MOCR in the frequency domain, before performing FFT for signal MOCR in the field of time, within the other FFT interval, for generating the second signal MOCR in the frequency domain, before removing the distortion from the first and second signals MOCR in the frequency domain, using the characteristics of the transmission channel is each of all subcarriers, obtained by interpolation of data evaluating the performance of the transmission channel in the direction of the frequency, to generate an aligned signal before determining the start position of the FFT interval, which represents a goal for the FFT performed by using the FFT, on the basis of the quality of the generated aligned signal; a selector that is designed to select one of the start positions of the FFT interval, which is determined by means of determining first, second and third positions; and the FFT tool designed to perform FFT for signal MOCR in the field of time by using the initial position selected by the selector, in the initial position of the FFT interval, for generating a first signal MOCR in the frequency domain.

Preferably, the pickup device may further include assessment tool designed to assess the numbers of the received data symbol based on the first signal MOCR in the frequency domain; in which the picker can choose the initial position of the FFT interval, which has been determined by means of determining the first position, when it marked the beginning of the demodulation, and the picker additionally selects the starting position of the FFT interval, which was selected by the means for determining the second position instead of what about the initial position, the selected means of determining the first position, after the evaluation of the number of symbol evaluator.

Preferably, the pickup device may further include a synchronization tool frame designed for the synchronization of the transmission frame MOCR, composed of multiple characters MOCR, based on the first signal MOCR in the frequency domain; in which, when the frame transmission MOCR synchronized using the synchronization frame, the selector may select such initial position of the FFT interval, which is defined by using the definition of the third position instead of the initial position defined by means of determining the second position.

Preferably, the means for determining the first position may determine the position shift of the maximum of the correlation values for the length of the guard interval as the start position of the FFT interval, which represents a goal for the FFT performed by using the FFT.

Preferably, the means for determining the second position can evaluate the magnitude of the interference between symbols in relation to each of the multiple paths that make up the path of multipath propagation, by multiplying the length in the time direction, which is the interference with another character when the mouth is avleat candidate for the FFT interval, the power path, which is the interference from the other symbol, and by summing the works resulting from the multiplying performed for each of these ways.

Preferably, the means defining the third position can define the start position of the FFT interval used to generate the first signal MOCR in the frequency domain, as the start position of the FFT interval, which represents a goal for the FFT performed by using the FFT, if the quality of the aligned signal obtained from the first signal MOCR in the frequency domain, will be higher than the quality of the aligned signal received from the second signal MOCR range of frequencies, and means for determining a third location additionally determines the initial position of the other interval FFT used for generating the second signal MOCR in the frequency domain, as the start position of the FFT interval representing the target of the FFT performed by using the FFT, if the quality of the aligned signal received from the second signal MOCR in the frequency region higher than the quality of the aligned signal obtained from the first signal MOCR in the frequency domain.

In accordance with another alternative embodiment of the present invention provides a method and a program, provide the traveler execution by computer processing, each of the processing includes the following steps: provide a calculation tool for determining the first position of the correlation values between the signal MOCR in the field of time, the components of the signal MOCR in the field of time, representing the character MOOR, on the one hand, and a signal obtained by delaying the signal MOCR in the field of time, the length of the effective symbol, on the other hand, to determine the start position of the FFT interval, which is equal to the length of the effective symbol and which is used as an interval signal representing a target for FFT performed using the FFT, with reference to the maximum value correlation; provides an assessment tool for determining the second position of the characteristics of the transmission channel is known signal included in the first signal MOCR in the frequency domain comprising signal MOCR in the frequency domain obtained by performing FFT for signal MOCR in the field of time before interpolation assess the characteristics of the transmission channel in the time direction to obtain assessment data characteristics of the transmission channel, before performing OBPF according to evaluation of the characteristics of the transmission channel, to assess the profile of the delay before measurement of the interference between symbols in relation to each of the set of candidates of FFT intervals, based on the île delay, before defining the initial position of the candidate interval FFT, in which the amount of interference between symbols is the smallest, as the start position of the FFT interval, which represents a goal for the FFT performed by using the FFT; provide installation tool for determining a third location of another interval FFT in position with the offset of the FFT interval used to generate the first signal MOCR in the frequency domain, before performing FFT for signal MOCR in the field of time, within the other FFT interval, for generating the second signal MOCR in the frequency domain, before removing the distortion from the first and second signals MOCR in the frequency domain using the characteristics of the transmission channel of each of all subcarriers obtained by interpolation of data evaluating the performance of the transmission channel in the direction of the frequency, to generate an aligned signal before determining the start position of the FFT interval, which represents a goal for the FFT performed by using the FFT, on the basis of the quality of the generated aligned signal; choose one of the start positions of the FFT interval, identified by means of identifying the first and third positions; and perform FFT for signal MOCR in the field of time, using the selected initial Polo is a group of as the start position of the FFT interval to generate a first signal MOCR in the frequency domain.

In accordance with a variant embodiment of the present invention selects one of the possible initial positions of the FFT interval, which was defined means of identifying the first and third positions. Then perform FFT for signal MOCR in the field of time, using the selected initial position as defined for the starting position of the FFT interval, and accordingly generate a first signal MOCR in the frequency domain.

It should be noted that the pickup device can be either an independent device or one of the internal blocks of the device.

Thus, the present invention being embodied, as noted above, allows you to switch the method of synchronization symbols MOCR in accordance with the circumstances.

Brief description of drawings

Additional advantages of the present invention will be understood when reading the following description and attached drawings on which:

figure 1 is a schematically illustrated view of representing characters MACR;

figure 2 schematically shows a view representing the structure layout of signals SPM;

figure 3 shows a block diagram representing a typical partial structure of the pickup device MACR;

figure 4 shows a block diagram Ave is Glavnaya another typical partial structure of the pickup device MACR;

figure 5 shows a block diagram representing an additional typical partial structure of the pickup device MACR;

6 shows a block diagram representing a typical overall structure of the pickup device MACR;

7 - shows a diagram representing the data evaluation characteristics in the time direction;

Fig - shows a diagram representing the data interpolation characteristics in the direction of frequency;

Fig.9 shows a block diagram of a sequence of operations explaining the processing of switching performed by the controller synchronization symbol;

figure 10 shows a block diagram representing a typical block structure correlation guard interval;

11 is a schematically illustrated view representing typical signals processed by the blocks indicated in figure 10;

Fig is shown a diagram illustrating a multipath propagation environment;

Fig - shows a diagram illustrating how to estimate the value of the index (IC, interference between symbols);

Fig - shows a diagram representing a typical filter evaluation IC;

Fig - shows a diagram representing the profile of a delay and a filter evaluation IC, superimposed on each other;

figa, 16B and 16C is shown diagrams that represent typical results of the filtering process;

figa, 17B and 17C is shown diagrams illustrating how to detect the position of the characters;

Fig - shows a diagram representing the relationship between the interval FFT demodulation and FFT interval control;

Fig - schematically shows a view representing another interdependence between interval FFT demodulation and FFT interval control;

Fig shows a block diagram representing a typical block structure calculation of signal quality;

Fig - shows a diagram representing a typical data interpolation with zero value in the field of time; and

Fig shows a block diagram representing a typical structure of hardware of the computer.

Detailed description of the invention

[General structure of the pickup device MOCR]

Figure 3-5 shows a flowchart representing typical patterns of the device 100 receiving MOCR made in practice, as a variant embodiment of the present invention. Each of Fig.3-5 shows the partial structure of the device 100 receiving MOCR. The relationship between these structures is shown in generalized form in Fig.6.

The antenna 101 receives a broadcast wave signal transmission MOCR transmitted by the transmission device station broadcasts, which are not shown. The accepted wave broadcast output to the tuner 102. The tuner 102 is composed of an arithmetic unit 102A and the local oscillator 102b.

The arithmetic unit 102A RF (RF, radio frequency) signal received from the antenna 101, the signal from the local oscillator 102b, for frequency conversion of the RF signal in the signal IF (FC, intermediate frequency). The if signal output in the BPF (BPF, bandpass filter)103.

The local oscillator 102b generates a sinusoidal signal having a predetermined frequency, and outputs the generated signal in the arithmetic unit 102A. PF 103 filters the if signal from the tuner 102, and transmits this filtered signal in block 104 A/D (a/d, analog-to-digital) conversion.

Block 104 a/d conversion converts the if signal coming from the PF 103, from analog to digital form, using the carrier frequency, and outputs the digital if signal in block 105 orthogonal demodulation. Block 105 orthogonal demodulation performs orthogonal demodulation of the if signal coming from block 104 a/d conversion, and outputs a signal MOOR in the main bandwidth.

In the following description, the signal MOOR in the main bandwidth before the FFT is called a signal MOCR in the field of time. The signal MOCR in the field of time is a complex signal that includes a component of a real axis component (I) component and imaginary axis component (Q)obtained from the orthogonal demodulation. The signal MOCR in the field of time, the output unit 105 orthogonal demodulation, served in the block 06 correction offset.

Block 106 correction, performs various correction signal MOCR in the field of time, coming from block 105 orthogonal demodulation. As an illustration of the block 106 correction performs offset samples obtained by block 104 a/d conversion (i.e. corrects the deviations of the moments of the sample), on the basis of the correction signal sample bias supplied from block 112 of the sample/carrier synchronization.

In addition, the block 106 correction, performs the offset for the carrier frequency received from the block 105 orthogonal demodulation (i.e. corrects deviations from the carrier frequency used by the transmission device), on the basis of the correction signal of the carrier signal transmitted by block 112 of the sample/carrier synchronization.

The signal MOCR in the field of time, processed by the block 106 correction, served in the block 107 synchronization symbol, and block 108 FFT demodulation, and in block 115 FFT control, as shown in figure 4.

Block 107 synchronization symbol sync the characters MOCR and displays in block 108 FFT demodulation flag synchronization symbol indicating the start position of the FFT interval. Block 108 FFT demodulation performs FFT aimed at interval signal, having the same length, and the effective symbol length. The initial position of the interval of the signal denoted by the flag synchronization symbol.

Block 107 synchronization symbol selects one of three positions: the position defined on the basis of the signal MOCR in the field of time before the FFT, the position defined on the basis of the characteristics of the transmission channel which was obtained from the signal after the FFT, or the position specified based on the signal alignment. The method for determining each of these provisions in the initial position of the FFT interval will be described in detail below. In the following description start position of the FFT interval may simply be called a symbol position, as appropriate.

In addition, the block 107 synchronization symbol displays the flag DFT (DFT, discrete Fourier transform) unit 115 FFT control. As will be described in detail below, the flag DFT is a flag that indicates the initial position of the interval signal toward which the processing performed by block 115 FFT control. Block 115 FFT control performs processing equivalent to the FFT interval established shifted by a given amount relative to the FFT interval, which was aimed processing performed by the block 108 FFT demodulation.

Block 108 FFT demodulation sets the FFT interval, the interval having the length of the effective symbol, starting from the position indicated by the synchronization flag symbol, filed the components is 107 synchronization symbol.

In addition, the block 108 FFT demodulation selects the signal of the FFT interval of the signal MOCR in the field of time, coming from block 106 correction, and performs FFT for the selected signal of the FFT interval. The FFT operation performed by the block 108 FFT demodulation, provides data that has been transmitted using subcarriers, that is, the signal MOCR representing a transmitted symbol in the IQ plane. The output unit 108 FFT demodulation is specified by the following expression (1):

where "Y" denotes the output of block 108 FFT demodulation, the subscript "m" represents the number of symbol subscript "k" represents the number of carrier, "H" represents the frequency response of the current transmission channel, "X" for the transmission signal, represented by point QPSK or QAM signal, and "N" for an item that integrates components of the interference originating from noise components and the resulting multipath propagation.

As described above, the signal after FFT processing is expressed by adding noise and other components to what was obtained by multiplying the transmitted signal at the frequency response of the transmission channel.

The signal MOCR obtained by performing FFT for signal MOCR in the field of time, represents the signal in the frequency domain. In the following description, the signal MOCR that PR who was processing the FFT, you can call the signal MOCR in the frequency domain, as appropriate. The signal MOCR in the frequency domain transmit block 109 alignment (figure 5), in block 112 the sample/carrier synchronization, unit 113 estimates the number symbol, in block 114, the synchronization frame and the block 115 FFT control.

Block 191 selection unit 109 alignment selects one of the two rooms of the symbol number of the symbol transmitted by unit 113 estimates the number symbol (symbol MOCR), or the number of character specified by block 114, the synchronization frame. Missed the number of the character selected thus, the output block 192 selection of the pilot signal.

Block 192 selection of the pilot signal allocates RP signals are arranged, as shown in figure 2. The allocation of the TL signals requires determining where the currently received data is sorted in the order of the characters. Block 191 of choice passes to block 192 selection of pilot signal information to determine the sequence number.

For example, the number of the symbol transmitted by unit 113 estimates the number symbol, chosen in the range from the start time of the demodulation prior to completion of the synchronization frame and transmit the synchronization flag of the frame. After the sync frame select the number of the symbol transmitted by the block 114, the synchronization frame.

In accordance with the number of symbols transmitted block 191 of choice, the Lok 192 selection of the pilot signal selects the TL signal, last modulation Vpmn of signal MOCR in the frequency domain, the transmitted block 108 FFT demodulation.

For example, if the currently received data has a number of 0 symbols, this means that the signal RP is passed using subcarriers having the numbers 0, 12 and 24 subcarriers; block 192 selection of the pilot signal allocates accordingly, the TL signal. Block 192 selection of the pilot signal displays the selected SPM signal in block 193 division.

Block 193 division divides the TL signal coming from block 192 selection of the pilot signal, the reference signal from block 194 generating a reference signal, in doing so, the evaluation of the characteristics of the transmission channel PN signal.

The value of the characteristic of the transmission channel PN signal is expressed by the expression (2)below. The signal X used to obtain the values of the characteristics of the transmission channel, generate a using block 194 to generate the reference signal.

where the symbol "~" indicates that the value to which it is attached, represents the estimated value. Subscripts "n" and "1" indicate the position of the TL signal.

Block 193 dividing the output data of the characteristics of the transmission channel, representing the evaluation of the characteristics of the transmission channel, in block 195 evaluation of the transmission channel in the time direction. Block 194 generating oporn the signal generates and outputs the reference signal, intended for use by unit 193 division.

Block 195 evaluation of the transmission channel in the time direction evaluates the characteristics of the transmission channel symbols MOCR, built in the time direction of subcarriers in which linked RP signals. The characteristic of the transmission channel in the direction of the time estimate to illustrate, using interpolation or by accessing the adaptive filter.

Block 195 evaluation of the transmission channel in the direction of the time displays estimates of the characteristics in the time direction, represents a characteristic of the transmission channel, at intervals of three subcarriers in a block 196 adjust the phase and in block 200 the choice of the optimal coefficient of the filter.

7 schematically shows a view representing estimates of the characteristics in the time direction. Assessment data characteristics in the time direction, such as shown in Fig.7, get with the help of block 195 evaluation of the transmission channel in the time direction using the data characteristics of the transmission channel in relation to the TL signal, are arranged, as shown in figure 2. 7, each of the blank and shaded circles represent subcarriers (transmitted symbol) signal MOCR. Each of the shaded circles denotes the transmitted symbol, the characteristic of the transmission channel which is assessed in accordance with obrabotki, performed by block 195 evaluation of the transmission channel in the direction of time.

The characteristic of the transmission channel estimate in the time direction using the data characteristics of the transmission channel in relation to the TL signal. This allows characterization of the transmission channel of each character MOCR through the interval of three subcarriers.

Block 196 adjust the phase adjusts the phase data evaluation characteristics in the time direction, the transmitted block 195 evaluation of the transmission channel in the time direction, overlapping with the center of the filter, which passes the block 200 of the choice of the optimal filter coefficient. Assessment data characteristics in the time direction adjust by turning the complex signal components I and Q), representing the value of the sampling data evaluation characteristics in the time direction, in accordance with the number of the subcarrier to subcarrier corresponding to the sampled value, and in accordance with the center of the filter.

Block 196 adjustable phase displays estimates of the characteristics in the time direction with the adjusted phase in block 197 interpolation filter frequency and in block 107 synchronization symbol (figure 3).

Block 197 interpolation filter frequency changes the bandwidth of the interpolation filter based on the coefficient transferred from the block 200 of the choice of the optimal filter coefficient, to issue the log processing interpolation frequency, resulting in the characteristic of the transmission channel interpolate in the direction of frequency. As an illustration, block 197 interpolation filter frequency interpolates two zero, as the newly obtained sample values between the values of the sampling data evaluation characteristics in the time direction, the transmitted block 195 evaluation of the transmission channel in the direction of time.

In addition, the block 197 interpolation filter frequency uses LPF (low-pass, filter low frequency), filter data for evaluation of characteristics in the time direction, the count value of the sample which is three times larger than the original data for interpolation characteristics of the transmission channel in the direction of frequency. The width of the band-pass filter LPF (interpolation filter), filter, regulate, using a coefficient that is passed to block 200 of selecting the optimal coefficient of the filter.

Filtering using an interpolation filter with adjustable bandwidth, block 197 interpolation filter frequency removes duplicate components related to the zero interpolation of the data evaluation characteristics in the time direction. This allows characterization of the transmission channel, interpolated in the direction of frequency.

Block 197 interpolation filter frequency outputs in block 199 division and unit 117 division features istica transmission channel, interpolated in the direction of the frequency, that is, the interpolation data characteristics in the direction of the frequency representing the characteristic of the transmission channel all subcarriers.

On Fig schematically shows a view representing the data interpolation characteristics in the direction of frequency. Block 197 interpolation filter frequency uses assessment data characteristics in the time direction, represents a characteristic of the transmission channel, at intervals of three subcarriers to obtain the characteristics of the transmission channel of each of subcarriers constituting the symbol MOCR, shown shaded on Fig.

Block 198 adjust the phase adjusts the phase of the signal MOCR in the frequency domain, the transmitted block 108 FFT demodulation, in accordance with the center of the filter, which passes the block 200 of the choice of the optimal filter coefficient. The signal MOCR in the frequency domain with the adjusted phase output in block 199 division.

Block 199 division divides the signal MOCR in the frequency domain, coming from block 198 adjustment phase, the value of the transmission channel, to correct the distortion of the amplitude and phase of the signal MOCR in the frequency domain, obtained in the transmission channel. The signal MOCR in the frequency domain after the correction of distortion output as a balanced signal.

Distortions, which were obtained by the signal MOCR, as an illustration, as a result, the antibodies of multipath propagation through the transmission channel, act as multiplication signal MOCR. Thus, distortion of the received signal MOCR in the transmission channel, adjust by dividing the actually received signal MOCR on the characteristics of the transmission channel. The aligned signal output unit 199 division, passed in block 110 error correction in block 107 synchronization symbol.

Block 200 of the choice of the optimal filter coefficient chooses the optimal interpolation filter for use in processing the interpolation frequency in accordance with the signal MOCR in the range of frequencies passed by the block 108 FFT demodulation, and data-based evaluation characteristics in the time direction, the transmitted block 195 evaluation of the transmission channel in the direction of time.

As an illustration of the block 200 of the choice of the optimal filter coefficient tries to perform the processing of the interpolation frequency in many conditions using interpolation filters, the width and position from the center of the bandwidth of each of which change. The processing unit 200 of the choice of the optimal coefficient of the filter selects the interpolation filter, which provides the signal with the highest quality.

In addition, the selection block 200 the optimum filter coefficient outputs a coefficient representing the bandwidth of the selected filter interpolation in block 197 filter inter is ASCII frequency, and outputs information indicating the position of the center of the bandwidth of the selected filter in the blocks 196 and 198 adjust the phase.

In addition, the block 200 of the choice of the optimal filter coefficient estimates that there is a variation of the delay, the equivalent bandwidth of the selected interpolation filter, and displays information about it in block 107 synchronization symbol. Block 200 of the choice of the optimal filter coefficient will be described in more detail below.

The processing performed by the block 109 alignment, includes an assessment of the values of H in the expression (1)shown above, using partially known values of X and dividing the value of Y on the evaluation value H to obtain estimates of the unknown transmitted signal X. Using the same symbols as in the expression (1)above, the following expression (3) expresses the aligned signal output unit 109 alignment:

If the value of H estimate exactly matches the actual characteristic H of the transmission channel, then the output unit 109 alignment is expressed by summing the transmitted signal X, which is obtained by dividing the element N of noise on the value of H.

Block 110 error correction performs processing of removing alternation aligned signal coming from block 199 division unit 109 alignment, and also performed the such processing, how to troubleshoot puncturing, the Viterbi decoding, the elimination of the extension signal and decode RS (PC, reed-Solomon). Block 110 error correction outputs in the output buffer 111 decoded data obtained by performing various processing.

The type of processing performed by the block 110 error correction switch in accordance with the information of the transmission parameter and flag the start of a frame transmitted by the block 114, the synchronization frame, shown in figure 4. Block 110 error correction allows you to receive only packets (i.e. the actual packages).

The output buffer 111 inserts ineffective (not transmitted) packets in a predetermined order between effective packets transmitted block 110 error correction, and these packets are passed in are further schemes. Provisions were inserted ineffective packets is determined using information of the transmission parameter transmitted by the block 114, the synchronization frame.

Block 112 of the sample/carrier synchronization, shown in figure 3, detects the sampling error and the error of the carrier, expressed in the magnitude of the rotation phase in the time direction using signals RP and UCPM/VK included in the signal MOCR in the frequency domain, the transmitted block 108 FFT demodulation.

In addition, the block 112 of the sample/carrier synchronization filters detektirovaniya sampling error and Osh is BKU carrier to generate a correction signal sample bias and signal correction signal carrier frequency for the correction. Block 112 of the sample/carrier synchronization outputs the generated correction signals in block 106 alignment.

Unit 113 estimates the number symbol, shown in figure 4, estimates the number of the character at the current received data signal based MOCR in the frequency domain, the received block 108 FFT demodulation.

As noted above, the number of the symbol, the assessment of which was obtained by unit 113 estimates the number symbol is used to highlight signal RP from the period of time beginning demodulation before the end of the synchronization frame (frame transfer MOCR).

Since one frame transmission MOCR consists of 204 symbols MOCR takes time to output the decoded data if the alignment processing may not be initiated until the frame synchronization is completed. For this reason, the evaluation of symbol numbers do unit 113 estimates the number of symbols and the processing of the alignment begins with the use of the estimates of numbers of characters.

In more detail below explains how to obtain estimates of numbers of characters. Unit 113 estimates the number of symbol initially receives the data subcarrier for a given character and then receives the data subcarrier for four characters, following after them.

With regard to each of the initially received data symbol and the subsequent received data symbol unit 113 estimates the Omer character gets the first value of correlation between the data transmitted subcarriers numbered 0, 12, 24, etc. subcarriers.

Similarly, with regard to each of the initially received data symbol and the subsequent received data symbol unit 113 estimates of the numbers of the character receives a second correlation value between the data transmitted by subcarriers having numbers 3, 15, 27, etc. subcarriers.

In addition, with regard to each of the initially received data symbol and the subsequent received data symbol unit 113 estimates the number of character gets the third correlation value between the data transmitted by subcarriers numbered 6, 18, 30, etc. subcarriers.

With regard to each of the initially received data symbol and the subsequent received data symbol unit 113 estimates the number of character then receives a fourth correlation value between the data transmitted by subcarriers numbered 9, 21, 33, etc. subcarriers.

Unit 113 estimates the number of symbol compares the first to fourth correlation values. If the comparison determines that the first correlation value is the largest, then the unit 113 estimates the number of symbol estimates that originally adopted the symbol is 0 symbol and that the next received symbol is 4 characters.

If it is determined that the second correlation value is the largest, then the unit 113 estimates the number symbol is evaluated, that originally adopted the symbol is 1 character and that subsequent received symbol has 5 characters.

If it is found that the third correlation value is the largest, then the unit 113 estimates the number of symbol estimates that originally adopted the symbol is 2 characters and that the next received symbol is 6 characters.

If it is determined that the fourth correlation value is the largest, then the unit 113 estimates the number of symbol estimates that originally adopted the symbol is 3 characters and that subsequent received symbol has the number 7 symbol.

Thus, as explained above with reference to figure 2, the number of characters evaluated, using the fact that the signals RP distributed at intervals of four characters MOOR in the time direction and at intervals of 12 subcarriers in the direction of frequency.

Unit 113 estimates the number of symbol displays in block 109 align the assessment rooms of character, with an accuracy module four (i.e. accuracy, known for the remainder of the division by 4). When perform an assessment of the number symbol, unit 113 estimates the number of symbol displays in block 107 synchronization symbol flag the completion of the evaluation, marking the completion of the assessment rooms character.

Block 114 synchronization frame selects the signal TMS of signal MOCR in the frequency domain transmitted in block 08 FFT demodulation, and detects the byte synchronization to generate a non character. Block 114 synchronization frame displays the generated character number in block 109 alignment.

In addition, when determining that the generated character number reached 204 after detecting the byte synchronization unit 114 synchronization frame determines that the frame synchronization is completed. At this point, the block 114, the synchronization frame displays the synchronization flag of the frame, marking the completion of the synchronization frame, in block 107, the synchronization symbol in the block 109 alignment.

In addition, the block 114, the synchronization frame decodes and outputs information of the transmission parameter attached in units of the transmission frame MOCR, and outputs the flag the start of a frame indicating a starting position of the transmission frame MOCR. Information of the transmission parameter includes the actual data transfer speed and other information. Information of the transmission parameter and flag the start of a frame output unit 114, the synchronization frame, serves to block 110 error correction and the output buffer 111.

Block 115 FFT control performs the FFT and the alignment interval different from the interval, on which we focused FFT, using block 108 FFT demodulation. As an illustration, when performing the FFT and the alignment unit 111 FFT management summarizes the result of the FFT passed nl is com 108 FFT demodulation, with the DFT. The amount generated in such a stacking unit 115 FFT control signal is MOCR in the frequency domain, i.e. it is passed to block 116 to adjust the phase, shown in figure 5. Block 115 FFT control will also be described in more detail below.

Block 116 adjustment phase adjusts the phase of the signal MOCR in the frequency domain, coming from block 115 FFT management, in accordance with the center of the filter, the passed block 200 of the choice of the optimal filter coefficient. Adjustable phase signal MOCR in the frequency domain output block 117 division.

Block 117 division divides the adjusted phase signal MOCR in the frequency domain, obtained from block 116 adjustment phase, the value of the transmission channel, the transmitted block 197 interpolation filter frequency, resulting in correcting distortions in amplitude and phase, the signal MOCR in the frequency domain received in the transmission channel. Block 117 division displays in block 107 synchronization symbol aligned signal made up of signal MOCR in the frequency domain, after the distortion correction.

[The structure and operation unit 107 synchronization character]

Block 107 synchronization symbol, shown in figure 3, is illustrated below. Block 107 synchronization symbol consists of a controller 131 synchronization symbol; blocks 132, 133 and 134 define first, second and third paragraph the provisions of the symbol; switch 135, block 136 generating synchronization flag symbol and block 137 generating control flag DFT. As an illustration, when I turn on the power to the device 100 receiving MOCR or when switching channels, the control unit of a higher level enters the start signal demodulation marks the start of the demodulation, the controller 131 synchronization symbol.

The controller 131 synchronization symbol, in turn, outputs a switching signal to the switch 135. This signal provides the selection switch 135 to any of the provisions of the symbol defined by blocks 132, 133 and 134 define first, second and third positions of the symbol.

As an illustration, when the input signal the beginning of the demodulation controller 131 synchronization symbol connects the first switch 135 to output "a"to select the character position specified by the block 132 to determine the first character position.

Block 136 generating synchronization flag symbol displays in block 108 FFT demodulation flag synchronization symbol, indicating the character position specified by the block 132 to determine a first symbol position. Block 108 FFT demodulation sets the FFT interval with reference to a specific character position.

The method by which determine the position of the character in the block 132 to determine the first position of the SIM is Ola, based on the signal MOCR in the field of time before FFT processing.

In order to perform the FFT block 108 FFT demodulation requires the synchronization flag symbol, with reference to which must be installed FFT interval. Only after the synchronization flag symbol representing the character position specified by the block 132 to determine the first position, is passed to block 108 FFT demodulation, he gets the ability to perform the FFT.

An opportunity to perform FFT means getting the possibility of estimating the number of symbol-based signal MOCR in the frequency domain. This also means that the signals RP can be separated from signal MOCR in the frequency domain based on the assessment of non symbol, resulting in an estimate can be made of the characteristics of the transmission channel.

As described above, when you get the estimate of the number of symbol unit 113 estimates the number of character passes a flag to the end of the evaluation, the controller 131 synchronization symbol. After receiving assessment data characteristics in the time direction, which are characteristic of the transmission channel at intervals of three subcarriers, block 195 evaluation of the transmission channel in the direction of the time it transmits the received data to assess the characteristics in the time direction in the block 133 determine the second character position.

After taking the flag end of the evaluation, describes the surrounding, what was the estimate of the number of a character from unit 113 estimates the number symbol, the controller 131 synchronization symbol next connects the switch 135 to the output "b" to select the character position specified by block 133 determine the second character position.

Block 136 generating synchronization flag symbol displays in block 108 FFT demodulation flag synchronization symbol, indicating the character position specified by block 133 defining the second position of the symbol block 108 FFT demodulation sets the FFT interval with reference to a specific character position.

The method by which the position of the character is determined by block 133 defining the second position of the character based on assessment data characteristics in the time direction, obtained from the signal MOCR in the frequency domain, after it is processed FFT. Only after assessment data characteristics in the time direction will be filed, the position of the character can be defined in this way.

Due to the possibility of obtaining assessment data characteristics in the time direction becomes possible to interpolate estimates of the characteristics in the time direction, in the direction of the frequency and adjust the distortion included in a signal MOCR in the frequency domain, using the characteristic of the transmission channel for all subcarriers.

After the correction of distortion obtained in the transmission channel, block 199 division and unit 117 division shown in figure 5, transmit the aligned signal in block 134 to determine the position of the third symbol.

When the block 114, the synchronization frame receives the synchronization flag frame after frame synchronization, the controller 131 synchronization control character then switches the switch 135 to the output "c" to select the character position specified by the block 134 to determine the position of the third symbol.

Block 136 generating synchronization flag symbol displays in block 108 FFT demodulation flag synchronization symbol, indicating the character position specified by the block 134 to determine the position of the third symbol. Block 108 FFT demodulation sets the FFT interval with reference to a specific character position.

The method by which determine the position of the character, using block 134 to determine the position of the third symbol, based on the aligned signal obtained by correcting the distortion in the transmission channel. Only after the transfer of the aligned signal, therefore, can be specified character position.

The controller 131 synchronization symbol connects the switch 135 to the output "C" to select the character position specified by the block 134 to determine the position of the third symbol. This is the state support until until you enter another start signal demodulation.

In the above description presents as one of three positions of the symbol appropriately select and output: the character position specified by the block 132, the first symbol position, the position of the character defined by block 133 defining the second position of the symbol, and the symbol position determined by the block 134 to determine the third character position.

In the following description the method by which the block 132 to determine the position of the first character determines the character position, will be called the first method of determining the method by which the block 133 defining the second position of the symbol determines the second character position, will be called the second detection method, and the method by which the block 134 to determine a third location of the third character specifies the character position, will be called the third method definition.

The second method of determining includes determining the position, in which the interference between the characters is minimal, as the position of the character, as explained below. Thus, the second detection method provides the best characteristics for reception than the first method definition so that the position of the character is determined on the basis of the signal MOCR in the field of time.

The third is the method of determining includes determining the position, in which quality is actually aligned signal to optimize the position of the character, as explained below. Thus, the third detection method provides the best characteristics for reception than the second determination method, the result of which determines the position of the character based on assessment data characteristics in the time direction.

Under the control of the controller 131 synchronization characteristics symbol of welcome, in principle, be the better, the more time passes from the start of the demodulation. The first through third methods of determination will be described in more detail below.

Block 136 generating synchronization flag symbol displays in block 108 FFT demodulation flag synchronization symbol, denoting the position of the character that is passed via the switch 135.

Based on the symbol position determined by the block 134 to determine the position of the third symbol, block 137 generation flag DFT control generates the flag DFT, indicating the initial position of the interval representing the target processing unit 115 FFT control. Generated thus flag DFT output in block 115 FFT control.

Below, with reference to the block diagram of the sequence of operations shown in Fig.9, the described processing of switching performed by the controller 131 synchronization symbol. This processing starts when injected signal the beginning of demodulation.

At step S1, the controller 131 synchronization symbol connects the switch 135 to output "a" to select the character position specified by the block 132 to determine a first symbol position. The synchronization flag symbol that indicates the character position specified by the block 132 to determine the first position of the character display block 108 FFT demodulation. The FFT block is then set with reference to the initial position, determined in this way.

At step S2, the controller 131 synchronization symbol determines whether the flag is passed to the completion of the evaluation unit 113 estimates the number symbol. If at step S2 it is determined that the flag end of the assessment was not accepted, then the controller 131 synchronization symbol is returned to step S1 and constantly chooses the symbol position determined by the block 132 to determine the first character position.

If at step S2 it is determined that the flag end of the evaluation was adopted, then jumps to step S3. At step S3, the controller 131 synchronization symbol is connected to the switch 135, the output "b"to select the character position specified by block 133 define a second symbol position. The synchronization flag symbol that indicates the character position specified by block 133 defining the second position of the character display block 108 FFT demodulation. The FFT block is then set with reference to began the ing position, determined in this way.

At step S4, the controller 131 synchronization symbol determines whether the flag is passed to the synchronization frame by the block 114, the synchronization frame. If in step S4 it is determined that the synchronization flag frame was not received, then the controller 131 synchronization symbol is returned to step S3 and continuously selects the position of the character defined by block 133 determine the second character position.

If in step S4 it is determined that the synchronization flag frame was adopted, then jumps to step S5. At step S5, the controller 131 synchronization symbol connects the switch 135 to the output "C"to select the character position defined by the block 134 to determine the position of the third symbol. The synchronization flag symbol, denoting the position of the character defined by the block 134 to determine the position of the third symbol display in block 108 FFT demodulation. The FFT block is then set with reference to a specific, thus the initial position.

The above-described processing is performed each time enter the start signal demodulation.

The point in time at which you want to perform an operation with the switch 135 to output the character position specified by the block 134 to determine the position of the third character, not limited to the period prior to the filing of the flag synchronization frame after the end the of the synchronization frame. Alternatively, the period of time that has passed after the start of demodulation, it is possible to count with the timer, and operation switch 135 may then be performed after a relatively long period of time (after the start of demodulation), equivalent to the time required to complete the synchronization of the frame.

[First method definition]

Below is illustrated the first way to determine which unit 132 of the first symbol position determines the position of the character. As shown in figure 3, the block 132 to determine the first position of the symbol consists of section 141 of the correlation of the guard interval and plot 142 detecting the position of the maximum value.

Figure 10 shows a block diagram representing a typical structure of section 141 of the correlation of the guard interval. The signal MOCR in the field of time passed to block 106 correction, introduced in section 141-1 delay duration of the effective symbol section 141-2 multiplication. Section 141-1 delay duration effective character performs a signal delay MOCR in the field of time on the length of the effective symbol, and outputs the delayed signal MOCR in the field of time in the area 141-2 multiplication.

Figure 11 schematically shows typical signals processed by the blocks presented on figure 10. In the case when the and signal MOCR in the field of time will be filed in section 141 of the correlation of the guard interval, as the received signal (a)shown in the upper part of figure 11, section 141-1 delay duration of the effective symbol outputs another signal (b), shown second from the top. In the horizontal direction figure 11 presents the time direction.

Section 141-2 multiplication multiplies the signal MOCR in the field of time, coming from block 106 correction on the signal MOCR in the field of time, who was detained by section 141-1 delay effective duration of the symbol and which is injected at the same time.

When multipath interference and noise do not take into account, the signal ZI (guard interval), one of the signals 1 symbol, identical to the signal interval from which was copied signal ZI. The signal interval from which was copied signal Z. in the input signal MOCR in the field of time has the same distribution of time interval as the signal ZI in the delayed signal MOCR in the field of time. By averaging the results of multiplication of these signals receive interval set to a nonzero value.

The output of the multiplication (C), shown third from the top figure 11 represents the output section 141-2 multiplication. The results of the multiplication, the output section 141-2 multiplication, passed in the plot 141-3 averaging move the guard interval.

On the site 141-3 averaging move the guard interval get the average value is the move for the same length, as the length of ZI, output signals that come from the area 141-2 multiplication, and this section presents the third top figure 11. The average value of displacement, thus obtained, deduce in section 142 of the detection of the maximum position of figure 3. The output section 141-3 averaging move the guard interval is a sequence, the maximum value which occurs at the boundaries of the symbol, as shown in the fourth position from the top figure 11.

Section 142 of the detection of the maximum position detects position in which occurs the maximum value of the sequence, which represents the average value of displacement is transmitted plot 141-1 delay duration of the effective symbol. As shown in the lower part of figure 11, section 142 of the detection of the maximum position then determines the position, the next position of the maximum value over the length of ZI, as the position of the character. Section 142 of the detection of the maximum position then displays the position of the character defined thus, the switch 135.

As described above, the block 132 to determine the first character position determines the position of the character, receiving the average value, given the fact that the signal ZI is identical to the signal interval from which the signal ZI was copied.

Below the belt is Auda reasons for which the first method definitions should be replaced with the second and third detection methods in the appropriate time.

In accordance with the first method of determining the path with the highest power is regarded as the main path, and the position of the character in the main path can then be detected. However, in an environment with multipath propagation, in which the echo signal precedes the main incoming path, the provisions of the preceding echo you want to detect in order to determine the position of the character without IC (interference between characters).

Environment with multipath propagation, in which there is a prior echo explained below with reference to Fig. As an illustration, suppose that there is an environment with multipath propagation, shown as the received signal (a) in the upper part Fig. In this example, the arrival time of the previous echo precedes the time of arrival of the primary path approximately the same period of time, and ZI.

In this environment, the received signal (a) is multiplied by the delayed signal (b), and in the sequence of averages of movement, position, next position of the maximum value GT (SV, protective time interval), is considered as the status symbol. In this case, as in asana at the bottom pig, the FFT interval includes the signal of the character following the target character, and may well be IC.

As described above, in an environment with multipath propagation, in which there is the pre-echo and in which the delay spread is greater than the duration ZI, IC occurs if you use the first method definition. Then you want to detect the position where the IC is minimal, but the first method definition can hardly meet this requirement.

[Second method definition]

Provided below is a second way to determine which unit 133 defining the second position of the symbol determines the position of the character. As shown in figure 3, the block 133 defining the second position of the symbol consists of section 151 OBPF, section 152 valuation IC and section 153 of the search for the minimal provisions.

Section 151 OBPF evaluates the delay profile, performing OBPF according to evaluation of the characteristics in the time direction, which I commend using block 196 adjust the phase, shown in figure 5, and which is characteristic of the transmission channel at intervals of three subcarriers. Thus obtained evaluation of the delay profile is deduced in section 152 valuation IMS.

In this example, evaluation data characteristics in the time direction is administered and processed after the reg is formulated phase. However, such processing equivalent to processing, which includes data before adjusting the phase.

Section 152 valuation IC evaluates the value of the IC by filtering the delay profile estimated by the section 151 OBPF, and outputs the value assessment of IC in section 153 of finding the minimum position. The shape of the filter used for filtering determine, using the information on the variation of the delay, the transmitted block 200 of selecting the optimal coefficient of the filter shown in figure 5.

Section 153 of the search for the minimal provisions detects, as the position of the character, the position at which the value of IC, the resulting filtering, minimum, and outputs the position of the character, detektirovanie so.

Next will be described how the plot 152 evaluation of the IC evaluates the IC. On Fig shows a diagram illustrating how usually perform an assessment of the value of IC.

Here it is assumed that there are three paths P1, P2 and P3, as shown in Fig. Horizontal direction on Fig indicates the direction of time. In the upper part Fig width of each of the bands representing the way, is the power given path.

At the bottom Fig shows the delay profile estimated by the section 151 OBPF. Lots PP1-R presented to indicate power levels of the paths P1-P3. The capacity of each of the paths also determine the use of the delay profile.

When this interval is set as the FFT interval, the value of IC is obtained by multiplying the length in the direction of the time interval, which is the IC on the power and the way in which occurs the IC, and by summing the results of multiplying all the way.

For example, if the FFT interval, such as shown in Fig, then the IC occurs between the path P2 and by P3. The value of IC is expressed as dt2×PP2+dt3×RR where dt2 denotes the length in the direction of the time interval of the path P2, which is the IC, and dt3 is the length in the direction of the time interval of the path P3, where occurs the IC. Section 152 valuation IMS performs processing filter to achieve the same result as in the above calculations.

On Fig shows a diagram representing a typical filter estimates the IC used to estimate the IC. On Fig, the vertical axis represents the filter coefficients (gain), and the horizontal axis indicated the degree measure of branches.

The filter FI IC process evaluation Fig formed so that the gain is equal to zero on the interval indicator branches whose length corresponds to the length of ZI. It is also possible to make the length of the interval, where the gain is equal to zero, corresponding to the length of delay spread, transmit unit 200 optimal choice from the cylinder is enta filter.

In addition, the filter FI evaluation Eames molded in such a way that the gain is increased in the interval, following the provisions of f1 at the rear end of the interval with zero gain and proportional to the distance from this position f1, and that the gain also increases in the interval before the position f2 on the front end of the interval with zero gain and proportional to the distance from this position f2. The gradient of the straight line defining the gain of the interval following the provisions of f1, can be arbitrary, and therefore may represent a gradient of a straight line that defines the gain of the interval before the next position f2.

On Fig shows a diagram representing the profile of delay Fig and filter FI evaluation IC on Fig superimposed on each other. As shown in Fig when the interval is set as a candidate for the FFT interval, the filter FI evaluation IC is positioned so that the initial position of the FFT interval coincides with the position f2 of the front end of the interval with zero gain.

In this case, the path P1 is within the interval with zero gain, so the power PP1 path P1 is multiplied by zero. Path P2 is sequentially after the position f1 of the rear end of the interval with nuevascarreras.com gain therefore, the power PP2 path P2 is multiplied by the predetermined gain DT2. The path P3 is also located after the position f1, so the power RR path P3 is multiplied by the gain DT3, which is greater than the gain DT2.

Section 152 valuation IMS summarizes the results of multiplication to obtain estimates of the magnitude of the IC. The operations section 152 assessment of IC, such as a filtering process, is defined by following expression (4):

where NN denotes the sample size of all the data located after ABPF (i.e. the number of points OBPF).

Section 152 valuation IMS performs the filtering processing described above, many times by shifting the position of the candidate interval FFT on the desired width (that is, by shifting the position of the filter FI evaluation IC on the desired width).

On figa, 16B and 16C shows a diagram representing typical processing results filtering. The results shown figa-16C, when the filtering processing is performed by shifting the position (time) of the candidate interval FFT from left to right, for example, from time t1 to time tN.

When the candidate interval FFT set in such a way as to make the time t1 its initial position, the path p1 is defined in the interval with zero gain, as shown in the upper part figa. M is mnost PP1 path P1 can then be multiplied by zero.

The path P2 have consistently after position f1 of the rear end of the interval with zero gain, so that the power PP2 path P2 is multiplied by the gain DT2a. The path P3 is also located after the position f1, so the power RR path P3 is multiplied by a coefficient DT3a gain that is greater than the coefficient DT2a gain.

The graph at the bottom figa represents the estimate of the IC as the sum of the results described above multiplications. On figa, the horizontal axis is indicated by an initial position of the candidate interval FFT, and the vertical axis represents the estimated value of IC. In the example shown in figa, to estimate the IC receive the value of D1.

Similarly, when the candidate of the FFT interval set in such a way as to make time tk its initial position, the paths P1 and P2 define the interval with zero gain, as shown in the upper part on Fig Century Power PP1 path P1 and the power PP2 path P2 can then be multiplied by zero.

The path p3 is located after the position f1 of the rear end of the interval with zero gain, so the power RR path P3 is multiplied by a coefficient DT3b gain. In the example shown in figv, to estimate the IC receive the value of Dk, as shown in the graph in the lower part in the drawing.

When the candidate interval FFT set so to make the time tN its initial position, the path P1 is located before the position t2 of the front end of the interval with zero gain, as shown in the upper part figs. Power PP1 path P1 can then be multiplied by a factor of DT1c gain.

In addition, the path P2 is located before the position f2 of the front end of the interval with zero gain. Power PP2 path P2 can then be multiplied by a factor of DT2c gain that is smaller than the coefficient DT1c gain.

The path P3 is placed in the interval with zero gain, so the power RR path P3 is multiplied by zero. In the example shown in figs, to estimate the IC receive the value of DN, as shown in the graph in the lower part in the drawing.

Section 152 valuation IMS sends in section 153 of the search for the minimal position information indicating the correlation between the estimated values of IC, on the one hand, and the initial provisions of the candidate interval FFT, on the other hand, with these values and conditions are a result of processing filter, in which all the specified position is used as the start position candidates of the FFT interval.

Next explains how detects the position of the character with section 153 of finding the minimum position. On figa, 17B and 17C schematically shows views illustrating the AK detects the position of the characters. On figa shows the delay profile, and figv graphically marked interdependence between estimated values of IC and the initial positions of the candidates of the FFT interval.

When the interdependence between the estimated value IC and the initial positions of the candidates interval FFT receive, as shown in figv, section 153 of the search for the minimal position detects the position indicated by shaded triangle pointing up, as the situation in which the estimation of the IC minimum. The position where the evaluation value of the minimum IC, defined as the start position of the FFT interval, that is, as the position of the character.

On figs shows a case where the FFT interval is set with the position of the character on FIGU, which is considered as the initial position of the frame. As shown in figs, IC occurs only on the path P3. Since the capacity of the path P3 is lower than in all other ways, the value of IC becomes smaller than if the FFT interval was located, as shown in Fig.

In accordance with the second detection method, as described above, the position where the value of the IC minimum, determine how the position of the character.

The following describes the reasons why the third way definitions are used instead of the second detection method. As an illustration, can lead to cases in which b is lsoe number of ways, in which power is too low for detection using OBPF. In such cases, the symbol position determined by the second determination method, in fact, may not be an optimal situation. IC, arising together with paths, the capacity of which is too small to detect using OBPF, do not take into account the second method definition.

In this case, use the third method definitions. The third way to determine is a method by which to determine the optimal position, as the position of the character, even if there are many ways in which power is too low for detection using OBPF.

[The third way of definition]

Below is illustrated a third way to determine which block 134 to determine the position of the third character specifies the character position. Based on the symbol position determined by the block 134 to determine the position of the third symbol, set the interval to which the target processing unit 115 FFT management, and aligned with the receive signal accordingly. The aligned signal serves back to block 134 to determine the position of the third symbol, which then determines the position of the character.

Before the description of the block 134 to determine the position of the third character will be given an explanation of b is an eye 115 FFT control. Block 115 FFT management processes target interval with a shift on the S samples (time) relative to the interval on which we focused FFT performed by the block 108 FFT demodulation. Flag DFT output unit 137 generation flag DFT represents the initial position of the target interval.

The execution result of the DFT block 115 FFT management receives information indicating the difference between the FFT performed by the block 108 FFT demodulation. The sum information of the difference output unit 108 FFT demodulation enable signal generating MOCR in the frequency domain, which will be obtained if the FFT will be performed in the interval established with the shift of the S samples.

Thus, when the target area is selected with the shift of the S samples, the block 115 FFT control performs processing equivalent to the processing that is performed by a block 108 FFT demodulation.

The interval on which we focused processing performed by the block 108 FFT demodulation, can be called the interval FFT demodulation, and the interval on which we focused processing unit 115 FFT control, you can call the FFT interval control, as appropriate, in the following description. When the operation unit 115 FFT management, represents the DFT, the output unit 115 FFT control equivalent to the output unit 108 FFT demodulation, therefore, the interval on which we focused processing performed by block 115 FFT control, is called the FFT interval control.

The fact that the processing performed by block 115 FFT control, is equivalent to the processing performed by the block 108 FFT demodulation, explained below, using mathematical expressions.

It is assumed that the start time of the interval FFT demodulation is zero and that the length of the interval FFT demodulation and FFT interval control represents the length N of the effective symbol. The following expression (5) defines the signal Y0(ω) at frequency ω obtained by performing FFT on the signal MOCR in the field of time, length N, selected from the interval FFT demodulation:

where r(k) denotes the signal MOCR in the field of time at time "k"and "j" is the imaginary unit quantitative measurements.

As shown in Fig, assume that the start time of the interval FFT demodulation is after the start time of the FFT interval control time "s". In this case, the signal MOCR in the field of time, within the FFT interval control is defined as r(s)r(s+1), ..., r(N-1+s). The following expression (6) defines the signal YS(ω)obtained by performing the FFT in the FFT interval control:

As shown in Fig, assume that the start time of the interval FFT demodulation is before the start time of the FFT interval control time "s". In this case, the signal MOCR in the field of time, within the FFT interval control is defined as r(-s), r(-s+1), ..., r(-), r(0), r(1) ...r(N-1-s). The following expression (7) defines the signal Y-S(ω)obtained by performing the FFT in the FFT interval control:

The first term in expressions (6) and (7), shown above, is the result of the FFT aimed at interval FFT demodulation. The output of block 108 FFT demodulation can be used without modification as the value of the first member in expressions (6) and (7).

The second term in expressions (6) and (7)above shows the result of the DFT aimed at signal MOCR during the "s". Block 115 FFT management performs operations to obtain the value of the second term in expression (6) or (7)shown above, and summarizes the results of operations from the output unit 108 FFT demodulation.

As shown in figure 4, the block 115 FFT management consists of the controller 171 FFT control arithmetic unit 172, block 173 selection, storage device 174, the arithmetic unit 175 DFT, storage devices 176 and block 177 summation.

Flag DFT output unit 137 generation flag DFT control, injected into the controller 171 FFT control. The signal MOCR in the field of time, the output unit 106 correction, enter in the arithmetic unit 172, and in block 173 of choice. The signal MOCR in the region of frequencies, the output of block 108 FFT demodulation, enter in block 177 summation.

The controller 171 FFT management manages the entire unit 115 FFT control during the execution of its operations, therefore, as established by the FFT interval control based on the flag of the DFT, and to generate the FFT performed on the interval set with the shift S of the samples relative to the interval FFT demodulation.

Using the offset value set by the block 107 synchronization symbol, the controller 171 FFT control selectively determines whether there is the start time of the FFT interval control after start time interval FFT demodulation (i.e. must be completed operation in accordance with the expression (6)), or earlier than the start time (i.e. must be completed operation in accordance with the expression (7)).

The arithmetic unit 172 subtracts the signal contained in the storage device 174, the signal MOCR in the field of time, lodged by block 106 correction. Received, the signal thus output in block 173 selection.

Under the control of the controller 171 FFT control block 173 selection selects either the signal MOCR in the field of time passed to block 106 correction, or a signal arithmetic unit 172. The signal selected store in the storage device 174.

As an illustration, if BP is me beginning of the FFT interval control should later than the start time of the interval FFT demodulation, as shown in Fig, block 173 select selects the signal MOCR in the field of time, coming from block 106 correction, when an input signal occurs during the interval A. When the input signal occurs during the time interval that follows after the interval A on the length N of the effective symbol, block 173 select selects the signal from the arithmetic unit 172 as a result of the subtraction.

Similarly, if the start time of the FFT interval control should be earlier than the start time of the interval FFT demodulation, as shown in Fig, block 173 select selects the signal MOCR in the field of time, coming from block 106 correction, when an input signal occurs during the interval A. When the input signal occurs during the time interval that follows after the interval And through the length N of the effective symbol, block 173 select selects the signal from the arithmetic unit 172 as a result of the subtraction.

Under the control of the controller 171 FFT control storage device 174 stores the signal from the block 173 of choice. When the signal on the interval B shown in Fig and 19, it will be saved in the storage device 174, the stored signal is selected via the arithmetic unit 175 DFT.

If the start time of the FFT interval control should be later than the start time of the interval of the FFT demodu is acii, the arithmetic unit 175 performs DFT operation on the second term in the expression (6) on the basis of a signal selected from the storage device 174. The result of the operation output in the storage device 176. The controller 171 FFT control transmits information representing 2πk ω/N in the expression (6), in the arithmetic unit 175 DFT.

If the start time of the FFT interval control should be earlier than the start time of the interval FFT demodulation, the arithmetic unit 175 DFT performs operations in accordance with the second member of the expression (7) on the basis of a signal selected from the storage device 174. The result of this operation to display in the storage device 176. The controller 171 FFT control transmits information representing 2πk ω/N in the expression (7), in the arithmetic unit 175 DFT.

Under the control of the controller 171 FFT management in a storage device 176 save the operation result received from the arithmetic unit 17 DPF. When the arithmetic unit 175 performs DFT operation on the second term in the expression (6) or (7), the value stored in the storage device 176, get with the help of block 177 summation.

Block 177 summation sums the value obtained from the storage device 176, the signal MOCR in the frequency domain, the output unit 108 FFT demodulation. The amount resulting from the summation, then take the help of block 177 summation.

The output of block 177 summation represents the signal MOCR in the frequency domain obtained by performing FFT on the interval set with the shift on the YSin the expression (6) or Y-S(ω) in the expression (7), i.e. the value of "s" on the interval FFT demodulation.

The signal MOCR in the frequency domain, the output of block 177 summation, adjust the phase using block 116 regulation phase, shown in figure 5, before serving in the block 117 division. Block 117 division corrects the distortion of the transmission channel signal with the same characteristics of the transmission channel, which uses the block 199 division, and outputs the smoothed signal. The aligned signal output unit 117 division, serves to block 134 to determine the position of the third symbol, shown in figure 3, together with aligned signal output unit 199 division.

The aligned signal generated by the block 199 division will be aligned signal demodulation, and aligned with the signal generated by the block 117 division will be aligned with the control signal, as appropriate, in the following description.

Block 134 to determine the position of the third symbol will be described below. As shown in figure 3, the block 134 to determine the position of the third symbol consists of section 161 of the calculation of signal quality and a controller 162 search. The aligned signal demo is ulali, coming from a block 199 division, and aligned with the control signal from block 117 division introduced in section 161 of the calculation of signal quality. Each of the aligned signal demodulation and leveled control signal is a smoothed signal relating to the same symbol.

Section 161 of the calculation of signal quality counts quality aligned signal demodulation, as well as the quality of the aligned control signal and outputs information indicating the calculated quality value, the controller 162 of the search.

On Fig shows a block diagram representing a typical structure of section 161 of the calculation of signal quality. The aligned signal demodulation or aligned control signal is divided into component I component and Q before entering. The signal component I is administered in part 401 tough decisions and in part 403 subtraction; the signal component Q is introduced into the portion 402 tough decisions and in part 404 of the subtraction.

Part 401 hard decision hard decision on the input signal component I in accordance with the current modulation method. The result of the hard decision output in part 403 of the subtraction.

Part 402 hard decision hard decision for the input signal component Q in accordance with the current modulation method. The result of the hard decision output in part 404 of the subtraction.

Part 403 wichitan who gets the value of the difference between the output part 401 tough decisions and the power input component I. The resulting difference output in part 405 of the square.

Part 404 subtracting receives the difference between the output part 402 tough decisions and the power input component Q. thus Obtained difference derive in part 406 of the square.

Part 405 square receives the squared difference supplied part 403 subtraction. The calculation result display part 407 summation.

Part 406 square receives the squared difference supplied part 404 subtraction. The calculation result display part 407 summation.

Part 407 summation sums the outputs of part 405 of the square and part 406 of the square. The amount obtained by totaling, derive in part 408 of the summation.

Part 408 summation sums the output portion 407 of the summation and the value contained in the register 409. Unit 480 performs the summation operation of summing this number of times as the specified number of data, and outputs the accumulated result in the register 409. The accumulated result of the transactions related to the specified amount of data placed in the register 409 and transmits it in the controller 162 of the search shown in figure 3, as the information representing the quality of the aligned signal.

The controller 162 search compares the quality of the aligned signal demodulation output section 161 of the calculation of signal quality, with the quality of the aligned signal control the deposits. If it is determined that the quality of the aligned control signal is higher than the quality of the aligned signal demodulation, the controller 162 of the search displays the position of the character that indicates the start position of the current FFT interval control, so that the same interval as the current FFT interval control, will be installed as the next interval FFT demodulation.

Thus, if a signal with a higher quality is obtained when targeting the FFT interval control, instead of the interval FFT demodulation, then block 108 FFT demodulation performs FFT on this interval to obtain a signal with higher quality in the next time interval.

In addition, the controller 162 sets the search position obtained by shifting the initial position of the current FFT interval control on the desired width, as the initial position of the next FFT interval control, and outputs information indicating the specified position in the block 137 generating control flag DFT. To illustrate the position set with the shift in the direction opposite to the previous direction of the shift can be set as the initial position of the next FFT interval control.

On the other hand, if determined that the quality of the aligned signal demodulation higher than the quality in ravninnoe control signal, then, the controller 162 of the search displays the position of the character denoting the initial position of the current interval FFT demodulation, so that the same interval as the current interval FFT demodulation, will be installed as the next interval FFT demodulation. Thus, if a signal of high quality can be obtained, when the stored targeting interval FFT demodulation, then this state is stored.

The controller 162 of the search box, and then sets the position obtained by shifting the initial position of the current FFT interval control on the desired width, as the initial position of the next FFT interval control, and outputs information indicating the set position, in block 137 generation flag DFT control. To illustrate the position set with the shift in the same direction as the previous direction of the shift can be set as the initial position of the next FFT interval control.

When the symbol position determined as described above, on the basis of quality really aligned signal, it becomes possible to provide a higher performance device than if you were using the position of the character defined in accordance with the first or second method definition.

[The choice of the optimal filter coefficient]

Block 200 vibropiling coefficient filter will be described below. However, before this description the following is an explanation of the interpolation filter designed for use in block 197 interpolation filter frequency.

If we denote as Tu the length of the effective symbol, i.e. the length of the interval of a single minus symbol ZI, then the interpolation filter as an illustration, can be performed with a bandwidth of approximately Tu/3 (seconds) or less. Such an interpolation filter is used to suppress duplicate the components included in these estimates characteristics in the time direction, generated by the block 195 evaluation of the transmission channel in the time direction, resulting allocate the appropriate path representing the characteristic of the transmission channel.

Below are the reasons why estimates of the characteristics in the time direction contain duplicate components. Assessment data characteristics in the time direction is obtained from the signal MOCR in the frequency domain and, thus, represent the data in the frequency domain.

As described above, block 197 interpolation filter frequency generates estimates of the characteristics in the time direction, in which the number of data triples, as an illustration, by interpolating the two zeros. Assessment data characteristics in the time direction in the field of time and data characteristics in which echolalia with a null value in the field of time have the same frequency components.

In addition, estimates of the characteristics in the time direction comprise a sequence selected values indicating the characteristics of the transmission channel, at intervals of three subcarriers. If the length of the effective symbol is represented as Tu (seconds) and the interval from subcarrier to subcarrier Fc (Hz), then the true expression of Fc=1/Tu (Hz). The expression 3Fc=3/Tu (Hz) defines the interval between sample values in the data evaluation characteristics in the time direction, comprising the sequence of sample values representing the characteristics of the transmission channel at intervals of three subcarriers.

Thus, the expression Fc=1/Tu (Hz) defines the interval between sample values of the data characteristics of the interpolation zero values obtained by interpolating the two zeros between the values of the sampling data evaluation characteristics in the time direction.

At the same time, estimates of the characteristics in the time direction, for which the interval between sample values is defined as 3Fc=3/Tu (Hz)represent the data, the cycle which is defined as 1/3Fc=Tu/3 (seconds) in the field of time. These characteristics interpolation to zero, the interval between which the sample values are defined as Fc=1/Tu (Hz)represents the data with a cycle defined as 1/Fc=Tu (seconds) in the field of time, i.e. three rosabelle cycle assessment data characteristics in the time direction.

As described above, when data interpolation null values in the field of time have the same frequency components as the evaluation data and characteristics in the time direction, in the field of time, and the cycle is defined as three times greater than the cycle data assessment characteristics in the time direction, these characteristics interpolation null values in the field of time is converted into data, which is formed by three-fold repetition of assessment data characteristics in the field of time in the time direction.

On Fig shows a schematic view representing a typical data characteristics interpolation null values in the field of time. This is an example of two ways: the main route and the previous echo. On Fig on the horizontal axis shows time and the vertical axis indicated the power levels of the path.

These characteristics of the interpolation values of zero, the loop is designated as Tu (seconds), consider how the data generated by the threefold repetition of multipath propagation, the corresponding data assessment characteristics in the time direction, the cycle which is defined as Tu/3 (seconds) in the field of time.

On Fig, if the signals are multipath propagation, shown shaded in the centre, to highlight how these interpolate the characteristics in the direction of the frequency, then other data multipath propagation want to delete, in order to receive the appropriate signals multipath propagation, which corresponds to the interpolation characteristics in the direction of frequency.

Thus, block 197 interpolation filter frequency filters the data characteristics of the interpolation values of zero, to eliminate signals of multipath propagation, except the signal is multipath propagation. Selected, thus, the signals of multipath propagation correspond to the interpolation characteristics in the direction of frequency.

These characteristics interpolation with zero value represent data in frequency. Data filtering characteristics of the interpolation values of zero with unit 197 interpolation filter frequency includes a convolution coefficient filter to filter the interpolation data characteristics interpolation zero values, which represent data in frequency.

Convolution in frequency includes multiplication by a window function in the field of time. Thus, data filtering characteristics of the interpolation values of zero may be expressed as a multiplication in the time portion of the data characteristics of the interpolation values of zero to fu is the Ktsia window, corresponding to the bandwidth of the block 197 interpolation filter frequency. Window function, indicated by the thick lines on Fig, is a function that is used in the multiplication performed as data filtering characteristics of the interpolation values of zero and which corresponds to the bandwidth of the block 197 interpolation filter frequency.

Cycle signal multipath propagation, repeated three times, denoted as Tu/3 (seconds). Thus, if the interpolation filter is provided in the form of a low-pass filter and its bandwidth will be of the same width as in the cycle of Tu/3 (seconds) signal multipath propagation, repeat three times, i.e. from-Tu/6 to +Tu/6, then can be allocated corresponding signals multipath propagation, which corresponds to the interpolation characteristics in the direction of frequency.

As described above, block 197 interpolation filter frequency uses the interpolation filter to highlight the corresponding signals of multipath propagation. The width and the center position of the passband of the interpolation filter govern in such a way as to include all relevant signals multipath propagation and to components, such as white noise, in addition to existing routes, to minimize the bandwidth limits./p>

Block 200 of the choice of the optimal filter coefficient will be described below. As shown in figure 5, the block 200 of the choice of the optimal filter coefficient consists of a controller 211 Central filter/bandwidth, storage devices 212 and 213 section 214 of the distortion correction of the transmission channel, section 215 interpolation frequency plot 216 calculate signal quality and section 217 of choosing the optimal value. The signal MOCR in the frequency domain, the output unit 108 FFT demodulation, is introduced into the storage device 212. Assessment data characteristics in the time direction, the output of block 195 evaluation of the transmission channel in the time direction, is introduced into the storage device 213.

The controller 211 of the center of the filter/band controls the write and read into the storage device 212 and 213 of them so that you save and retrieve data of the same symbol.

The controller 211 of the center of the filter/band displays a coefficient representing the bandwidth of the filter test interpolation (i.e. test strips) in section 215 interpolation frequency and plot 217 choosing the optimal value.

In addition, the controller 211 of the center of the filter/band displays a coefficient representing the position of the center of the filter bandwidth test interpolation (i.e. the test centre)in section 214 of the correction of the distortion of the transmission channel, section 215 is interpolatio frequency and section 217 of choosing the optimal value.

In the storage device 212 contains one symbol corresponding to the signal MOCR in the frequency domain, the transmitted block 108 FFT demodulation, under the control of the controller 211 of the center of the filter/band. The signal MOCR in the range of frequencies contained in the storage device 212 corresponding to one symbol is received with the help of section 214 of the correction of the distortion of the transmission channel.

Under the control of the controller 211 of the center of the filter/band in a storage device 213 contain one character corresponding to the data evaluation characteristics in the time direction, which is assessed through a block 195 evaluation of the transmission channel in the direction of time, as data representing a characteristic of the transmission intervals of three subcarriers. Assessment data characteristics in the time direction contained in the storage device 213, corresponding to one character is extracted using section 215 of the interpolation frequency.

Section 214 of the correction of the distortion of the transmission channel consists of part 231 adjust the phase and part 232 division. Part 231 adjust phase adjust one character corresponding to the signal MOCR in the frequency domain obtained from the storage device 212 in accordance with the test center transmitted by the controller 211 of the center of the filter/band, and outputs the regulated signal MOCR in the frequency domain in part 232 of the division.

In SL the tea, when the signal MOCR in the frequency domain is subjected to the phase adjustment in accordance with the test center, what's happening here, therefore, perform processing equivalent to the adjustment of the position of the center of the passband of the interpolation filter.

Every time characteristic of the transmission channel is passed through section 215 of the interpolation frequency part 232 division corrects the distortion of the transmission channel, contained in the signal MOCR in the frequency region corresponding to one character. Section 214 of the distortion correction of the transmission channel outputs in section 216 of the calculation of signal quality signal MOCR in the frequency domain, free from distortion.

Section 215 interpolation frequency consists of 241 adjust the phase and part 242 interpolation frequency. Part 241 adjust the phase adjusts the phase data evaluation characteristics in the time direction, obtained from the storage device in accordance with the test center transmitted by the controller 211 of the center of the filter/band. Assessment data characteristics in the time direction after the adjustment phase display part 242 interpolation frequency.

Part 242 interpolation frequency selects with increasing frequency sampling value of sampling data evaluation characteristics in the time direction with a factor of three. Part 242 interpolation frequency goes to execution of the processing is the interpolation frequency, using an interpolation filter with a width of its bandwidth, which is regulated in accordance with the sample rate passed by the controller 211 of the center of the filter/band.

As a result of processing the interpolation frequency part 242 interpolation frequency receives the transfer characteristic of all subcarriers. The characteristic of transmission received thus derive in part 232 dividing section 214 of the distortion correction of the transmission channel.

Section 216 of the calculation of signal quality calculates the signal quality MOCR in the frequency region corresponding to one symbol, each time a signal is available from the help section 214 of the distortion correction of the transmission channel. Thus, calculated as output per section 217 of choosing the optimal value as the test result. As an illustration, section 216 of the calculation of signal quality calculates the power of noise included in the signal MOCR in the frequency domain, and outputs the calculated value. Section 217 of the optimum values are selected sequentially stores the value calculated by section 216 of the calculation of signal quality. Section 217 of choosing the optimal value continuously receives the calculated values of quality, while the width and the center position of the passband of the interpolation filter will not change for testing on all structures and complete inspections.

The village is E. the results of inspections of structures section 217 of choosing the optimal value selects the interpolation filter, used to generate signal MOCR in frequency with the highest quality, and identifies the width and the center position of the passband of the selected interpolation filter.

As for the signal MOCR in the frequency domain, consisting of a single character that is a target for processing, section 217 of choosing the optimal value, thus determines the interpolation filter having a certain width, its bandwidth, and the specific position, as the position of the center of its passband, upon receipt of the signal with the highest quality.

Section 217 of choosing the optimal value displays in block 197 interpolation filter frequency coefficient representing the bandwidth of the selected filter interpolation. In addition, section 217 of choosing the optimal value displays the coefficient denoting the position of the center of the bandwidth of the selected filter interpolation in blocks 196 and 198 adjust the phase and in block 116 adjustment phase.

In addition, section 217 of choosing the optimal value considering the width the same as the bandwidth of the selected filter interpolation, as representing the variation of the delay, and outputs information indicating the variation of the delay unit 133 defining the second position of the character shown in figure 3.

In block 200 of choice opt the maximum coefficient of the filter, as described above, the signals in other ways, in addition to the main path, obtained from block 195 evaluation of the transmission channel in the time direction and transmitted in block 196 adjustment phase, you can use when attempting to process the interpolation frequency in accordance with the set of conditions under which change the width and the center position of the passband of the interpolation filter.

Thus, it becomes possible to select an interpolation filter, which allows to obtain a smoothed signal with the highest quality. When using a certain width and the position of the center of the bandwidth of the selected interpolation filter, the same filter interpolation, as the selected filter can be used to perform interpolation processing frequency for the signal of the main path.

The sequence of steps and processes described above may be performed using hardware or using software tools. When you want to perform processing on the basis of software, programs composing the software can be either pre-built into dedicated hardware, such as a computer, or may be set during the use of the respective medium recording the program in a personal computer utility sludge is similar to the equipment to run the program.

On Fig shows a block diagram representing a typical structure of hardware of the computer used to run programs which process the above-described steps and processes. On Fig CPU (CPU, Central processing unit) 501, a ROM, a persistent storage device 502, and the RAM (RAM, random access memory) 503 mutually connected by a bus 504.

Interface 505 input/output is also connected to the bus 504. Interface 505 input/output data is connected to the block 506 and input unit 507 output. Block 506 input typically consists of a keyboard and mouse, and block 507 output formed as an illustration of the display and speakers. Also to the bus 504 is connected block 508 drive, unit 509 data and actuator 510, which drives the removable media 511 information. Block 508 drive typically consists of a hard disk and/or non-volatile memory device, and block 509 data consists of network interface.

In the computer having the above-described structure, the CPU 501 loads the program as an illustration of block 508 the drive into the RAM 503 via the interface 505 input/output data and the bus 504 for program execution, carrying out, therefore, the above sequence of steps and processes.

Programs intended for execution by the CPU 501, as is illustratie can be transmitted in written form on a removable medium 511 information or can be provided through a cable or wireless transmission medium data such as a local area network, the Internet or other channels of digital broadcast, prior to installation in block 508 of the drive.

In addition, the program for executing with a computer can be processed in this description of the sequence (i.e. on the basis of time sequence), parallel or otherwise, in the appropriate time sequence, for example, in accordance with their call.

It should be noted that a variant of the embodiment of the present invention is not limited to the above-described variant embodiments, but various modifications can be embedded into it without going beyond the scope and essence of the present invention.

The present application contains subject matter related to those described in the priority application, Japanese patent JP 2008-253299, filed in the Japanese patent office on 30 September 2008, the full content of which is cited here as reference material.

1. The pickup device, comprising:
the means of determining the first position, designed to calculate correlation values between the signal, multiplexed with orthogonal frequency division in the field of time, the components of the signal, multiplexed with orthogonal frequency division in the field of time, imagine what they symbol multiplexing orthogonal frequency division, on the one hand, and a signal obtained by delaying the above-mentioned signal, multiplexed with orthogonal frequency division in the field of time, the length of the effective symbol, on the other hand, to determine the initial position of the interval of the fast Fourier transform, which is referred to the length of the effective symbol and which is used as an interval signal representing a target of the fast Fourier transform performed by using the fast Fourier transform, with reference to most of these correlations;
the means of determining the second position, designed to assess the characteristics of the transmission channel is known signal included in the first signal, multiplexed with orthogonal frequency division in the frequency domain comprising signal, multiplexed with orthogonal frequency division in the frequency domain obtained by performing a fast Fourier transform to this signal, multiplexed with orthogonal frequency division in the field of time before interpolation estimate characteristics of the transmission channel in the time direction to obtain assessment data characteristics of the transmission channel, before performing the inverse fast Fourier transform, for the said assessment data characterized the Tiki transmission channel, to assess the profile of delay before measurement of the interference between symbols in relation to each of the set of candidates mentioned interval of the fast Fourier transform, on the basis of the delay profile before you can determine the initial position of the candidate mentioned interval of the fast Fourier transform with the least amount of interference between symbols in the initial position of the above-mentioned interval of the fast Fourier transform, which represents a goal for the fast Fourier transform performed by the mentioned means of fast Fourier transform;
means defining a third position that is designed to set a different interval of the fast Fourier transform in the position established with a relative shift to the mentioned interval of the fast Fourier transform used to generate the first mentioned signal, multiplexed with orthogonal frequency division in the frequency domain, prior to performing the fast Fourier transform to this signal, multiplexed with orthogonal frequency division in the field of time within this mentioned in another interval of the fast Fourier transform, to generate a second signal, multiplexed with orthogonal frequency section is observed in the frequency domain, before removing distortions from the mentioned first and second signals, multiplexed with orthogonal frequency division frequency in the frequency domain, using the characteristics of the transmission channel of each of all subcarriers obtained by interpolation of such data to assess the characteristics of the transmission channel in the direction of the frequency, to generate an aligned signal before detecting the initial position of the above-mentioned interval of the fast Fourier transform, which represents a goal for the fast Fourier transform performed by the mentioned means of the fast Fourier transform, on the basis of the quality of the generated aligned signals;
the selector is designed to select one of the primary provisions of the interval of the fast Fourier transform, which is defined by the mentioned means defining first, second and third positions; and
the above-mentioned means of the fast Fourier transform that is designed to perform fast Fourier transform to this signal, multiplexed with orthogonal frequency division in the field of time, by using the initial position selected by the mentioned tool of choice in the initial position of the above-mentioned interval of the fast Fourier transform, to generate cited Otago first signal, multiplexed orthogonal frequency division in the frequency domain.

2. The pickup device according to claim 1, additionally containing an assessment tool designed to assess the numbers of the received data symbol based on the said first signal, multiplexed with orthogonal frequency division in the frequency domain;
in which the said selector selects this initial position of the above-mentioned interval of the fast Fourier transform, which is defined by the mentioned means of determining the first position, mark the beginning of demodulation, and the said picker additionally chooses the initial position of the above-mentioned interval of the fast Fourier transform, which are selected via the means of determining the second position instead of the initial position selected by the said means of determining the first position, after completing the assessment, the number of the character mentioned by means of evaluation.

3. The pickup device according to claim 2, additionally containing synchronization tool frame designed for the synchronization of the transmission frame by multiplexing orthogonal frequency division consisting of a set of symbols multiplexed with orthogonal frequency division on the basis of the said first signal, the multiplex is one of orthogonal frequency division in the frequency domain;
in which, when the said frame transmission, the multiplexed orthogonal frequency division synchronize using the synchronization tool of the frame, the said selector chooses the initial position of the above-mentioned interval of the fast Fourier transform, which is determined using the means defining the third position, instead of the initial position defined by the said means of determining the second position.

4. The pickup device according to claim 1 in which the said means of determining the first position determines the position set with the shift from most of these correlations on the length of the guard interval as the initial position of the above-mentioned interval of the fast Fourier transform, which represents a goal for the fast Fourier transform performed by the mentioned means of fast Fourier transform.

5. The pickup device according to claim 1 in which the said means of determining the second position performs the estimation of the amount of interference between symbols in relation to each of the multiple paths, multipath components, by multiplying the length in the time direction, on which there is interference with another character, when you are referred to the candidates mentioned interval b is strictly Fourier transform, on the capacity of the path, which provides an interference referred to another character, and by summing the results of the products obtained for each of these ways.

6. The pickup device according to claim 1 in which the said means for determining a third location determines the initial position of the above-mentioned interval of the fast Fourier transform used to generate the first mentioned signal, multiplexed with orthogonal frequency division in the frequency domain, as the initial position of the above-mentioned interval of the fast Fourier transform, which represents a goal for the fast Fourier transform performed by the mentioned means of the fast Fourier transform, if the quality of the aligned signal received from the first mentioned signal, multiplexed with orthogonal frequency division in the frequency region higher than the quality of the aligned signal obtained from the mentioned second signal, multiplexed with orthogonal frequency division in the frequency domain, and the said means for determining a third location additionally determines the initial position of the other interval of the fast Fourier transform used to generate the aforementioned second signal, multiplexed with orthogonal frequent Tim separation in the frequency domain, as the initial position of the above-mentioned interval of the fast Fourier transform, which represents a goal for the next fast Fourier transform performed by the mentioned means of the fast Fourier transform, if the quality of the aligned signal obtained from the mentioned second signal, multiplexed with orthogonal frequency division in the frequency region higher than the quality of the aligned signal received from the first mentioned signal, multiplexed with orthogonal frequency division in the frequency domain.

7. The method containing the following steps:
provide the calculation means determine the first position of the correlation values between the signal, multiplexed with orthogonal frequency division in the field of time, the components of the signal, multiplexed with orthogonal frequency division in the field of time, representing the symbol multiplexing orthogonal frequency division on the one hand, and a signal obtained by delaying the above-mentioned signal, multiplexed with orthogonal frequency division in the field of time, the length of the effective symbol, on the other hand, to determine the initial position of the interval of the fast Fourier transform, which is referred to the length of the effective symbol and the cat is which is used as an interval signal, representing the target of the fast Fourier transform performed by means of the fast Fourier transform, with reference to the largest of these correlation values;
provide performance evaluation tool for determining the second position of the characteristics of the transmission channel is known signal included in the first signal, multiplexed with orthogonal frequency division in the frequency domain comprising signal, multiplexed with orthogonal frequency division in the frequency domain obtained by performing a fast Fourier transform to this signal, multiplexed with orthogonal frequency division in the field of time before interpolation estimates the characteristics of the transmission channel in the time direction to obtain assessment data characteristics of the transmission channel, before performing the inverse fast Fourier transform, for the said assessment data characteristics of the transmission channel, to assess the profile of the delay before the estimation of the interference between characters in relation to each of the set of candidates mentioned interval of the fast Fourier transform, on the basis of the delay profile, before receiving the initial position of the candidate mentioned interval of the fast Fourier transform, for which the amount of interest the conference between the characters is the smallest, as the initial position of the above-mentioned interval of the fast Fourier transform, fast Fourier transform performed using the means of the fast Fourier transform;
ensure the mounting means for determining a third location of the other interval of the fast Fourier transform in position with a relative shift to the mentioned interval of the fast Fourier transform used to generate the first mentioned signal, multiplexed with orthogonal frequency division in the frequency domain, prior to performing the fast Fourier transform to this signal, multiplexed with orthogonal frequency division in the field of time, within the other interval of the fast Fourier transform, to generate a second signal, multiplexed with orthogonal frequency division in the frequency domain, before removing distortions from the mentioned first and second signals, multiplexed with orthogonal frequency division in the frequency domain, using characteristics the transmission channel of each of all subcarriers obtained by interpolation of such data to assess the characteristics of the transmission channel in the direction of the frequency, to generate an aligned signal before detecting the initial position providing Otago interval of the fast Fourier transform, representing the target of the fast Fourier transform performed by the mentioned means of the fast Fourier transform, on the basis of the quality of the generated aligned signals;
choose one of the start positions of the above-mentioned interval of the fast Fourier transform, which is defined using the definitions of the said first - mentioned third positions; and
perform a fast Fourier transform to this signal, multiplexed with orthogonal frequency division in the field of time, using the selected initial position, is selected as the initial position of the above-mentioned interval of the fast Fourier transform, to generate the first mentioned signal, multiplexed with orthogonal frequency division in the frequency domain.

8. The pickup device, comprising:
the definition block of the first position, is configured to calculate correlation values between the signal, multiplexed with orthogonal frequency division in the field of time, the components of the signal, multiplexed with orthogonal frequency division in the field of time, representing the symbol multiplexing orthogonal frequency division on the one hand, and a signal obtained by delaying the above-mentioned signal, multiplexers the aqueous orthogonal frequency division in the field of time, the length of the effective symbol, on the other hand, to determine the initial position of the interval of the fast Fourier transform, which is referred to the length of the effective symbol and which is used as an interval signal representing the target of the fast Fourier transform performed by the block fast Fourier transform, with reference to the largest of these correlation values;
the detection unit of the second position, is arranged to assess the characteristics of the transmission channel is known signal included in the first signal, multiplexed with orthogonal frequency division in the frequency domain, the components of the signal, multiplexed with orthogonal frequency division in the frequency domain obtained by performing a fast Fourier transform to this signal, multiplexed with orthogonal frequency division in the field of time before interpolation assess the characteristics of the transmission channel in the time direction to obtain assessment data characteristics of the transmission channel, before performing the inverse fast Fourier transform on the above assessment of the characteristics of the transmission channel, to assess the profile of the delay before the evaluation value interference between symbols in relation to each of the set of candidates cited Otago interval of the fast Fourier transform, on the basis of the delay profile before you can determine the initial position of the candidate mentioned interval of the fast Fourier transform, in which the amount of interference between symbols least, in the initial position of the above-mentioned interval of the fast Fourier transform, which represents a goal for the fast Fourier transform performed by the said block fast Fourier transform;
the definition block of the third pillar, made with the possibility to set a different interval of the fast Fourier transform in position with a relative shift to the mentioned interval of the fast Fourier transform used to generate the first mentioned signal, multiplexed with orthogonal frequency division in the frequency domain, prior to performing the fast Fourier transform to this signal, multiplexed with orthogonal frequency division in the field of time, within the other interval of the fast Fourier transform, to generate a second signal, multiplexed with orthogonal frequency division in the frequency domain, before removing the distortion of the mentioned first and second signals, multiplexed with orthogonal frequency division in the frequency domain using the features and advantages of the key transmission channel of each of all subcarriers, obtained by interpolation of such data to assess the characteristics of the transmission channel in the direction of the frequency, to generate an aligned signal before detecting the initial position of the above-mentioned interval of the fast Fourier transform, which represents a goal for the fast Fourier transform performed by the said block fast Fourier transform, on the basis of the quality of the generated aligned signals;
block selection is made with a choice of one of the primary provisions of the interval of the fast Fourier transform, which are determined by the block determining with said first mentioned in the third position; and
the mentioned block fast Fourier transform, implemented with the fast Fourier transform to this signal, multiplexed with orthogonal frequency division in the field of time, by using the initial position selected by the said block selection, as the initial position of the above-mentioned interval of the fast Fourier transform, to generate the first mentioned signal, multiplexed with orthogonal frequency division in the frequency domain.



 

Same patents:

FIELD: information technology.

SUBSTANCE: hard-decision bit from bits indicating the P-axial coordinate of a reception signal point is input into an area detection circuit, and based on the hard-decision bit input, the area detection circuit detects and outputs an area on the phase plane where the coordinate of the reception signal point is present. A soft-decision bit from bits indicating the coordinate of the reception signal point is input into a log-likelihood ratio (LLR) circuit, and based on the soft-decision bit input, the LLR circuit calculates a primary LLR. A LLR converter calculates the final LLR based on an output signal (area detection result) from the area detection circuit. In such a configuration, a log-likelihood ratio is calculated while limiting the scope within which the value of the log-likelihood ratio varies according to the position of the reception signal point, the interval between adjacent signal points including the hard-decision threshold of the bit.

EFFECT: log-likelihood ratio calculation at a higher rate while reducing the size of the circuit and consumed power, independent of the multilevel number of the modulation method.

22 cl, 17 dwg

FIELD: information technology.

SUBSTANCE: apparatus for transmitting data comprises an encoder for encoding data, a multiplexer for multiplexing the encoded data and a training sequence code (TSC), a modulator for modulating the multiplexed data using a defined modulation scheme and a transmitter for transmitting the modulated data. The modulator modulates TSC based on two constellation points having the highest absolute value and opposite signs among M constellation points in the constellation according to the defined modulation scheme.

EFFECT: high efficiency of transmitting and receiving data using a training sequence code.

20 cl, 17 dwg

FIELD: information technology.

SUBSTANCE: first evaluation of the wireless channel is obtained during restoration of a variety of parallel data streams on the basis of received pilot symbols. Detection is carried out for the received data symbols using the first channel evaluation to obtain detected symbols for the first data stream. Obtained detected symbols are decoded to receive the decoded first stream of data that are encoded again for obtaining repeatedly modulated symbols. The second channel evaluation is obtained on the basis of the repeatedly modulated symbols. The first and the second channel evaluations are joined together to obtain the third channel evaluation having the higher quality. The interfering signal determined by the first data stream is evaluated and removed using the third channel evaluation. Detection of symbols is carried out when removing the evaluated interference from the main stream using the third channel evaluation to obtain detected symbols for the second data stream. Obtained detected symbols are additionally decoded to receive the decoded data of the second data stream.

EFFECT: high-quality channel evaluation.

37 cl, 7 dwg

FIELD: radio communications, possible use in demodulators of radio-relay communication systems which use signals with quadrature amplitude manipulation.

SUBSTANCE: in accordance to the invention, error signal is generated every time when on two adjacent clock intervals change of modulating symbol value occurs, not only when sign change occurs. Device contains serially connected solving device (1), adder (4), second input of which is connected to output of solving device (1) through serially connected sign inverter (3) and first delay block (2), and multiplier (6), and also second delay block (5), connected to second input of device. Introduced are serially connected second adder (7), first input of which is connected to output of delay block (2), second input - to output of sign inverter (3), divider by two (8), and third adder (9), second input of which is connected to output of delay block (5), and its output - to second input of multiplier (6). Solving device (1) makes a decision about value of modulating symbol being receipt, and not about its sign.

EFFECT: increased interference resistance of device.

2 cl, 15 dwg, 1 tbl

FIELD: radio communications and radio communication systems.

SUBSTANCE: proposed demodulator that incorporates provision for receiving amplitude-modulated telephone data and transmitting frequency-telegraphy data over single radio communication channel at a time is provided with newly introduced demodulator channel for amplitude-modulated signal adder that enables compensation for noise occurring in demodulator due to frequency-telegraphy signal in received signal, channel organized to evaluate amplitude of frequency-telegraphy signal wherein noise resulting from amplitude-modulated signal in signal being received is compensated for, as well as channel separating useful information from frequency-telegraphy signal.

EFFECT: enlarged functional capabilities.

1 cl, 1 dwg

FIELD: communications.

SUBSTANCE: demodulation device for 64-based quadrature amplitude modulation for receipt of input signal, which contains k-numbered quadrature signal and k-numbered common-mode signal, which contains first and second soft solution generators, which are made with possible generation of soft solution values on basis of given equations.

EFFECT: higher efficiency.

3 cl, 6 dwg

FIELD: radio engineering; demodulating sixteen-position quadrature-amplitude keyed signals.

SUBSTANCE: proposed demodulator, type KAM-16, has three phase detectors, two solvers, two four-position modulators, three subtracters, adder, amplifier, two multipliers, two limiters, low-pass filter, voltage-controlled generator, and four EXCLUSIVE OR gates. Amplitude difference of demodulator quadrature subchannels is detected and eliminated by subjecting signal to following procedures. Demodulator input signal is decomposed by means of recovered carrier signal into cophasal and quadrature components which are passed through first and second controlled amplifiers, supplied to solver, and tetrad of demodulated characters (A, B, C, D) is obtained at demodulator output. Four-position phase keyed signal is obtained across output of first four-position modulator by means of recovered carrier signal and two digital characters (C, D) out of tetrad of demodulated characters (A, B, C, D).

EFFECT: enhanced noise immunity.

1 cl, 5 dwg

The invention relates to electrical engineering and can be used when the reception signal phase or combined amplitude and phase manipulation

The invention relates to modulation, transmission and reception of information signals

The invention relates to the field of radio and can be used in communication systems and radar systems

FIELD: information technologies.

SUBSTANCE: in a basic station there are several types of frequency band width for use in a communication system. The basic station comprises a transfer module, arranged with the possibility to transfer transferred data using a frequency band width from a number of several types of frequency band width in the frequency band aligned at a previously specified central frequency; and a multiplexing module made with the possibility of synchronisation channel multiplexing into a central frequency band of the previously specified width, including a central frequency of frequency band used in a transfer module, no matter what the frequency band width used in the transfer module is.

EFFECT: simplified procedure of connection to a downlink.

28 cl, 21 dwg

FIELD: information technology.

SUBSTANCE: RAKE receiver for mixed services based on code division multiple access broadband system includes a module (2) for high-speed reading/repeating antenna data, which transmits the control signal to a module (4) for controlling reading-recording antenna data twice within frame time; a module for controlling reading-recording antenna data, which speeds up frame transmission of delayed antenna data to a buffer module (6) for antenna data upon reception of the control signal; a module (5) for controlling multi-beam parameters, which transmits multi-beam parameters to the module (8) for multi-beam demodulation for controlling reading of antenna data in accordance with various types of services and controls a module (9) for generating scrambling and channel-forming codes jointly with a module (11) for controlling user parameters for generating corresponding scrambling and channel-forming codes needed for the multi-beam demodulation module (8); as well as a module (6) for buffering antenna data, which buffers delayed antenna data and accelerated antenna data are output after delay.

EFFECT: reducing use of resources.

10 cl, 8 dwg

FIELD: information technologies.

SUBSTANCE: to transfer messages changed from one information symbol to another, orthogonal code combinations are used, such as ensembles of discrete orthogonal signals generated by calculation of own numbers and own vectors of a diagonal positively determined symmetrical matrix, diagonal coefficients of which are chaotically generated numerical sequences.

EFFECT: increased structural security of information transfer system with code division of channels by using ensembles of orthogonal signals, which are chaotically generated on the basis of own vectors of the diagonal positively determined symmetrical matrix with N dimension.

3 dwg

FIELD: radio engineering.

SUBSTANCE: when encoding information, an ultra-wideband signal is used, consisting of nanosecond duration pulses described by a Gaussian function first-order derivative. The sequence of these pulses will include pulses following with a fixed period called ''reference" pulses, as well as pulses in between the reference pulses called "central" pulses. Logic "zero" or "one" encoding information will be contained in the time position of the "central" pulses relative "reference" pulses. These pulse delays are determined based on cepstrum processing and the time delays determined this way are then converted to a sequence of logic "zeroes" and "ones".

EFFECT: reliability of extracting information.

9 dwg

FIELD: information technology.

SUBSTANCE: slave base station (64) attains synchronisation with the reference base station (62) through messages transmitted from and received by a mobile station (60) either in the soft handoff region between the reference base station (62) and the slave base station (64) or within a range which allows the mobile station (60) to communicate with the slave base station (64). When the mobile station (60) is not in communication with both the reference base station (62) and the slave base station (64), then the round trip delay between the mobile station and the reference base station is measured by the reference base station (62). The reference base station (62) communicates the PN code used by the mobile station over the reverse link to the slave base station. The slave base station (64) acquires the signal from the mobile station (60) and determines when the signal from the mobile station arrives. The slave base station (64) then makes an estimate as to the length of the delay between transmission of a signal from the mobile station (60) to the slave base station (64)/ Based upon these measurements and estimates, the slave base station (64) determines the error which is present in the slave base station system time.

EFFECT: high synchronisation accuracy.

99 cl, 9 dwg

FIELD: information technologies.

SUBSTANCE: device to receive and send OFDM-signals with high noise immunity comprises a noiseless coder - interleaver, a symbol mapper, a unit of pilot channels formation, a unit of pseudorandom phase modulation of subcarriers, a unit to calculate reverse Fourier transformation, a unit to insert a protective interval, a unit of digital-to-analogue transformation, I/Q-modulator-frequency converter, a transmitting antenna, a receiving antenna, a unit to calculate noise-signal ratio, I/Q-demodulator-frequency converter, a unit of analogue-to-digital conversion, a unit to calculate direct Fourier transformation, a phase demodulator of subcarriers, a unit to assess and adjust channel parameters, a symbol demapper, a noiseless decoder-deinterleaver.

EFFECT: improved noise immunity.

3 dwg

FIELD: information technologies.

SUBSTANCE: method is carried out by development of a multi-channel serial Viterbi decoder, comprising the following functional units, interrelated to each other: an input buffer, a generator of a data word reading signal from the input buffer, a decoder of a data word command field, a unit of channel parameter registers, a unit to process a command "path metrics nullification", a unit to process a command "setting a value of the specified path metric", a unit to process a command "reading a bit from a path with the specified number", a unit to process a command "processing of input counts", a main memory of decoding paths and path metrics, a unit to generate a basic address of the main memory area of decoding paths and path metrics for the current decoding channel, a unit to generate an address of the main memory cell of decoding paths and path metrics and a unit of registers of decoding channels output data.

EFFECT: provision of the possibility to treat coded units of the final length for designs of the following types - terminated, truncated, circular ones.

3 cl, 3 dwg

FIELD: information technology.

SUBSTANCE: larger code space can be defined by introducing multiple code clusters within a sector, wherein each cluster has a unique scrambling code. Codes within a cluster can have orthogonal Walsh sequences that can be assigned to user devices to facilitate communicating over a wireless network and can overlap with codes in another cluster. The unique scrambling code assigned to each cluster can ensure that duplicate Walsh sequences in another cluster in the same sector appear as pseudo-noise codes.

EFFECT: high carrying capacity in WCDMA wireless network with limited codes.

35 cl, 9 dwg

FIELD: information technology.

SUBSTANCE: transmitting device and system for transmitting information objects have a coder which includes a pre-coding unit (PCU), a modulator, a synchronous sequence addition unit (SAD), a multiplexer, a sampling buffer (SB), a packet formation unit (PFU), a control data generator (CDG), a control data coder (CDC), a sample number generator (SNG) and a coder address generator (CAG).

EFFECT: high rate of transmitting information objects.

25 cl, 4 dwg

FIELD: radio engineering.

SUBSTANCE: there is proposed transmitting and receiving devices providing improvement of signal quality in ascending and descending channels which perform simultaneous radio transmission and reception of various signals from the appropriate antennae of the variety of antennae. Devices include multiplexing means of pilot signal, which use one or more of the following methods: multiplexing method with separation as to time, multiplexing method with separation as to frequency and multiplexing method with code separation, for multiplexing of pilot channels subject to being transmitted and received from the appropriate antennae; data multiplexing means having the possibility of time multiplexing of pilot channels and data channels; and means for transmission of signal by means of at least one of the following methods: spatial division multiplexing method (SDM) and spatial time transmission deviation method (STTD).

EFFECT: improving signal quality in ascending and descending channels.

10 cl, 19 dwg

FIELD: radio engineering.

SUBSTANCE: suggested algorithm for quasi-coherent receipt of multi-beam signal with continuous pilot signal is based on algorithm, adaptive to freeze frequencies, for estimation of complex skirting curve, which uses both pilot and information signal. Use of information symbols for estimation of complex skirting curve allows, with weak pilot signal, to substantially increase precision of estimation of said curve and, as a result, significantly decrease possible error of information parameters estimation.

EFFECT: higher interference resistance.

2 cl, 10 dwg

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